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0018-926X (c) 2013 IEEE. Personal use is permitted, but republication/redistribution requires IEEE permission. Seehttp://www.ieee.org/publications_standards/publications/rights/index.html for more information.
This article has been accepted for publication in a future issue of this journal, but has not been fully edited. Content may change prior to final publication. Citation information: DOI10.1109/TAP.2014.2298246, IEEE Transactions on Antennas and Propagation
IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. AA, NO. B Nov. 2013
1
Abstract—By combining a printed reflector-backed one-wave-
length bowtie antenna and a printed double loop antenna, a new
wideband high-gain antenna element is demonstrated. Due to its
low-profile structure of ~0.05λ0, it is attractive to be used in an
array environment. Experimentally, a series of antenna arrays
operated at 60 GHz are designed and fabricated. They achieve
wide impedance bandwidths covering the 57–64 GHz unlicensed
frequency band. Over this band, the measured antenna gains are
ranged from 14.5–15.5 dBi, 18.3–20.1 dBi and 22.5–25.2 dBi for
4-element, 14-element and 50-element antenna arrays, respectively.
The measured radiation pattern has low cross-polarization level
and low back radiation. The proposed low-profile antenna and
arrays are low-cost in fabrication as they are simply made on a
single-layer printed circuit board.
Index Terms—Low-profile antenna, wideband antenna,
antenna array, 60 GHz radio.
I. INTRODUCTION
ITH the advancement of millimeter-wave (MMW)
technologies, various applications have been proposed,
such as the 39-GHz band for licensed high-speed data links[1],
60-GHz band for unlicensed short range data links [2], 77-GHz
band for automotive radar [3], 94-GHz band for imaging radar
[4], and 71–76, 81–86, 92–95 GHz bands for point-to-point
high bandwidth communication links. For these applications,
the high free space loss and strong atmospheric absorption limit
the distance of communications. Thus, high-gain antennas are
normally required to mitigate the attenuation of such
high-frequency electromagnetic radiation.
Recently, many antennas and arrays with good directional
property were proposed in [5]–[15] for the unlicensed 57–64
GHz frequency band due to many attractive applications
including high definition multimedia interface, high definition
video streaming, high-speed internet, and wireless gigabit
Ethernet. Most of these designs are made of multi-layer
substrates which increase antenna complexity and
manufacturing costs, regardless of using any fabrication
techniques such as printed circuit board (PCB), liquid crystal
Manuscript received Nov. 2, 2013. This work was supported in part by the
Research Grants Council of the Hong Kong SAR and CityU Strategic Research
Grant. [Project No. CityU 9041677 and SRG 7008113]
The authors are with the Department of Electronic Engineering and the State
Key Laboratory of Millimeter Waves, City University of Hong Kong, Hong
Kong (phone: 852-97152234; e-mail: [email protected]).
polymer (LCP) and even low-temperature co-fired ceramic
(LTCC). Among those antennas, Yagi antenna is a good
solution for high gain applications [5], [6]. In [6], the method of
placing stacked Yagi directive elements on a 4 × 4 patch
antenna array fed by a substrate integrated waveguide (SIW)
network realized a high gain and low side-lobe performance.
Slot antenna array also exhibits high-gain property [7]–[9]. The
use of backed cavity as reflector and radiating element
enhancing antenna gain and impedance bandwidth was reported
in [7]. The plate-laminated slot array excited by a
hollow-waveguide corporate-feed achieved a high gain of over
32 dBi [8]. In 2011, Grid array antennas at 60-GHz band were
first proposed by Zhang, et al. [11]. The antenna achieved a
maximum gain of 17.7 dBi [11]. In addition, based on cavity
array, horn antenna, magneto-electric dipole and tapered slot,
many millimeter-wave antennas with good performances were
designed [12]–[15].
For practical use, antennas that are low in fabrication cost and
low in profile are highly desirable. Microstrip patch antenna is a
competitive choice. Several designs on metamaterial structures
or superstrate enable a patch element to achieve high gain at
60-GHz band [16]–[18]. However, these techniques need
multi-layer fabrication, and therefore lose the low-cost
advantage of microstrip antenna. Array of patch elements can be
used for realizing high gain. The microstrip line fed microstrip
antenna array is a single-layer structure, and hence low in
fabrication cost, but suffers from narrow bandwidth [19].
Techniques are available to enhance the bandwidth of
microstrip antennas but multi-layer structures are unavoidable,
including using L-probe feed [20], stacked patches [21], U-slot
patch [22] and aperture coupled feed [23].
In this paper, we present a new unidirectional radiating
element consisting of a planar reflector-backed one-wavelength
bowtie and a double-loop antenna. Design of high gain antenna
arrays based on this antenna element is also investigated. These
antenna array prototypes are fabricated by using a single-layer
printed circuit board technology and designed to operate at
60-GHz band. They have a low profile of 0.05λ0 (λ0 is the
wavelength referring to 60GHz) and achieve wide impedance
bandwidths and high gains. The design process, broadband
characteristic and radiation pattern for single element are
elaborated in Section II. Three antenna arrays of 4-element,
14-element and 50-element are investigated in Section III.
A Low-Profile Unidirectional Printed Antenna
for Millimeter-Wave Applications
Mingjian Li and Kwai-Man Luk, Fellow, IEEE
W
0018-926X (c) 2013 IEEE. Personal use is permitted, but republication/redistribution requires IEEE permission. Seehttp://www.ieee.org/publications_standards/publications/rights/index.html for more information.
This article has been accepted for publication in a future issue of this journal, but has not been fully edited. Content may change prior to final publication. Citation information: DOI10.1109/TAP.2014.2298246, IEEE Transactions on Antennas and Propagation
IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. AA, NO. B Nov. 2013
2
II. ANTENNA ELEMENT
A. Design Process
Practical applications at millimeter wave usually require
high-gain unidirectional radiation antennas. If we design a
millimeter-wave antenna array in a single-layer structure, the
dielectric substrate must be properly chosen for minimizing the
insertion loss of the feeding network and assuring the validity of
using microstrip line at millimeter wave. Too thin substrate
gives large conductor loss and too thick substrate introduces
large radiation loss [24]. In this paper, Duroid 5880 substrate is
chosen as its thickness = 0.254 mm (~0.05λ0, λ0 is the
wavelength at 60 GHz in free space), dielectric permittivity εr =
2.24, metal thickness t = 1/2 oz and loss tangent tanδ = 0.004 at
60 GHz [25]. On this substrate, 46.5–170 ohm microstrip lines
can be achieved practically (line width 0.035–0.89 mm) at 60
GHz. Hence, we need an antenna which possesses wideband
and low-profile characteristics at the same time. Microstrip line
fed microstrip antenna has a low profile but suffers from a
narrow bandwidth. A conventional half-wavelength dipole
antenna has a wide bandwidth, but it should be placed above a
reflector with a distance of about λ/4 for achieving a reasonable
performance.
Fig. 1(a) shows a trapezoidal microstrip patch antenna which
is excited at its edge. This antenna is very narrow in bandwidth
as no bandwidth enhancement technique is employed [20]–[23].
Fig. 1(b) shows a reflector-backed one-wavelength bowtie
antenna which consists of two portions, the upper dipole arm
and the lower dipole arm. The upper arm is operated as a
microstrip line fed trapezoidal microstrip patch antenna which
is identical to the antenna shown in Fig. 1(a). The lower arm,
placed opposite to the upper arm, is operated as another
trapezoidal microstrip patch antenna. This arm is excited by a
microstrip-line (MSL) to coplanar-waveguide (CPW) transition
which also feeds the upper arm at its output end. This transition,
composed of two sections including a tapered section and a
straight section (Cw = 0.2mm, gap = 0.03mm), ensures the 1λ
bowtie antenna with a relatively wide impedance bandwidth. As
shown in Fig. 1(c), the reflector-backed one-wavelength bowtie
antenna is loaded with two 1λ loops. The two loops, working as
the conventional double-quad or bi-quad antenna [26], are
connected in parallel to the bowtie antenna for broadening the
antenna impedance bandwidth further. The dimensions of the
proposed antenna element are summarized in TABLE I.
B. Broadband Characteristic
Fig. 2 shows the input impedances of the three antennas
shown in Fig. 1. The trapezoidal microstrip patch antenna
resonates at around 50 GHz with a very large Re (Z11). It can be
easily matched to 50 ohm but will be narrowband owing to its
single resonance. The reflector-backed one-wavelength bowtie
antenna has two electrical resonances at around 51 GHz and
56.5 GHz which are caused by the upper and lower dipole arms,
Excitation/2
Excitation
MSL-CPW Transition
1
(a) (b)
Excitation
Cw
MSL-CPW
Transition
Bottom
LayerTop
Layer
W50
D2
W
S1
L1
D3
S3
D1S2L2
1 Loops
(c)
Fig. 1. Antenna design process. (a) Perspective view of the trapezoidal
microstrip patch antenna, (b) perspective view of the reflector-backed
one-wavelength bowtie antenna, (c) top view of the loop-loaded
reflector-backed one-wavelength bowtie antenna.
TABLE I
DIMENSIONS FOR THE PROPOSED ANTENNA
Parameter D1 D2 D3 L1 L2
Value(mm) 3.58
1.00λ 2.7
0.76λ 1
0.28λ 3.08
0.86λ 1.98
0.55λ
Parameter S1 S2 S3 W
Value(mm) 1.5
0.42λ 0.28
0.08λ 4.1
1.15λ 0.1
0.03λ
λ is one electrical wavelength in Duroid 5880 substrate at 60 GHz.
Fig. 2. Input impedances of the trapezoidal microstrip patch antenna,
reflector-backed one-wavelength bowtie antenna and loop-loaded reflector-backed one-wavelength bowtie antenna.
0018-926X (c) 2013 IEEE. Personal use is permitted, but republication/redistribution requires IEEE permission. Seehttp://www.ieee.org/publications_standards/publications/rights/index.html for more information.
This article has been accepted for publication in a future issue of this journal, but has not been fully edited. Content may change prior to final publication. Citation information: DOI10.1109/TAP.2014.2298246, IEEE Transactions on Antennas and Propagation
IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. AA, NO. B Nov. 2013
3
respectively. The two arms, operated as two trapezoidal patches,
have different resonant frequencies due to their different
feeding methods. From 50 to 65 GHz, the Re (Z11) and Im (Z11)
of the bowtie antenna vary substantially from 18 to 187 ohm and
-60 to 86 ohm, respectively. The loop-loaded reflector-backed
one-wavelength bowtie antenna possesses three resonances at
around 52 GHz, 56 GHz and 63 GHz. Like the bowtie antenna,
the first two resonances are from the bowtie arms and the third
resonance is introduced by the loaded 1λ loops. The loops,
paralleled with the bowtie, reduce the magnitudes of the Re (Z11)
and Im (Z11) below 59 GHz. Meanwhile, the input impedance
above 59 GHz is increased because of the third resonance
introduced. Hence, compared with the bowtie antenna, this
loop-loaded bowtie antenna element has more stable input
impedance with Re (Z11) of 26–95 ohm and Im (Z11) of -25–50
ohm from 50 to 65 GHz.
C. Radiation Pattern
Fig. 3 shows a simulated radiation pattern of the loop-loaded
dipole antenna at 60 GHz. The maximum gain is about 10 dBi in
the broadside direction. The radiation pattern in the E-plane is
slightly asymmetrical and the cross-polarization level in the
H-plane is high, over -15 dB, which are due to the separation in
one arm of the bowtie to make space for the microstrip-line to
coplanar-waveguide transition. To justify this argument, a
loop-loaded electric dipole antenna excited at its center (without
the MSL to CPW transition) is examined as shown in Fig. 4. It
demonstrates that symmetrical radiation patterns in both
principle planes are achieved. Since the cross-polarization
levels are lower than -40 dB in both planes, the x-pol curves
cannot be shown in the figure.
III. ANTENNA ARRAYS
A. Array Geometries
Fig. 5(a) shows the 4-element antenna array (D3 = 1.4 mm, S1
= 1.9 mm) which adopts the parallel feeding method. This
method suffers from an asymmetrical radiation pattern with a
slightly high cross-polarization level because of the radiation
loss from the feed lines and the element asymmetrical geometry
caused by the MSL to CPW transition.
Fig. 5(b) shows the 14-element antenna array (D3 = 1.4 mm,
S1 = 1.9 mm, L1 = 2.78 mm and L2 = 1.68 mm). It adopts the
hybrid series/parallel feeding method. This method has smaller
frequency sensitivity of the radiation pattern than a purely series
feeding method and therefore achieves a wider gain bandwidth.
The reason is that nearly each frequency dependent microstrip
line segment in the network can find a counterpart in which the
current is in 180° phase difference. Meanwhile, compared with
the parallel feeding method, the series/parallel feeding method
reduces microstrip lines used in the network when exciting an
array with a given number of elements [24], [27]. Thus, this
method has lower insertion loss.
Fig. 5(c) shows the 50-element antenna array which also
adopts the hybrid series/parallel feeding method. Each element
Screws
Feed
point
Antenna fixture
Duroid
5880
15mm
Screws
Feed
point
Antenna fixture
Duroid
5880
20mm
(a) (b)
Duroid5880
Feedpoint
T-Junction Shift
Screw
35mm
Line 1
Line 2
Line 3
Line 4
Line 5 (2 line)
Junction shift
Antenna fixture
/2
line
1
line (~0.80)
Line 6 (2 line)
W100
Ref. 1
Ref. 2
Unconnected
element
Adjacent
elements
Oppesite
elements
(c)
Fig. 5. Top and side views of the proposed antenna arrays. (a) 4-element array,
(b) 14-element array, (c) 50-element array.
Fig. 3. Radiation pattern of the loop-loaded reflector-backed one-wavelength
bowtie antenna at 60 GHz.
Excitation
Fig. 4. Loop-loaded reflector-backed one-wavelength bowtie antenna excited
at its center and its radiation pattern at 60 GHz.
0018-926X (c) 2013 IEEE. Personal use is permitted, but republication/redistribution requires IEEE permission. Seehttp://www.ieee.org/publications_standards/publications/rights/index.html for more information.
This article has been accepted for publication in a future issue of this journal, but has not been fully edited. Content may change prior to final publication. Citation information: DOI10.1109/TAP.2014.2298246, IEEE Transactions on Antennas and Propagation
IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. AA, NO. B Nov. 2013
4
is through a 100 ohm impedance transformer (W100 = 0.2mm) to
increase the antenna output impedance. And then it is connected
to its opposite neighboring elements through λ/2 71 Ω lines
(Line 1, 2, 3 & 4), so that the signals at Ref. 1 and Ref. 2
reference planes are 180° apart, which is vital for achieving a
broadside radiation beam and suppressing the radiation losses
due to the element asymmetry geometry, as mentioned in
Section II-C. This also means that the adjacent elements are
joined through 1λ lines (Line 1, 2, 3 & 4), which makes the
element spacing equals to ~0.8λ0 (λ0 is the wavelength at 60
GHz in free space). The Line 2 and Line 3 are responsible for
feeding the middle 28 elements. And the Line 1 and Line 4 feed
the upper and lower 22 elements. Notice that the Line 1, 2, 3 & 4
do not function as impedance transformers because of λ/2 lines
between opposite neighboring elements [25]. The Line 5 and
Line 6 with 2λ are responsible for connecting the Line 1 & 2 and
Line 3 & 4, respectively. The junctions in the middle of the Line
2 and Line 3 are shifted upwards and downwards respectively
for keeping a length of 2λ for the Line 5 & 6, so that all elements
can be excited in phase. The junctions of the Line 2 & 3 joined
to the feed point through λ/4 50 Ω impedance transformers (W50
= 0.7mm) and tapered lines for impedance transformation. The
feed point is positioned at the lower side of the substrate for the
sake of confirming 180° phase difference at the junctions of the
Line 2 & 3. It can be observed that most of the elements are
connected together at the edges of the loops for reducing the
element spacing to ~0.8λ0. The connection between adjacent
elements has no influence on the element operation. The reason
is that the main electromagnetic radiation is from the radiating
slots of the bowtie arms. Although some part of the radiation is
from the loops, especially at higher frequencies, the adjacent
elements are in phase and therefore the connection between
them will not affect the element radiation. The unconnected
elements are not joined to their adjacent elements for leaving
enough space occupied by the vertical lines (such as Line 5 & 6).
This 50-element array, printed on the single-layer Duroid 5880
substrate, is mounted on an aluminum antenna fixture (thickness
= 1.5 mm) by using four metal screws (M1). A V-band
connector (SHF: KPC185F302) and a glass bead (SHF: GB185)
are assembled together and launched at the back of the antenna
fixture. The inner conductor of the connector is connected to the
array feed network at the feed point, as shown in Fig. 5. In
practice, the three proposed arrays may be integrated into a
60-GHz MMIC or silicon CMOS system directly so that the
antenna fixture is not a compulsory part.
B. Array Performances
All simulations were implemented by EM simulation
software Ansoft HFSS. In simulation, the setups for the
substrate and metal are referred to [25] (εr = 2.24, tanδ = 0.004,
ρcopper = 5.8 × 107 S/m). And the measurements on impedance
bandwidth, gain and radiation patterns were accomplished by a
millimeter wave band Agilent E8361A Network Analyzer and
an in-house far-field millimeter-wave antenna measurement
system which was also employed in [14]. It is noted that this
system has been updated so as to broaden the measurable
elevation angle range to ±90°. The details on the measurement
setup have been introduced in [14].
Fig. 6 shows the simulated and measured SWRs of the three
proposed arrays. The measured impedance bandwidths of the
4-element, 14-element and 50-element arrays (SWR ≤ 2) are
24.2% (51.8 to 66.1GHz), > 24% (55 to 70 GHz) and > 16.7%
(56.7 to 67 GHz), respectively, which all cover 57–64 GHz
band. Fig. 7 shows the simulated and measured broadside gains
of the proposed arrays. The measured 3-dB gain bandwidths of
the 4-element, 14-element and 50-element arrays are 20.9%
(54.3 to 67 GHz), 18.9% (56.4 to 68.2 GHz) and 12.5% (57 to
64.6 GHz), respectively. For the sake of the series/parallel
feeding method, the gain bandwidth tends to decrease, as the
number of antenna elements increases [27]. The measured peak
gains for the three arrays are 15.5dBi at 60.2GHz, 20.1dBi at
61GHz and 25.2 dBi at 58.4 GHz. The overlapped 3dB gain
(a)
(b)
(c)
Fig. 6. Simulated and measured SWRs. (a) 4-element array, (b) 14-element
array, (c) 50-element array.
Fig. 7. Simulated and measured gains of the 4-element, 14element and
50-element antenna arrays.
0018-926X (c) 2013 IEEE. Personal use is permitted, but republication/redistribution requires IEEE permission. Seehttp://www.ieee.org/publications_standards/publications/rights/index.html for more information.
This article has been accepted for publication in a future issue of this journal, but has not been fully edited. Content may change prior to final publication. Citation information: DOI10.1109/TAP.2014.2298246, IEEE Transactions on Antennas and Propagation
IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. AA, NO. B Nov. 2013
5
bandwidth and the impedance bandwidth for the 4-element,
14-element and 50-element arrays is 19.6% (54.3 to 66.1 GHz),
18.9% (56.4 to 68.2 GHz) and 12.5% (57 to 64.6 GHz),
respectively. Simulations are in relatively good agreement with
results obtained from experiments. Fig. 8 shows the simulated
and measured radiation patterns of the 50-element antenna array.
Over the whole operating frequency band, the measured
radiation pattern exhibits a cross-polarization level less than -30
dB, front-to-back ratio larger than 31 dB and the first side-lobe
level less than -9 dB. Both the measured and simulated results
agree very well. By applying the Tai and Pereira equation [28],
the antenna directivity can be evaluated. The approximated
directivity at 60 GHz is 26.5 dBi, and the corresponding
radiation and aperture efficiencies are 63.7% and 72.5%,
respectively.
Photos of the array prototypes with 4 elements, 14 elements
and 50 elements are shown in Fig. 9. The key data of our works
and other arrays for 60-GHz applications is summarized in
TABLE II. It is noted that our proposed low-cost low-profile
printed antenna arrays, fabricated by using single-layer PCBs,
achieve wide impedance bandwidth, high gain, and high
radiation and aperture efficiencies.
TABLE II
KEY DATA OF ANTENNA ARRAYS FOR 60GHZ APPLICATIONS.
Ref. Type No. of
Layer
No. of
Element Size (mm3)
Impedance
Bandwidth
3dB Gain
Bandwidth
Max Gain
(dBi)
Aperture
Efficiency
Radiation
Efficiency
[6] Yagi (PCB) 6 16 28×24×2.4 10.5% 7% 18 n.a. n.a.
[8] Slot (Plate-laminated) 22 256 75×76×6.6 7.9% >7.9% 33 88.7% >70%
[9] Slot (PCB) 1 144 30.7×30.7×0.508 4.1% >4.1% 22 41.2% 68%
[11] Grid (LTCC) 3 60 15×15×0.6 18.7% 17.2% 17.7 59.9%* n.a.
[12] Cavity (LTCC) 20 64 47×31×2 17.1% >17.1% 22.1 49.8% 44.4%
[20] Patch (LTCC) 10 16 14.4×14.4×1 29% 18.3% 17.5 n.a. n.a.
14-element Loop-loaded dipole (PCB) 1 14 20×20×0.254 22.1% 18.9% 20.1 71.9% 69.7%
50-element Loop-loaded dipole (PCB) 1 50 35×35×0.254 >16.7% 12.5% 25.2 72.5% 63.7%
The aperture efficiency and radiation efficiency are the measured values at the operation frequency of each antenna (60 GHz for our works).
* Aperture efficiency was calculated from simulated 90% radiation efficiency.
E-Plane H-Plane
-40
-30
-20
-10
0
0
30
60
90
120
150
180
210
240
270
300
330
-40
-30
-20
-10
0
-40
-30
-20
-10
0
0
30
60
90
120
150
180
210
240
270
300
330
-40
-30
-20
-10
0
57 GHz
-40
-30
-20
-10
0
0
30
60
90
120
150
180
210
240
270
300
330
-40
-30
-20
-10
0
-40
-30
-20
-10
0
0
30
60
90
120
150
180
210
240
270
300
330
-40
-30
-20
-10
0
60 GHz
-40
-30
-20
-10
0
0
30
60
90
120
150
180
210
240
270
300
330
-40
-30
-20
-10
0
-40
-30
-20
-10
0
0
30
60
90
120
150
180
210
240
270
300
330
-40
-30
-20
-10
0
64 GHz
Fig. 8. Simulated and measured radiation patterns of the 50-element antenna
array at 57 GHz, 60 GHz, and 64 GHz.
(a)
Feed point
V-band connectorSHF: KPC185F302
Copperground
Antenna fixture
(b) (c) (d)
Fig. 9. Photos of the antenna array prototypes. (a) Top view of all proposed
arrays, (b) backside view of the fabricated PCB for 50-element array, (c)
backside view of the 50-element array with antenna fixture, (d) side view of
the 50-element array with antenna fixture.
0018-926X (c) 2013 IEEE. Personal use is permitted, but republication/redistribution requires IEEE permission. Seehttp://www.ieee.org/publications_standards/publications/rights/index.html for more information.
This article has been accepted for publication in a future issue of this journal, but has not been fully edited. Content may change prior to final publication. Citation information: DOI10.1109/TAP.2014.2298246, IEEE Transactions on Antennas and Propagation
IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. AA, NO. B Nov. 2013
6
IV. CONCLUSION
A new printed loop-loaded reflector-backed one-wavelength
bowtie antenna has been presented. This element has a low
profile of ~0.05λ0 and stable input impedance at the same time.
Based on this element, a series of low-cost single-layer antenna
arrays were designed and fabricated at 60 GHz. They have wide
impedance bandwidths covering 57–64 GHz and high gain
properties. The unidirectional radiation patterns exhibit low
cross-polarization and back radiation levels. The measured
results of the fabricated prototypes are in good agreement with
simulated results. In addition, the proposed antenna array made
of single-layer printed circuit board is very low cost in
fabrication. They are excellent candidates for various low-cost
millimeter-wave systems.
ACKNOWLEDGMENT
The authors would like to thank Mr. Kung Bo Ng for helping
with the antenna measurements. This work was supported in
part by the Research Grants Council of the Hong Kong SAR and
CityU Strategic Research Grant. [Project No. CityU 9041677
and SRG 7008113]
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2005.
Mingjian Li (S’10) received the B.Sc. (Eng.)
degrees in electronic and communication
engineering from City University of Hong Kong in
2010, where he is currently pursuing Ph.D. degree.
His recent research interests include wideband
antennas, millimeter-wave antennas and arrays, base
station antennas, circularly-polarized antennas and
small antennas.
Mr. Li received the Honorable Mention at the
student contest of 2011 IEEE APS-URSI Conference
and Exhibition held in Spokane, US. He was
awarded the Best Student Paper Award (Second Prize) in the 2012 IEEE
International Workshop on Electromagnetics (IEEE iWEM2012) held in
Chengdu, China.
0018-926X (c) 2013 IEEE. Personal use is permitted, but republication/redistribution requires IEEE permission. Seehttp://www.ieee.org/publications_standards/publications/rights/index.html for more information.
This article has been accepted for publication in a future issue of this journal, but has not been fully edited. Content may change prior to final publication. Citation information: DOI10.1109/TAP.2014.2298246, IEEE Transactions on Antennas and Propagation
IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. AA, NO. B Nov. 2013
7
Kwai-Man Luk (M’79–SM’94–F’03) was born and
educated in Hong Kong. He received the B.Sc. (Eng.)
and Ph.D. degrees in electrical engineering from The
University of Hong Kong in 1981 and 1985,
respectively.
He joined the Department of Electronic
Engineering, City University of Hong Kong, in 1985
as a Lecturer. Two years later, he moved to the
Department of Electronic Engineering, Chinese
University of Hong Kong, where he spent four years.
He returned to the City University of Hong Kong in
1992, and is currently Chair Professor of Electronic Engineering and Director
of State Key Laboratory in Millimeter waves (Hong Kong). He is the author of
three books, nine research book chapters, over 290 journal papers and 220
conference papers. He has received five US and more than 10 PRC patents. His
recent research interests include design of patch, planar and dielectric resonator
antennas, and microwave measurements.
Prof. Luk is a Fellow of the Chinese Institute of Electronics, PRC, a Fellow
of the Institution of Engineering and Technology, UK, a Fellow of the Institute
of Electrical and Electronics Engineers, USA and a Fellow of the
Electromagnetics Academy, USA. He is Deputy Editor-in-Chief of PIERS
journals. He was a Chief Guest Editor for a special issue on “Antennas in
Wireless Communications” published in the PROCEEDINGS OF THE IEEE in July
2012. He was Technical Program Chairperson of the 1997 Progress in
Electromagnetics Research Symposium (PIERS), General Vice-Chairperson of
the 1997 and 2008 Asia-Pacific Microwave Conference (APMC), General
Chairman of the 2006 IEEE Region Ten Conference (TENCON), Technical
Program Co-chairperson of 2008 International Symposium on Antennas and
Propagation (ISAP), and General Co-chairperson of 2011 IEEE International
Workshop on Antenna Technology (IWAT). He received the Japan Microwave
Prize at the 1994 Asia Pacific Microwave Conference held in Chiba in
December 1994, and the Best Paper Award at the 2008 International
Symposium on Antennas and Propagation held in Taipei in October 2008. He
was awarded the very competitive 2000 Croucher Foundation Senior Research
Fellow in Hong Kong and the 2011 State Technological Invention Award (2nd
Honor) of China.
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