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14-Bit, 105/125 MSPS, IF Sampling ADC AD9445
Rev. 0 Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.Tel: 781.329.4700 www.analog.com Fax: 781.461.3113 2005 Analog Devices, Inc. All rights reserved.
FEATURES 125 MSPS guaranteed sampling rate (AD9445BSV-125) 78.3 dBFS SNR/92 dBFS SFDR with 30 MHz input (3.2 V p-p) 74.8 dBFS SNR/95 dBFS SFDR with 30 MHz input (2.0 V p-p) 77.0 dBFS SNR/87 dBFS SFDR with 170 MHz input (3.2 V p-p) 74.6 dBFS SNR/95 dBFS SFDR with 170 MHz input (2.0 V p-p) 73.0 dBFS SNR/88 dBFS SFDR with 300 MHz input (2.0 V p-p) 102 dBFS 2-tone SFDR with 30 MHz and 31 MHz 92 dBFS 2-tone SFDR with 170 MHz and 171 MHz 60 fsec rms jitter Excellent linearity
DNL = 0.25 LSB typical INL = 0.8 LSB typical
2.0 V p-p to 4.0 V p-p differential full-scale input Buffered analog inputs LVDS outputs (ANSI-644 compatible) or CMOS outputs Data format select (offset binary or twos complement) Output clock available 3.3 V and 5 V supply operation
APPLICATIONS Multicarrier, multimode cellular receivers Antenna array positioning Power amplifier linearization Broadband wireless Radar Infrared imaging Medical imaging Communications instrumentation
GENERAL DESCRIPTION
The AD9445 is a 14-bit, monolithic, sampling analog-to-digital converter (ADC) with an on-chip IF sampling track-and-hold circuit. It is optimized for performance, small size, and ease of use. The product operates at up to a 125 MSPS conversion rate and is designed for multicarrier, multimode receivers, such as those found in cellular infrastructure equipment.
The ADC requires 3.3 V and 5.0 V power supplies and a low voltage differential input clock for full performance operation. No external reference or driver components are required for many applications. Data outputs are CMOS or LVDS compatible (ANSI-644 compatible) and include the means to reduce the overall current needed for short trace distances.
FUNCTIONAL BLOCK DIAGRAM
CMOSOR
LVDSOUTPUTSTAGING
CLOCKAND TIMING
MANAGEMENT
AGND DRGND DRVDD
VREF
CLK+
VIN+
AD9445
VIN
CLKDCO
0548
9-00
1
AVDD1 AVDD2
DCS MODEDFSRF ENABLE
OUTPUT MODET/H
BUFFER14
PIPELINEADC
2
28
2
OR
D13 TO D0
REF
REFBSENSE REFT
Figure 1.
Optional features allow users to implement various selectable operating conditions, including input range, data format select, high IF sampling mode, and output data mode.
The AD9445 is available in a Pb-free, 100-lead, surface-mount, plastic package (100-lead TQFP/EP) specified over the industrial temperature range 40C to +85C.
PRODUCT HIGHLIGHTS
1. High performance: outstanding SFDR performance for IF sampling applications such as multicarrier, multimode 3G, and 4G cellular base station receivers.
2. Ease of use: on-chip reference and high input impedance track-and-hold with adjustable analog input range and an output clock simplifies data capture.
3. Packaged in a Pb-free, 100-lead TQFP/EP package.
4. Clock duty cycle stabilizer (DCS) maintains overall ADC performance over a wide range of clock pulse widths.
5. OR (out-of-range) outputs indicate when the signal is beyond the selected input range.
6. RF enable pin allows users to configure the device for optimum SFDR when sampling frequencies above 210 MHz (AD9445-125) or 240 MHz (AD9445-105).
AD9445
Rev. 0 | Page 2 of 40
TABLE OF CONTENTS Features .............................................................................................. 1
Applications....................................................................................... 1
General Description ......................................................................... 1
Functional Block Diagram .............................................................. 1
Product Highlights ........................................................................... 1
Revision History ............................................................................... 2
Specifications..................................................................................... 3
DC Specifications ......................................................................... 3
AC Specifications.......................................................................... 4
Digital Specifications ................................................................... 6
Switching Specifications .............................................................. 6
Timing Diagrams.......................................................................... 7
Absolute Maximum Ratings............................................................ 8
Thermal Resistance ...................................................................... 8
ESD Caution.................................................................................. 8
Terminology .......................................................................................9
Pin Configurations and Function Descriptions ......................... 10
Equivalent Circuits ......................................................................... 15
Typical Performance Characteristics ........................................... 16
Theory of Operation ...................................................................... 24
Analog Input and Reference Overview ................................... 24
Clock Input Considerations...................................................... 26
Power Considerations................................................................ 27
Digital Outputs ........................................................................... 27
Timing ......................................................................................... 27
Operational Mode Selection ..................................................... 28
Evaluation Board ............................................................................ 29
Outline Dimensions ....................................................................... 37
Ordering Guide .......................................................................... 37
REVISION HISTORY
10/05Revision 0: Initial Version
AD9445
Rev. 0 | Page 3 of 40
SPECIFICATIONS DC SPECIFICATIONS AVDD1 = 3.3 V, AVDD2 = 5.0 V, DRVDD = 3.3 V, LVDS mode, specified minimum sampling rate, 2.0 V p-p differential input, internal trimmed reference (1.0 V mode), AIN = 1.0 dBFS, DCS on, unless otherwise noted. RF ENABLE = AGND.
Table 1. AD9445BSVZ-105 AD9445BSVZ-125 Parameter Temp Min Typ Max Min Typ Max Unit RESOLUTION Full 14 14 Bits ACCURACY
No Missing Codes Full Guaranteed Guaranteed Offset Error Full 7 +7 7 +7 mV 25C 3 3 mV Gain Error Full 3 +3 3 +3 % FSR 25C 2 +2 2 +2 % FSR Differential Nonlinearity (DNL)1 Full 0.6 0.25 +0.65 0.6 0.25 +0.65 LSB 5 5 Integral Nonlinearity (INL)1 25C 0.65 0.8 LSB Full 1.6 +1.6 2 +2 LSB
VOLTAGE REFERENCE Output Voltage VREF = 1.0 V Full 0.9 1.0 1.1 0.9 1.0 1.1 V Load Regulation @ 1.0 mA Full 2 2 mV Reference Input Current (External VREF = 1.6 V) Full A
INPUT REFERRED NOISE 25C 1.0 1.0 LSB rms ANALOG INPUT
Input Span VREF = 1.6 V Full 3.2 3.2 V p-p VREF = 1.0 V Full 2.0 2.0 V p-p
Internal Input Common-Mode Voltage Full 3.5 3.5 V External Input Common-Mode Voltage Full 3.1 3.9 3.1 3.9 V Input Resistance2 Full 1 1 k Input Capacitance2 Full 6 6 pF
POWER SUPPLIES Supply Voltage
AVDD1 Full 3.14 3.3 3.46 3.14 3.3 3.46 V AVDD2 Full 4.75 5.0 5.25 4.75 5.0 5.25 V DRVDDLVDS Outputs Full 3.0 3.6 3.0 3.6 V DRVDDCMOS Outputs Full 3.0 3.3 3.6 3.0 3.3 3.6 V
Supply Current1 AVDD1 Full 335 364 384 424 mA AVDD21, 3 Full 169 196 172 199 mA IDRVDD1LVDS Outputs Full 63 78 63 78 mA IDRVDD1CMOS Outputs Full 14 14 mA
PSRR Offset Full 1 1 mV/V Gain Full 0.2 0.2 %/V
POWER CONSUMPTION LVDS Outputs Full 2.2 2.4 2.3 2.6 W CMOS Outputs (DC Input) Full 2.0 2.1 W
1 Measured at the maximum clock rate, fIN = 15 MHz, full-scale sine wave, with a 100 differential termination on each pair of output bits for LVDS output mode and
approximately 5 pF loading on each output bit for CMOS output mode. 2 Input capacitance or resistance refers to the effective impedance between one differential input pin and AGND. Refer to Figure 6 for the equivalent analog input structure. 3 For RF ENABLE = AVDD1, IAVDD2 increases by ~30 mA, which increases power dissipation.
AD9445
Rev. 0 | Page 4 of 40
AC SPECIFICATIONS AVDD1 = 3.3 V, AVDD2 = 5.0 V, DRVDD = 3.3 V, LVDS mode, specified minimum sample rate, 2.0 V p-p differential input, internal trimmed reference (1.0 V mode), AIN = 1.0 dBFS, DCS on, RF ENABLE = ground, unless otherwise noted.
Table 2. AD9445BSVZ-105 AD9445BSVZ-125
Parameter Temp Min Typ Max Min Typ Max Unit SIGNAL-TO-NOISE RATIO (SNR)
fIN = 10 MHz 25C 74.3 74.1 dB fIN = 30 MHz 25C 73.3 74.3 72.9 73.8 dB Full 73 72.5 dB fIN = 170 MHz 25C 72.9 73.6 72.3 73.2 dB fIN = 225 MHz1 25C 72.2 73 72 72.9 dB Full 72.2 71.4 dB fIN = 300 MHz2 25C 71.4 72.1 71.3 72 dB fIN = 400 MHz2 25C 71 71 dB fIN = 450 MHz2 25C 70.5 70.5 dB fIN = 10 MHz (3.2 V p-p Input) 25C 77.6 77.3 dB fIN = 30 MHz (3.2 V p-p Input) 25C 77.5 77.3 dB fIN = 170 MHz (3.2 V p-p Input) 25C 76 76 dB fIN = 225 MHz (3.2 V p-p Input)1 25C 75.3 75.4 dB fIN = 300 MHz (3.2 V p-p Input)2 25C 73.7 73.5 dB
SIGNAL-TO-NOISE AND DISTORTION (SINAD) fIN = 10 MHz 25C 74.2 73.9 dB fIN = 30 MHz 25C 73.2 74.2 72.8 73.7 dB Full 72.8 72.3 dB fIN = 170 MHz 25C 72.3 73.3 72.4 73.0 dB fIN = 225 MHz1 25C 71.4 72.5 71.9 72.5 dB Full 71.3 70.7 dB fIN = 300 MHz2 25C 70.2 71.7 69.3 71.5 dB fIN = 400 MHz2 25C 67.2 66.3 dB fIN = 450 MHz2 25C 65.2 64.3 dB fIN = 10 MHz (3.2 V p-p Input) 25C 77.4 76.9 dB fIN = 30 MHz (3.2 V p-p Input) 25C 77.3 76.8 dB fIN = 170 MHz (3.2 V p-p Input) 25C 75.7 75.4 dB fIN = 225 MHz (3.2 V p-p Input)1 25C 75.1 75.2 dB fIN = 300 MHz (3.2 V p-p Input)2 25C 72.5 71.8 dB
EFFECTIVE NUMBER OF BITS (ENOB) fIN = 10 MHz 25C 12.2 12.2 Bits fIN = 30 MHz 25C 12.2 12.1 Bits fIN = 170 MHz 25C 12.1 12.0 Bits fIN = 225 MHz1 25C 12.0 12.0 Bits fIN = 300 MHz2 25C 11.8 11.8 Bits fIN = 400 MHz2 25C 11.7 11.7 Bits fIN = 450 MHz2 25C 11.6 11.6 Bits
AD9445
Rev. 0 | Page 5 of 40
AD9445BSVZ-105 AD9445BSVZ-125 Parameter Temp Min Typ Max Min Typ Max Unit SPURIOUS-FREE DYNAMIC RANGE
(SFDR, Second or Third Harmonic)
fIN = 10 MHz 25C 95 95 dBc fIN = 30 MHz 25C 84 92 85 94 dBc Full 83 82 dBc fIN = 170 MHz 25C 82 94 80 91 dBc fIN = 225 MHz1 25C 76 87 83 88 dBc Full 75 75 dBc fIN = 300 MHz2 25C 76 87 75 87 dBc fIN = 400 MHz2 25C 75 73 dBc fIN = 450 MHz2 25C 70 69 dBc fIN = 10 MHz (3.2 V p-p Input) 25C 92 92 dBc fIN = 30 MHz (3.2 V p-p Input) 25C 88 91 dBc fIN = 170 MHz (3.2 V p-p Input) 25C 86 86 dBc fIN = 225 MHz (3.2 V p-p Input)1 25C 81 80 dBc fIN = 300 MHz (3.2 V p-p Input)2 25C 77 76 dBc
WORST SPUR EXCLUDING SECOND OR THIRD HARMONICS
fIN = 10 MHz 25C 97 97 dBc fIN = 30 MHz 25C 99 90 98 89 dBc Full 90 88 dBc fIN = 170 MHz 25C 99 92 93 85 dBc fIN = 225 MHz1 25C 94 88 94 84 dBc Full 86 80 dBc fIN = 300 MHz2 25C 97 90 92 82 dBc fIN = 400 MHz2 25C 93 93 dBc fIN = 450 MHz2 25C 82 87 dBc fIN = 10 MHz (3.2 V p-p Input) 25C 97 95 dBc fIN = 30 MHz (3.2 V p-p Input) 25C 97 95 dBc fIN = 170 MHz (3.2 V p-p Input) 25C 97 95 dBc fIN = 225 MHz (3.2 V p-p Input)1 25C 95 94 dBc fIN = 300 MHz (3.2 V p-p Input)2 25C 93 91 dBc
TWO-TONE SFDR fIN = 30.3 MHz @ 7 dBFS,
31.3 MHz @ 7 dBFS 25C 102 102 dBFS
fIN = 170.3 MHz @ 7 dBFS, 171.3 MHz @ 7 dBFS
25C 92 91 dBFS
ANALOG BANDWIDTH Full 615 615 MHz 1 RF ENABLE = low (AGND ) for AD9445-105; RF ENABLE = high (AVDD1) for AD9445-125. 2 RF ENABLE = high (AVDD1).
AD9445
Rev. 0 | Page 6 of 40
DIGITAL SPECIFICATIONS AVDD1 = 3.3 V, AVDD2 = 5.0 V, DRVDD = 3.3 V, RLVDS_BIAS = 3.74 k, unless otherwise noted.
Table 3. AD9445BSVZ-105 AD9445BSVZ-125 Parameter Temp Min Typ Max Min Typ Max Unit CMOS LOGIC INPUTS (DFS, DCS MODE, OUTPUT MODE)
High Level Input Voltage Full 2.0 2.0 V Low Level Input Voltage Full 0.8 0.8 V High Level Input Current Full 200 200 A Low Level Input Current Full 10 +10 10 +10 A Input Capacitance Full 2 2 pF
DIGITAL OUTPUT BITSCMOS MODE (D0 to D13, OTR)1 DRVDD = 3.3 V
High Level Output Voltage Full 3.25 3.25 V Low Level Output Voltage Full 0.2 0.2 V
DIGITAL OUTPUT BITSLVDS MODE (D0 to D13, OTR) VOD Differential Output Voltage2 Full 247 545 247 545 mV VOS Output Offset Voltage Full 1.125 1.375 1.125 1.375 V
CLOCK INPUTS (CLK+, CLK) Differential Input Voltage Full 0.2 0.2 V Common-Mode Voltage Full 1.3 1.5 1.6 1.3 1.5 1.6 V Differential Input Resistance Full 1.1 1.4 1.7 1.1 1.4 1.7 k Differential Input Capacitance Full 2 2 pF
1 Output voltage levels measured with 5 pF load on each output. 2 LVDS RTERM = 100 .
SWITCHING SPECIFICATIONS AVDD1 = 3.3 V, AVDD2 = 5.0 V, DRVDD = 3.3 V, unless otherwise noted.
Table 4. AD9445BSVZ-105 AD9445BSVZ-125 Parameter Temp Min Typ Max Min Typ Max Unit CLOCK INPUT PARAMETERS
Maximum Conversion Rate Full 105 125 MSPS Minimum Conversion Rate Full 10 10 MSPS CLK Period Full 9.5 8.0 ns CLK Pulse Width High1 (tCLKH) Full 3.8 3.2 ns CLK Pulse Width Low1 (tCLKL) Full 3.8 3.2 ns
DATA OUTPUT PARAMETERS Output Propagation DelayCMOS (tPD)2 (Dx, DCO+) Full 3.35 3.35 ns Output Propagation DelayLVDS (tPD)3 (Dx+), (tCPD)3 (DCO+) Full 2.1 3.6 4.8 2.3 3.6 4.8 ns Pipeline Delay (Latency) Full 13 13 Cycles Aperture Delay (tA) Full ns Aperture Uncertainty (Jitter, tJ) Full 60 60 fsec
rms 1 With duty cycle stabilizer (DCS) enabled. 2 Output propagation delay is measured from clock 50% transition to data 50% transition with 5 pF load. 3 LVDS RTERM = 100 . Measured from the 50% point of the rising edge of CLK+ to the 50% point of the data transition.
AD9445
Rev. 0 | Page 7 of 40
TIMING DIAGRAMS
N 13 N 12 N N + 1
AIN
CLK+
CLK
DATA OUT
DCO+
DCO
N
N + 1
N 1
tCLKHtCLKL
1/fS
tPD
13 CLOCK CYCLES
tCPD
0548
9-00
2
Figure 2. LVDS Mode Timing Diagram
N + 1N + 2
N 1
tCLKL
13 CLOCK CYCLES
0548
9-00
3
N
tCLKH
tPD
VIN
CLK+
CLK
DX
DCO+
DCO
N 13 N 12 N 1 N
Figure 3. CMOS Timing Diagram
AD9445
Rev. 0 | Page 8 of 40
ABSOLUTE MAXIMUM RATINGS
Table 5. Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability.
With Respect To Parameter Rating
ELECTRICAL AVDD1 AGND 0.3 V to +4 V AVDD2 AGND 0.3 V to +6 V DRVDD DGND 0.3 V to +4 V AGND DGND 0.3 V to +0.3 V
THERMAL RESISTANCE AVDD1 DRVDD 4 V to +4 V
The heat sink of the AD9445 package must be soldered to ground. AVDD2 DRVDD 4 V to +6 V AVDD2 AVDD1 4 V to +6 V Table 6. D0 to D13 DGND 0.3 V to DRVDD + 0.3 V Package Type JA JB JC Unit CLK+/CLK AGND 0.3 V to AVDD1 + 0.3 V 100-lead TQFP/EP 19.8 8.3 2 C/W
AGND 0.3 V to AVDD1 + 0.3 V OUTPUT MODE, DCS MODE, DFS, SFDR, RF ENABLE
Typical JA = 19.8C/W (heat sink soldered) for multilayer board in still air. VIN+, VIN AGND 0.3 V to AVDD2 + 0.3 V
VREF AGND 0.3 V to AVDD1 + 0.3 V Typical JB = 8.3C/W (heat sink soldered) for multilayer board in still air. SENSE AGND 0.3 V to AVDD1 + 0.3 V
REFT, REFB AGND 0.3 V to AVDD1 + 0.3 V Typical JC = 2C/W (junction to exposed heat sink) represents the thermal resistance through heat sink path.
ENVIRONMENTAL 65C to +125C Storage Temperature
Range Airflow increases heat dissipation, effectively reducing JA. Also, more metal directly in contact with the package leads from metal traces through holes, ground, and power planes reduces the JA. It is required that the exposed heat sink be soldered to the ground plane.
40C to +85C Operating Temperature Range
300C Lead Temperature (Soldering 10 sec)
Junction Temperature 150C
ESD CAUTION ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on the human body and test equipment and can discharge without detection. Although this product features proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance degradation or loss of functionality.
AD9445
Rev. 0 | Page 9 of 40
TERMINOLOGY Analog Bandwidth (Full Power Bandwidth) Minimum Conversion Rate
The clock rate at which the SNR of the lowest analog signal frequency drops by no more than 3 dB below the guaranteed limit.
The analog input frequency at which the spectral power of the fundamental frequency (as determined by the FFT analysis) is reduced by 3 dB.
Aperture Delay (tA) Offset Error The major carry transition should occur for an analog value of LSB below VIN+ = VIN. Offset error is defined as the deviation of the actual transition from that point.
The delay between the 50% point of the rising edge of the clock and the instant at which the analog input is sampled.
Aperture Uncertainty (Jitter, tJ) Out-of-Range Recovery Time The sample-to-sample variation in aperture delay. The time it takes for the ADC to reacquire the analog input after a transition from 10% above positive full scale to 10% above negative full scale, or from 10% below negative full scale to 10% below positive full scale.
Clock Pulse Width and Duty Cycle Pulse width high is the minimum amount of time that the clock pulse should be left in the Logic 1 state to achieve rated performance. Pulse width low is the minimum time the clock pulse should be left in the low state. At a given clock rate, these specifications define an acceptable clock duty cycle.
Output Propagation Delay (tPD) The delay between the clock rising edge and the time when all bits are within valid logic levels.
Differential Nonlinearity (DNL, No Missing Codes) Power-Supply Rejection Ratio An ideal ADC exhibits code transitions that are exactly 1 LSB
apart. DNL is the deviation from this ideal value. Guaranteed no missing codes to 14-bit resolution indicates that all 16,384 codes must be present over all operating ranges.
The change in full scale from the value with the supply at the minimum limit to the value with the supply at the maximum limit.
Signal-to-Noise and Distortion (SINAD) Effective Number of Bits (ENOB) The ratio of the rms input signal amplitude to the rms value of the sum of all other spectral components below the Nyquist frequency, including harmonics but excluding dc.
The effective number of bits for a sine wave input at a given input frequency can be calculated directly from its measured SINAD using the following formula:
( )6.02
1.76=
SINADENOB Signal-to-Noise Ratio (SNR)
The ratio of the rms input signal amplitude to the rms value of the sum of all other spectral components below the Nyquist frequency, excluding the first six harmonics and dc.
Gain Error The first code transition should occur at an analog value of LSB above negative full scale. The last transition should occur at an analog value of 1 LSB below the positive full scale. Gain error is the deviation of the actual difference between first and last code transitions and the ideal difference between first and last code transitions.
Spurious-Free Dynamic Range (SFDR) The ratio of the rms signal amplitude to the rms value of the peak spurious spectral component. The peak spurious component may be a harmonic. SFDR can be reported in dBc (that is, degrades as signal level is lowered) or dBFS (always related back to converter full scale). Integral Nonlinearity (INL)
The deviation of each individual code from a line drawn from negative full scale through positive full scale. The point used as negative full scale occurs LSB before the first code transition. Positive full scale is defined as a level 1 LSB beyond the last code transition. The deviation is measured from the middle of each particular code to the true straight line.
Temperature Drift The temperature drift for offset error and gain error specifies the maximum change from the initial (25C) value to the value at TMIN or TMAX.
Total Harmonic Distortion (THD) The ratio of the rms input signal amplitude to the rms value of the sum of the first six harmonic components. Maximum Conversion Rate
The clock rate at which parametric testing is performed. Two-Tone SFDR The ratio of the rms value of either input tone to the rms value of the peak spurious component. The peak spurious component may or may not be an IMD product.
AD9445
Rev. 0 | Page 10 of 40
PIN CONFIGURATIONS AND FUNCTION DESCRIPTIONS
74 D8+73 D872 D7+
69 D6
70 D6+
71 D7
75 DRGND
68 DCO+67 DCO66 D5+
64 DRVDD63 DRGND62 D4+61 D460 D3+59 D358 D2+57 D256 D1+55 D154 D0+53 D0 (LSB)52 DNC51 DNC
65 D5
PIN 1
DNC = DO NOT CONNECT
100
RF
ENA
BLE
99
AG
ND
98
AG
ND
97
AVD
D1
96
AVD
D1
95
AVD
D1
94
AVD
D1
93
AVD
D1
92
AVD
D1
91
AG
ND
90
OR
+
89
OR
88
DR
VDD
87
DR
GN
D
86
D13
+ (M
SB)
85
D13
84
D12
+
83
D12
82
D11
+
81
D11
80
D10
+
79
D10
78
D9+
77
D9
76
DR
VDD
26
AVD
D2
27
AVD
D2
28
AVD
D2
29
AVD
D2
30
AVD
D2
31
AVD
D2
32
AVD
D1
33
AVD
D1
34
AVD
D1
35
AVD
D2
36
AVD
D1
37
AVD
D2
38
AVD
D1
39
AG
ND
40
CLK
+
41
CLK
42
AG
ND
43
AVD
D1
44
AVD
D1
45
AVD
D1
46
AG
ND
47
DR
GN
D
48
DR
VDD
49
DN
C
50
DN
C
2DNC3OUTPUT MODE4DFS
7SENSE
6AVDD1
5LVDS_BIAS
1DCS MODE
8VREF9AGND10REFT
12AVDD213AVDD214AVDD215AVDD216AVDD217AVDD218AVDD119AVDD120AVDD121AGND22VIN+23VIN24AGND25AVDD2
11REFB
AD9445LVDS MODE
TOP VIEW(Not to Scale)
0548
9-00
4
Figure 4. 100-Lead TQFP/EP Pin Configuration in LVDS Mode
AD9445
Rev. 0 | Page 11 of 40
Table 7. Pin Function Descriptions100-Lead TQFP/EP in LVDS Mode Pin No. Mnemonic Description 1 DCS MODE Clock Duty Cycle Stabilizer (DCS) Control Pin. CMOS compatible. DCS = low (AGND) to
enable DCS (recommended); DCS = high (AVDD1) to disable DCS. 2, 49 to 52 DNC Do Not Connect. These pins should float. 3 OUTPUT MODE CMOS-Compatible Output Logic Mode Control Pin. OUTPUT MODE = 0 for CMOS mode;
OUTPUT MODE = 1 (AVDD1) for LVDS outputs. 4 DFS Data Format Select Pin. CMOS control pin that determines the format of the output data.
DFS = high (AVDD1) for twos complement; DFS = low (ground) for offset binary format. 5 LVDS_BIAS Set Pin for LVDS Output Current. Place 3.7 k resistor terminated to DRGND. 6, 18 to 20, 32 to 34, 36, 38, 43 to 45, 92 to 97
AVDD1 3.3 V (5%) Analog Supply.
7 SENSE Reference Mode Selection. Connect to AGND for internal 1 V reference; connect to AVDD1 for external reference.
8 VREF 1.0 V Reference I/O. Function dependent on SENSE and external programming resistors. Decouple to ground with 0.1 F and 10 F capacitors.
9, 21, 24, 39, 42, 46, 91, 98, 99, Exposed Heat Sink
AGND Analog Ground. The exposed heat sink on the bottom of the package must be connected to AGND.
10 REFT Differential Reference Output. Decoupled to ground with 0.1 F capacitor and to REFB (Pin 14) with 0.1 F and 10 F capacitors.
11 REFB Differential Reference Output. Decoupled to ground with a 0.1 F capacitor and to REFT (Pin 13) with 0.1 F and 10 F capacitors.
12 to 17, 25 to 31, 35, 37 AVDD2 5.0 V Analog Supply (5%). 22 VIN+ Analog InputTrue. 23 VIN Analog InputComplement. 40 CLK+ Clock InputTrue. 41 CLK Clock InputComplement. 47, 63, 75, 87 DRGND Digital Output Ground. 48, 64, 76, 88 DRVDD 3.3 V Digital Output Supply (3.0 V to 3.6 V). 53 D0 (LSB) D0 Complement Output Bit (LVDS Levels). 54 D0+ D0 True Output Bit. 55 D1 D1 Complement Output Bit. 56 D1+ D1 True Output Bit. 57 D2 D2 Complement Output Bit. 58 D2+ D2 True Output Bit. 59 D3 D3 Complement Output Bit. 60 D3+ D3 True Output Bit. 61 D4 D4 Complement Output Bit. 62 D4+ D4 True Output Bit. 65 D5 D5 Complement Output Bit. 66 D5+ D5 True Output Bit. 67 DCO Data Clock OutputComplement. 68 DCO+ Data Clock OutputTrue. 69 D6 D6 Complement Output Bit. 70 D6+ D6 True Output Bit. 71 D7 D7 Complement Output Bit. 72 D7+ D7 True Output Bit. 73 D8 D8 Complement Output Bit. 74 D8+ D8 True Output Bit. 77 D9 D9 Complement Output Bit. 78 D9+ D9 True Output Bit. 79 D10 D10 Complement Output Bit. 80 D10+ D10 True Output Bit. 81 D11 D11 Complement Output Bit. 82 D11+ D11 True Output Bit.
AD9445
Rev. 0 | Page 12 of 40
Pin No. Mnemonic Description 83 D12 D12 Complement Output Bit. 84 D12+ D12 True Output Bit. 85 D13 D13 Complement Output Bit. 86 D13+ (MSB) D13 True Output Bit. 89 OR Out-of-Range Complement Output Bit. 90 OR+ Out-of-Range True Output Bit. 100 RF ENABLE RF ENABLE Control Pin. CMOS-compatible control pin to optimize the configuration of
the AD9445 analog front end. Connecting RF ENABLE to AGND optimizes SFDR performance for applications with analog input frequencies 230 MHz for the 105 MSPS speed grade, this pin should be connected to AVDD1 for optimum SFDR performance. Power dissipation from AVDD2 increases by 150 mW to 200 mW.
AD9445
Rev. 0 | Page 13 of 40
74 D273 D172 D0 (LSB)
69 DNC
70 DNC
71 DNC
75 DRGND
68 DCO+67 DCO66 DNC
64 DRVDD63 DRGND62 DNC61 DNC60 DNC59 DNC58 DNC57 DNC56 DNC55 DNC54 DNC53 DNC52 DNC51 DNC
65 DNC
PIN 1
DNC = DO NOT CONNECT
100
RF
ENA
BLE
99
AG
ND
98
AG
ND
97
AVD
D1
96
AVD
D1
95
AVD
D1
94
AVD
D1
93
AVD
D1
92
AVD
D1
91
AG
ND
90
OR
89
D13
(MSB
)
88
DR
VDD
87
DR
GN
D
86
D12
85
D11
84
D10
83
D9
82
D8
81
D7
80
D6
79
D5
78
D4
77
D3
76
DR
VDD
26
AVD
D2
27
AVD
D2
28
AVD
D2
29
AVD
D2
30
AVD
D2
31
AVD
D2
32
AVD
D1
33
AVD
D1
34
AVD
D1
35
AVD
D2
36
AVD
D1
37
AVD
D2
38
AVD
D1
39
AG
ND
40
CLK
+
41
CLK
42
AG
ND
43
AVD
D1
44
AVD
D1
45A
VDD
146
AG
ND
47
DR
GN
D
48
DR
VDD
49
DN
C
50
DN
C
2DNC3OUTPUT MODE4DFS
7SENSE
6AVDD1
5LVDS_BIAS
1DCS MODE
8VREF9AGND10REFT
12AVDD213AVDD214AVDD215AVDD216AVDD217AVDD218AVDD119AVDD120AVDD121AGND22VIN+23VIN24AGND25AVDD2
11REFB
AD9445CMOS MODE
TOP VIEW(Not to Scale)
0548
9-00
5
Figure 5. 100-Lead TQFP/EP Pin Configuration in CMOS Mode
AD9445
Rev. 0 | Page 14 of 40
Table 8. Pin Function Descriptions100-Lead TQFP/EP in CMOS Mode Pin No. Mnemonic Description 1 DCS MODE Clock Duty Cycle Stabilizer (DCS) Control Pin. CMOS compatible. DCS = low (AGND) to enable
DCS (recommended); DCS = high (AVDD1) to disable DCS. 2, 49 to 62, 65 to 66, 69 to 71 DNC Do Not Connect. These pins should float. 3 OUTPUT
MODE CMOS-Compatible Output Logic Mode Control Pin. OUTPUT MODE = 0 for CMOS mode; OUTPUT MODE = 1 (AVDD1) for LVDS outputs.
4 DFS Data Format Select Pin. CMOS control pin that determines the format of the output data. DFS = high (AVDD1) for twos complement; DFS = low (ground) for offset binary format.
5 LVDS_BIAS Set Pin for LVDS Output Current. Place 3.7 k resistor terminated to DRGND. 6, 18 to 20, 32 to 34, 36, 38, 43 to 45, 92 to 97
AVDD1 3.3 V (5%) Analog Supply.
7 SENSE Reference Mode Selection. Connect to AGND for internal 1 V reference; connect to AVDD1 for external reference.
8 VREF 1.0 V Reference I/O. Function dependent on SENSE and external programming resistors. Decouple to ground with 0.1 F and 10 F capacitors.
9, 21, 24, 39, 42, 46, 91, 98, 99, Exposed Heat Sink
AGND Analog Ground. The exposed heat sink on the bottom of the package must be connected to AGND.
10 REFT Differential Reference Output. Decoupled to ground with 0.1 F capacitor and to REFB (Pin 14) with 0.1 F and 10 F capacitors.
11 REFB Differential Reference Output. Decoupled to ground with a 0.1 F capacitor and to REFT (Pin 13) with 0.1 F and 10 F capacitors.
12 to 17, 25 to 31, 35, 37 AVDD2 5.0 V Analog Supply (5%). 22 VIN+ Analog InputTrue. 23 VIN Analog InputComplement. 40 CLK+ Clock InputTrue. 41 CLK Clock InputComplement. 47, 63, 75, 87 DRGND Digital Output Ground. 48, 64, 76, 88 DRVDD 3.3 V Digital Output Supply (3.0 V to 3.6 V). 67 DCO Data Clock OutputComplement. 68 DCO+ Data Clock OutputTrue. 72 D0 (LSB) D0 True Output Bit (CMOS levels). 73 D1 D1 True Output Bit. 74 D2 D2 True Output Bit. 77 D3 D3 True Output Bit. 78 D4 D4 True Output Bit. 79 D5 D5 True Output Bit. 80 D6 D6 True Output Bit. 81 D7 D7 True Output Bit. 82 D8 D8 True Output Bit. 83 D9 D9 True Output Bit. 84 D10 D10 True Output Bit. 85 D11 D11 True Output Bit. 86 D12 D12 True Output Bit. 89 D13 (MSB) D13 True Output Bit. 90 OR Out-of-Range True Output Bit. 100 RF ENABLE RF ENABLE CMOS-compatible Control Pin. Optimizes the configuration of the analog front end.
Connecting RF ENABLE to AGND optimizes SFDR performance for applications with analog input frequencies 230 MHz for the 105 MSPS speed grade, this pin should be connected to AVDD1 for optimum SFDR. Power dissipation from AVDD2 increases by 150 mW to 200 mW.
AD9445
Rev. 0 | Page 15 of 40
EQUIVALENT CIRCUITS
X13.5V
1k
1k
AVDD2
VIN+
VIN
T/H
AVDD2
0548
9-00
66pF
6pF
DX
DRVDD
0548
9-00
9
Figure 6. Equivalent Analog Input Circuit Figure 9. Equivalent CMOS Digital Output Circuit
RF ENABLE, DCSMODE, OUTPUT
MODE, DFS
VDD
30k
0548
9-01
0
0548
9-00
7
1.2V
DRVDD DRVDD
K
3.74k ILVDSOUTLVDS_BIAS
Figure 10. Equivalent Digital Input Circuit,
DFS, DCS MODE, OUTPUT MODE Figure 7. Equivalent LVDS_BIAS Circuit
CLK+
3k
2.5k
3k
2.5k
AVDD2
CLK
0548
9-01
1
DRVDD
DX DX+
V
V
V
V
0548
9-00
8
Figure 11. Equivalent Sample Clock Input Circuit Figure 8. Equivalent LVDS Digital Output Circuit
AD9445
Rev. 0 | Page 16 of 40
TYPICAL PERFORMANCE CHARACTERISTICS AVDD1 = 3.3 V, AVDD2 = 5.0 V, DRVDD = 3.3 V, rated sample rate, LVDS mode, DCS enabled, TA = 25C, 2.0 V p-p differential input, AIN = 1.0 dBFS, internal trimmed reference (nominal VREF = 1.0 V), unless otherwise noted.
0
1300 62.500
0548
9-01
2
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
125MSPS30.3MHz @ 1.0dBFSSNR = 73.4dBENOB = 12.1BITSSFDR = 94dBc
10
20
30
40
50
60
70
80
90
100
110
120
15.625 31.250 46.875
0
1300 62.500
0548
9-01
5
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
125MSPS225.3MHz @ 1.0dBFSSNR = 72.9dBENOB = 12.1BITSSFDR = 88dBc
10
20
30
40
50
60
70
80
90
100
110
120
15.625 31.250 46.875
Figure 12. AD9445-125 64k Point Single-Tone FFT/125 MSPS/30.3 MHz Figure 15. AD9445-125 64k Point Single-Tone FFT/125 MSPS/225.3 MHz
0
1300 62.500
0548
9-01
3
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
125MSPS100.3MHz @ 1.0dBFSSNR = 0dBENOB = 12.1BITSSFDR = 96dBc
10
20
30
40
50
60
70
80
90
100
110
120
15.625 31.250 46.875
0
1300 62.500
0548
9-01
6
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
125MSPS300.3MHz @ 1.0dBFSSNR = 72.0dBENOB = 11.8BITSSFDR = 87dBc
10
20
30
40
50
60
70
80
90
100
110
120
15.625 31.250 46.875
Figure 13. AD9445-125 64k Point Single-Tone FFT/125 MSPS/100.3 MHz Figure 16. AD9445-125 64k Point Single-Tone FFT/125 MSPS/300.3 MHz
0
1300 62.500
0548
9-01
4
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
125MSPS170.3MHz @ 1.0dBFSSNR = 73.2dBENOB = 12.0BITSSFDR = 91dBc
10
20
30
40
50
60
70
80
90
100
110
120
15.625 31.250 46.875
0
1300 62.500
0548
9-01
7
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
125MSPS450.3MHz @ 1.0dBFSSNR = 70.5dBENOB = 11.6BITSSFDR = 69dBc
10
20
30
40
50
60
70
80
90
100
110
120
15.625 31.250 46.875
Figure 14. AD9445-125 64k Point Single-Tone FFT/125 MSPS/170.3 MHz Figure 17. AD9445-125 64k Point Single-Tone FFT/125 MSPS/450.3 MHz
AD9445
Rev. 0 | Page 17 of 40
100
95
90
85
80
75
70
65
60
550 50 100 150 200 250 300 350 400 450
0548
9-01
8
ANALOG INPUT FREQUENCY (MHz)
(dB
)
SFDR +25C
SNR +25C
SFDR +85C
SFDR 40C
SNR +85C
SNR 40C
100
95
90
85
80
75
70
65
60
550 50 100 150 200 250 300 350 400 450
0548
9-02
1
ANALOG INPUT FREQUENCY (MHz)
(dB
)
SFDR +25C
SNR +25C
SFDR +85CSFDR 40C
SNR +85C
SNR 40C
Figure 18. AD9445-125 SNR/SFDR vs. Analog Input Frequency,
125 MSPS, 2.0 V p-p Input Range Figure 21. AD9445-125 SNR/SFDR vs. Analog Input Frequency,
125 MSPS, 3.2 V p-p Input Range
100
550 100
0548
9-01
9
ANALOG INPUT FREQUENCY (MHz)
(dB
)
SFDR +25C
SNR +25C
SFDR +85C
SFDR 40C
SNR +85C
SNR 40C
20 30 40 50 60 70 80 90
95
90
85
80
75
70
65
60
10
105
700
0548
9-02
2
SAMPLE RATE (MSPS)
(dB
)
100
95
90
85
80
75
20 40 60 80 100 120 140
105M SFDR dBc
125M SFDR dBc
105M SNR dB
125M SNR dB
Figure 19. AD9445-125 SNR/SFDR vs. Analog Input Frequency,
3.2 V p-p Input Range, 125 MSPS, CMOS Output Mode Figure 22. AD9445 Single-Tone SNR/SFDR vs. Sample Rate 2.3 MHz
120
0100 0
0548
9-02
0
ANALOG INPUT AMPLITUDE (dB)
(dB
)
100
80
60
40
20
90 80 70 60 50 40 30 20 10
SNR dB
SNR dBFS
SFDR dBc
SFDR dBFS120
0100 0
0548
9-02
3
ANALOG INPUT AMPLITUDE (dB)
(dB
)
100
80
60
40
20
90 80 70 60 50 40 30 20 10
SNR dB
SNR dBFS
SFDR dBc
SFDR dBFS
Figure 20. AD9445-125 SNR/SFDR vs. Analog Input Level,
125 MSPS/225.3 MHz Figure 23. AD9445-125 SNR/SFDR vs. Analog Input Level,
125 MSPS/225.3 MHz, CMOS Output Mode
AD9445
Rev. 0 | Page 18 of 40
0
1300 52.500
0548
9-02
4
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
105MSPS30.3MHz @ 1.0dBFSSNR = 74.3dBENOB = 12.2BITSSFDR = 92dBc
10
20
30
40
50
60
70
80
90
100
110
120
13.125 26.250 39.375
0
1300 52.500
0548
9-02
7
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
105MSPS225.3MHz @ 1.0dBFSSNR = 73.0dBENOB = 12.0BITSSFDR = 87dBc
10
20
30
40
50
60
70
80
90
100
110
120
13.125 26.250 39.375
Figure 24. AD9445-105 64k Point Single-Tone FFT/105 MSPS/30.3 MHz Figure 27. AD9445-105 64k Point Single-Tone FFT/105 MSPS/225.3 MHz
0
1300 52.500
0548
9-02
5
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
105MSPS100.3MHz @ 1.0dBFSSNR = 73.5dBENOB = 11.8BITSSFDR = 93dBc
10
20
30
40
50
60
70
80
90
100
110
120
13.125 26.250 39.375
0
1300 52.500
0548
9-02
8
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
105MSPS300.3MHz @ 1.0dBFSSNR = 72.1dBENOB = 11.8BITSSFDR = 87dBc
10
20
30
40
50
60
70
80
90
100
110
120
13.125 26.250 39.375
Figure 25. AD9445-105 64k Point Single-Tone FFT/105 MSPS/100.3 MHz Figure 28. AD9445-105 64k Point Single-Tone FFT/105 MSPS/300.3 MHz
0
1300 52.500
0548
9-02
6
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
105MSPS170.3MHz @ 1.0dBFSSNR = 73.6dBENOB = 12.1BITSSFDR = 94dBc
10
20
30
40
50
60
70
80
90
100
110
120
13.125 26.250 39.375
0
1300 52.500
0548
9-02
9
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
105MSPS450.3MHz @ 1.0dBFSSNR = 70.5dBENOB = 11.6BITSSFDR = 70dBc
10
20
30
40
50
60
70
80
90
100
110
120
13.125 26.250 39.375
Figure 26. AD9445-105 64k Point Single-Tone FFT/105 MSPS/170.3 MHz Figure 29. AD9445-105 64k Point Single-Tone FFT/105 MSPS/450.3 MHz
AD9445
Rev. 0 | Page 19 of 40
100
95
90
85
80
75
70
65
60
550 50 100 150 200 250 300 350 400 450
0548
9-03
0
ANALOG INPUT FREQUENCY (MHz)
(dB
)
SFDR +25C
SNR +25C
SFDR +85C
SFDR 40C
SNR +85C
SNR 40C
100
95
90
85
80
75
70
65
60
550 50 100 150 200 250 300 350 400 450
0548
9-03
3
ANALOG INPUT FREQUENCY (MHz)
(dB
)
SFDR +25C
SNR +25C
SFDR +85CSFDR 40C
SNR +85C
SNR 40C
Figure 30. AD9445-105 SNR/SFDR vs. Analog Input Frequency,
105 MSPS, 2.0 V p-p Figure 33. AD9445-105 SNR/SFDR vs. Analog Input Frequency,
105 MSPS, 3.2 V p-p
100
602.7 2.9 3.1 3.3 3.5 3.7 3.9 4.1 4.3
0548
9-03
4
ANALOG INPUT COMMON-MODE VOLTAGE
(dB
)
SNR dB
SFDR dBc95
90
85
80
75
70
65
100
95
90
85
80
75
70
65
60
550 180
0548
9-03
1
ANALOG INPUT FREQUENCY (MHz)
(dB
)
SFDR +25C
SNR +25C
SFDR +85C
SFDR 40C
SNR +85C
SNR 40C
20 40 60 80 100 120 140 160
Figure 31. AD9445-105 SNR/SFDR vs. Analog Input Frequency,
3.2 V p-p Input Range, 105 MSPS, CMOS Output Mode Figure 34. AD9445-105 SNR/SFDR vs. Analog Input Common Mode,
105 MSPS/10.3 MHz
120
0100 0
0548
9-03
2
ANALOG INPUT AMPLITUDE (dB)
(dB
)
100
80
60
40
20
90 80 70 60 50 40 30 20 10
SNR dB
SNR dBFS
SFDR dBc
SFDR dBFS120
0100 0
0548
9-03
5
ANALOG INPUT AMPLITUDE (dB)
(dB
)
100
80
60
40
20
90 80 70 60 50 40 30 20 10
SNR dB
SNR dBFS
SFDR dBc
SFDR dBFS
Figure 32. AD9445-105 SNR/SFDR vs. Analog Input Level,
105 MSPS/225.3 MHz Figure 35. AD9445-105 SNR/SFDR vs. Analog Input Level,
105 MSPS/225.3 MHz, CMOS Output Mode
AD9445
Rev. 0 | Page 20 of 40
0
140
130
0 54.500
0548
9-03
7
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
125MSPS30.3MHz @ 7.0dBFS31.3MHz @ 7.0dBFSSFDR = 102dBFS
1020304050607080
90100110
120
13.625 27.250 40.875
0
120100 0
0548
9-04
1
FUNDAMENTAL LEVEL (dB)
SPU
R A
ND
IMD
3 (d
B)
20
40
60
80
100
10
30
50
70
90
110
90 80 70 60 50 40 30 20 10
SFDR dBFS
SFDR dBc
WORST IMD3 dBc
WORST IMD3 dBFS
Figure 36. AD9445-125 64k Point Two-Tone FFT/
125 MSPS/30.3 MHz, 31.3 MHz Figure 39. AD9445-125 Two-Tone SFDR vs. Analog Input Level
125 MSPS/170.3 MHz, 171.3 MHz
0
120100 0
0548
9-03
8
FUNDAMENTAL LEVEL (dB)
SPU
R A
ND
IMD
3 (d
B)
20
40
60
80
100
10
30
50
70
90
110
90 80 70 60 50 40 30 20 10
SFDR dBFS
SFDR dBc
WORST IMD3 dBc
WORST IMD3 dBFS
0
140
130
0
0548
9-04
2
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
105MSPS30.3MHz @ 7.0dBFS31.3MHz @ 7.0dBFSSFDR = 102dBFS
1020304050607080
90100110
120
0 52.50013.125 26.250 39.375
Figure 37. AD9445-125 Two-Tone SFDR vs. Analog Input Level
125 MSPS/30.3 MHz, 31.3 MHz Figure 40. AD9445-105 64k Point Two-Tone FFT/105 MSPS/30.3 MHz, 31.3 MHz
0
140
130
0 54.500
0548
9-04
0
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
125MSPS170.3MHz @ 7.0dBFS171.3MHz @ 7.0dBFSSFDR = 91dBFS
1020304050607080
90100110
120
13.625 27.250 40.875
0
120100 0
0548
9-04
3
FUNDAMENTAL LEVEL (dB)
SPU
R A
ND
IMD
3 (d
B)
20
40
60
80
100
10
30
50
70
90
110
90 80 70 60 50 40 30 20 10
SFDR dBFS
SFDR dBc
WORST IMD3 dBc
WORST IMD3 dBFS
Figure 38. AD9445-125 64k Point Two-Tone FFT/
125 MSPS/170.3 MHz, 171.3 MHz Figure 41. AD9445-105 Two-Tone SFDR vs. Analog Input Level
105 MSPS/30.3 MHz, 31.3 MHz
AD9445
Rev. 0 | Page 21 of 40
25000
0 0548
9-04
4
OUTPUT CODE
FREQ
UEN
CY
N + 4
621127
7968
2219023754
135575 2
20000
15000
10000
5000
N 4 N 3 N 2 N 1 N N + 1 N + 2 N + 3
9003
30000
0 0548
9-04
7
OUTPUT CODE
FREQ
UEN
CY
N + 4
3 307
3350
15743
26294
3493
227 2N 4 N 3 N 2 N 1 N N + 1 N + 2 N + 3
16117
25000
20000
15000
10000
5000
SAMPLE SIZE = 65538
Figure 42. AD9445-125 Grounded Input Histogram Figure 45. AD9445-105 Grounded Input Histogram
0
140
130
0
0548
9-04
5
FREQUENCY (MHz)
AM
PLIT
UD
E (d
BFS
)
105MSPS170.3MHz @ 7.0dBFS171.3MHz @ 7.0dBFSSFDR = 92dBFS
1020304050607080
90100110
120
0 52.50013.125 26.250 39.375
0
0.840
0548
9-04
8
TEMPERATURE (C)
GA
IN E
RR
OR
(%FS
R)
0.1
0.2
0.3
0.4
0.5
0.6
0.7
20 0 20 40 60 80
Figure 43. AD9445-105 64k Point Two-Tone FFT/105 MSPS/170.3 MHz, 171.3 MHz Figure 46. AD9445-125 Gain vs. Temperature
0.4
0.40
0548
9-04
9
OUTPUT CODE
DN
L ER
RO
R (L
SB)
0 16384
0.3
0.2
0.1
0
0.1
0.2
0.3
4096 8192 12288
0
120100 0
0548
9-04
6
FUNDAMENTAL LEVEL (dB)
SPU
R A
ND
IMD
3 (d
B)
20
40
60
80
100
10
30
50
70
90
110
90 80 70 60 50 40 30 20 10
SFDR dBFS
SFDR dBc
WORST IMD3 dBc
WORST IMD3 dBFS
Figure 44. AD9445-105 Two-Tone SFDR vs. Analog Input Level
105 MSPS/170.3 MHz, 171.3 MHz Figure 47. AD9445-105 DNL Error vs. Output Code, 105 MSPS, 10.3 MHz
AD9445
Rev. 0 | Page 22 of 40
0.4
0.40
0548
9-05
0
OUTPUT CODE
DN
L ER
RO
R (L
SB)
0 16384
0.3
0.2
0.1
0
0.1
0.2
0.3
4096 8192 12288
1.0
1.00
0548
9-05
3
OUTPUT CODE
INL
ERR
OR
(LSB
)
0 163844096 8192 12288
0.8
0.6
0.4
0.2
0
0.2
0.4
0.6
0.8
Figure 48. AD9445-125 DNL Error vs. Output Code, 125 MSPS, 10.3 MHz Figure 51. AD9445-125 INL Error vs. Output Code, 125 MSPS, 10.3 MHz
400
00
0548
9-06
6
SAMPLE RATE (MSPS)
I SU
PPLY
(mA
)
160
350
300
250
200
150
100
50
20 40 60 80 100 120 140
DRVDD
AVDD2
AVDD1
1.014
1.012
1.010
1.008
1.006
1.004
1.00240
0548
9-05
1
TEMPERATURE (C)
VREF
20 0 20 40 60 80
Figure 52. AD9445-105 Power Supply Current vs. Sample Rate
10.3 MHz @ 1 dBFS Figure 49. AD9445-125 VREF vs. Temperature
78
711.8
0548
9-06
7
ANALOG INPUT RANGE (V p-p)
(dB
)
4.2
170.3MHz SNR dB
225.3MHz SNR dB
300.3MHz SNR dB
77
76
75
74
73
72
2.0 2.2 2.4 2.6 2.8 3.0 3.2 3.4 3.6 3.8 4.0
0.5
0.50
0548
9-05
2
OUTPUT CODE
INL
ERR
OR
(LSB
)
0 163844096 8192 12288
0.4
0.3
0.2
0.1
0
0.1
0.2
0.3
0.4
Figure 53. AD9445-125 SNR vs. Analog Input Range, 125 MSPS/170.3 MHz, 225.3 MHz, 300.3 MHz
Figure 50. AD9445-105 INL Error vs. Output Code, 105 MSPS, 10.3 MHz
AD9445
Rev. 0 | Page 23 of 40
78
711.8
0548
9-06
8
ANALOG INPUT RANGE (V p-p)
(dB
)
4.22.0 2.2 2.4 2.6 2.8 3.0 3.2 3.4 3.6 3.8 4.0
170.3MHz SFDR dBc
225.3MHz SFDR dBc
300.3MHz SFDR dBc
77
75
76
74
73
72
95
701.8
0548
9-07
1
ANALOG INPUT RANGE (V p-p)
(dB
)
4.22.0 2.2 2.4 2.6 2.8 3.0 3.2 3.4 3.6 3.8 4.0
170.3MHz SFDR dBc
225.3MHz SFDR dBc
300.3MHz SFDR dBc
90
85
80
75
Figure 54. AD9445-105 SNR vs. Analog Input Range, 105 MSPS/170.3 MHz, 225.3 MHz, 300.3 MHz
Figure 57. AD9445-105 SFDR vs. Analog Input Range, 105 MSPS/170.3 MHz, 225.3 MHz, 300.3 MHz
400
00
0548
9-06
9
SAMPLE RATE (MSPS)
I SU
PPLY
(mA
)
160
350
300
250
200
150
100
50
20 40 60 80 100 120 140
DRVDD
AVDD2
AVDD1
81
741.8 4.2
0548
9-03
9
ANALOG INPUT RANGE (V p-p)
(dB
)
80
79
78
77
76
75
2.0 2.2 2.4 2.6 2.8 3.0 3.2 3.4 3.6 3.8 4.0
105M SNR dBFS
125M SNR dBFS
Figure 55. AD9445-125 Power Supply Current vs. Sample Rate
10.3 MHz @ 1 dBFS Figure 58. SNR vs. Analog Input Range, 2.3 MHz @ 30 dBFS
95
701.8
0548
9-07
0
ANALOG INPUT RANGE (V p-p)
(dB
)
4.22.0 2.2 2.4 2.6 2.8 3.0 3.2 3.4 3.6 3.8 4.0
170.3MHz SFDR dBc
225.3MHz SFDR dBc
300.3MHz SFDR dBc
90
85
80
75
Figure 56. AD9445-125 SFDR vs. Analog Input Range, 125 MSPS/170.3 MHz, 225.3 MHz, 300.3 MHz
AD9445
Rev. 0 | Page 24 of 40
THEORY OF OPERATION The AD9445 architecture is optimized for high speed and ease of use. The analog inputs drive an integrated, high bandwidth track-and-hold circuit that samples the signal prior to quantization by the 14-bit pipeline ADC core. The device includes an on-board reference and input logic that accepts TTL, CMOS, or LVPECL levels. The digital output logic levels are user selectable as standard 3 V CMOS or LVDS (ANSI-644 compatible) via the OUTPUT MODE pin.
ANALOG INPUT AND REFERENCE OVERVIEW A stable and accurate 0.5 V band gap voltage reference is built into the AD9445. The input range can be adjusted by varying the reference voltage applied to the AD9445, using either the internal reference or an externally applied reference voltage. The input span of the ADC tracks reference voltage changes linearly.
Internal Reference Connection
A comparator within the AD9445 detects the potential at the SENSE pin and configures the reference into three possible states, which are summarized in Table 9. If SENSE is grounded, the reference amplifier switch is connected to the internal resistor divider (see Figure 59), setting VREF to ~1.0 V. Connecting the SENSE pin to VREF switches the reference amplifier output to the SENSE pin, completing the loop and providing a ~1.0 V reference output. If a resistor divider is connected as shown in Figure 60, the switch again sets to the SENSE pin. This puts the reference amplifier in a noninverting mode with the VREF output defined as
+=
R1R2VVREF 15.0
In all reference configurations, REFT and REFB drive the analog-to-digital conversion core and establish its input span. The input range of the ADC always equals twice the voltage at the reference pin for either an internal or an external reference.
Internal Reference Trim
The internal reference voltage is trimmed during the production test to adjust the gain (analog input voltage range) of the AD9445. Therefore, there is little advantage to the user supplying an external voltage reference to the AD9445. The gain trim is performed with the AD9445 input range set to 2.0 V p-p nominal (SENSE
connected to AGND). Because of this trim and the maximum ac performance provided by the 2.0 V p-p analog input range, there is little benefit to using analog input ranges
AD9445
Rev. 0 | Page 25 of 40
3.5V
VIN+
VIN
1V p-p
DIGITAL OUT = ALL 1s DIGITAL OUT = ALL 0s
0548
9-05
6
External Reference Operation
The AD9445s internal reference is trimmed to enhance the gain accuracy of the ADC. An external reference may be more stable over temperature, but the gain of the ADC is not likely to improve. Figure 49 shows the typical drift characteristics of the internal reference in both 1 V and 0.5 V modes.
When the SENSE pin is tied to AVDD, the internal reference is disabled, allowing the use of an external reference. An internal reference buffer loads the external reference with an equivalent 7 k load. The internal buffer still generates the positive and negative full-scale references, REFT and REFB, for the ADC core. The input span is always twice the value of the reference voltage; therefore, the external reference must be limited to a maximum of 1.6 V.
Figure 61. Differential Analog Input Range for VREF = 1.0 V
Therefore, the analog source driving the AD9445 should be ac-coupled to the input pins. The recommended method for driving the analog input of the AD9445 is to use an RF transformer to convert single-ended signals to differential (see
Analog Inputs
As with most new high speed, high dynamic range ADCs, the analog input to the AD9445 is differential. Differential inputs improve on-chip performance because signals are processed through attenuation and gain stages. Most of the improvement is a result of differential analog stages having high rejection of even-order harmonics. There are also benefits at the PCB level. First, differential inputs have high common-mode rejection of stray signals, such as ground and power noise. Second, they provide good rejection of common-mode signals, such as local oscillator feedthrough. The specified noise and distortion of the AD9445 cannot be realized with a single-ended analog input, so such configurations are discouraged. Contact sales for recommendations of other 14-bit ADCs that support single-ended analog input configurations.
Figure 62). Series resistors between the output of the transformer and the AD9445 analog inputs help isolate the analog input source from switching transients caused by the internal sample-and-hold circuit. The series resistors, along with the 1 k resisters connected to the internal 3.5 V bias, must be considered in impedance matching the transformer input. For example, if RT is set to 51 , RS is set to 33 , and there is a 1:1 impedance ratio trans-former, the input will match a 50 source with a full-scale drive of 10.0 dBm. The 50 impedance matching can also be incor-porated on the secondary side of the transformer, as shown in the evaluation board schematic (see Figure 67).
0548
9-05
70.1F
RT AD9445VIN+
VINRS
RSADT11WTANALOGINPUT
SIGNAL
With the 1 V reference, which is the nominal value (see the Internal Reference Trim section), the differential input range of the AD9445 analog input is nominally 2.0 V p-p or 1.0 V p-p on each input (VIN+ or VIN).
Figure 62. Transformer-Coupled Analog Input Circuit
High IF Applications The AD9445 analog input voltage range is offset from ground by 3.5 V. Each analog input connects through a 1 k resistor to the 3.5 V bias voltage and to the input of a differential buffer. The internal bias network on the input properly biases the buffer for maximum linearity and range (see the
In applications where the analog input frequency range is >100 MHz, the phase and amplitude matching at the analog inputs becomes critical to optimize performance of the ADC. The circuit in Figure 63 can be used to optimize the matching of these parameters. This configuration uses a double balun config-uration that has low parasitics, high bandwidth, and parasitic cancellation.
Equivalent Circuits section).
0548
9-05
8
0.1FCT AD9445
VIN+
VIN
3325
50SOURCE
2533
ETC1113ETC1113
0.1F
Figure 63. Double Balun-Coupled Analog Input Circuit
AD9445
Rev. 0 | Page 26 of 40
CLOCK INPUT CONSIDERATIONS Any high speed ADC is extremely sensitive to the quality of the sampling clock provided by the user. A track-and-hold circuit is essentially a mixer, and any noise, distortion, or timing jitter on the clock is combined with the desired signal at the analog-to-digital output. For that reason, considerable care was taken in the design of the clock inputs of the AD9445, and the user is advised to give careful thought to the clock source.
Typical high speed ADCs use both clock edges to generate a variety of internal timing signals and, as a result, may be sensitive to the clock duty cycle. Commonly a 5% tolerance is required on the clock duty cycle to maintain dynamic performance characteristics. The AD9445 contains a clock duty cycle stabilizer (DCS) that retimes the nonsampling edge, providing an internal clock signal with a nominal 50% duty cycle. Noise and distortion performance are nearly flat for a 30% to 70% duty cycle with the DCS enabled. The DCS circuit locks to the rising edge of CLK+ and optimizes timing internally. This allows for a wide range of input duty cycles at the input without degrading performance. Jitter in the rising edge of the input is still of paramount concern and is not reduced by the internal stabilization circuit. The duty cycle control loop does not function for clock rates of less than 30 MHz nominally. The loop is associated with a time constant that should be considered in applications where the clock rate can change dynamically, requiring a wait time of 1.5 s to 5 s after a dynamic clock frequency increase or decrease before the DCS loop is relocked to the input signal. During the time that the loop is not locked, the DCS loop is bypassed, and the internal device timing is dependent on the duty cycle of the input clock signal. In such an application, it may be appropriate to disable the duty cycle stabilizer. In all other applications, enabling the DCS circuit is recommended to maximize ac performance.
The DCS circuit is controlled by the DCS MODE pin; a CMOS logic low (AGND) on DCS MODE enables the duty cycle stabilizer, and logic high (AVDD1 = 3.3 V) disables the controller.
The AD9445 input sample clock signal must be a high quality, extremely low phase noise source to prevent degradation of performance. Maintaining 14-bit accuracy places a premium on the encode clock phase noise. SNR performance can easily degrade by 3 dB to 4 dB with 70 MHz analog input signals when using a high jitter clock source. (See the AN-501 Application Note, Aperture Uncertainty and ADC System Performance.) For optimum performance, the AD9445 must be clocked differentially. The sample clock inputs are internally biased to ~2.2 V, and the input signal is usually ac-coupled into the CLK+ and CLK pins via a transformer or capacitors. Figure 64 shows one preferred method for clocking the AD9445. The clock source (low jitter) is converted from single-ended to differential using an RF transformer. The back-to-back
Schottky diodes across the secondary of the transformer limit clock excursions into the AD9445 to approximately 0.8 V p-p differential. This helps prevent the large voltage swings of the clock from feeding through to other portions of the AD9445 and limits the noise presented to the sample clock inputs.
If a low jitter clock is available, it may help to band-pass filter the clock reference before driving the ADC clock inputs. Another option is to ac couple a differential ECL/PECL signal to the encode input pins, as shown in Figure 65.
0548
9-05
9
0.1F AD9445CLK+
CLKHSMS2812
DIODES
CLOCKSOURCE
ADT11WT
Figure 64. Crystal Clock Oscillator, Differential Encode
0548
9-06
0
0.1F
AD9445ENCODE
ENCODE
0.1F
VT
VT
ECL/PECL
Figure 65. Differential ECL for Encode
Jitter Considerations
High speed, high resolution ADCs are sensitive to the quality of the clock input. The degradation in SNR at a given input frequency (fINPUT) and rms amplitude due only to aperture jitter (tJ) can be calculated using the following equation:
SNR = 20 log[2fINPUT tJ]
In the equation, the rms aperture jitter represents the root-mean-square of all jitter sources, which includes the clock input, analog input signal, and ADC aperture jitter specification. IF undersampling applications are particularly sensitive to jitter, see Figure 66.
The clock input should be treated as an analog signal in cases where aperture jitter may affect the dynamic range of the AD9445. Power supplies for clock drivers should be separated from the ADC output driver supplies to avoid modulating the clock signal with digital noise. Low jitter crystal-controlled oscillators make the best clock sources. If the clock is generated from another type of source (by gating, dividing, or another method), it should be synchronized by the original clock during the last step.
http://www.analog.com/UploadedFiles/Application_Notes/3956522730668848977365163734AN501.pdf#xml=http://search.analog.com/search/pdfPainter.aspx?url=http://www.analog.com/UploadedFiles/Application_Notes/3956522730668848977365163734AN501.pdf&fterm=an-501&fterm=an-501&la=enhttp://www.analog.com/UploadedFiles/Application_Notes/3956522730668848977365163734AN501.pdf#xml=http://search.analog.com/search/pdfPainter.aspx?url=http://www.analog.com/UploadedFiles/Application_Notes/3956522730668848977365163734AN501.pdf&fterm=an-501&fterm=an-501&la=en
AD9445
Rev. 0 | Page 27 of 40
INPUT FREQUENCY (MHz)
SNR
(dB
c)
140
75
70
65
60
55
50
45
100010010
0548
9-06
1
0.2ps
0.5ps
1.0ps
1.5ps
2.0ps2.5ps3.0ps
resistor is placed at Pin 5 (LVDS_BIAS) to ground. Dynamic performance, including both SFDR and SNR, is maximized when the AD9445 is used in LVDS mode; designers are encouraged to take advantage of this mode. The AD9445 outputs include complimentary LVDS outputs for each data bit (Dx+/Dx), the overrange output (OR+/OR), and the output data clock output (DCO+/DCO). The RSET resistor current is multiplied on-chip, setting the output current at each output equal to a nominal 3.5 mA (11 IRSET). A 100 differential termination resistor placed at the LVDS receiver inputs results in a nominal 350 mV swing at the receiver. LVDS mode facilitates interfacing with LVDS receivers in custom ASICs and FPGAs that have LVDS capability for superior switching performance in noisy environments. Single point-to-point net topologies are recommended, with a 100 termination resistor placed as close to the receiver as possible. It is recommended to keep the trace length less than 2 inches and to keep differential output trace lengths as equal as possible.
Figure 66. SNR vs. Input Frequency and Jitter
POWER CONSIDERATIONS Care should be taken when selecting a power source. The use of linear dc supplies is highly recommended. Switching supplies tend to have radiated components that may be received by the AD9445. Each of the power supply pins should be decoupled as closely to the package as possible using 0.1 F chip capacitors.
CMOS Mode
In applications that can tolerate a slight degradation in dynamic performance, the AD9445 output drivers can be configured to interface with 2.5 V or 3.3 V logic families by matching DRVDD to the digital supply of the interfaced logic. CMOS outputs are available when OUTPUT MODE is CMOS logic low (or AGND for convenience). In this mode, the output data bits, Dx, are single-ended CMOS, as is the overrange output, OR. The output clock is provided as a differential CMOS signal, DCO+/DCO. Lower supply voltages are recommended to avoid coupling switching transients back to the sensitive analog sections of the ADC. The capacitive load to the CMOS outputs should be minimized, and each output should be connected to a single gate through a series resistor (220 ) to minimize switching transients caused by the capacitive loading.
The AD9445 has separate digital and analog power supply pins. The analog supplies are denoted AVDD1 (3.3 V) and AVDD2 (5 V), and the digital supply pins are denoted DRVDD. Although the AVDD1 and DRVDD supplies can be tied together, best performance is achieved when the supplies are separate. This is because the fast digital output swings can couple switching current back into the analog supplies. Note that both AVDD1 and AVDD2 must be held within 5% of the specified voltage.
The DRVDD supply of the AD9445 is a dedicated supply for the digital outputs in either LVDS or CMOS output mode. When in LVDS mode, the DRVDD should be set to 3.3 V. In CMOS mode, the DRVDD supply can be connected from 2.5 V to 3.6 V for compatibility with the receiving logic. TIMING
The AD9445 provides latched data outputs with a pipeline delay of 13 clock cycles. Data outputs are available one propagation delay (tPD) after the rising edge of CLK+. Refer to
DIGITAL OUTPUTS LVDS Mode Figure 2 and
Figure 3 for detailed timing diagrams. The off-chip drivers on the chip can be configured to provide LVDS-compatible output levels via Pin 3 (OUTPUT MODE). LVDS outputs are available when OUTPUT MODE is CMOS logic high (or AVDD1 for convenience) and a 3.74 k RSET
AD9445
Rev. 0 | Page 28 of 40
OPERATIONAL MODE SELECTION Data Format Select
The data format select (DFS) pin of the AD9445 determines the coding format of the output data. This pin is 3.3 V CMOS-compatible, with logic high (or AVDD1, 3.3 V) selecting twos complement and DFS logic low (AGND) selecting offset binary format. Table 10 summarizes the output coding.
Output Mode Select
The OUPUT MODE pin controls the logic compatibility, as well as the pinout of the digital outputs. This pin is a CMOS-compatible input. With OUTPUT MODE = 0 (AGND), the AD9445 outputs are CMOS compatible, and the pin assignment for the device is as defined in Table 8. With OUTPUT MODE = 1 (AVDD1, 3.3 V), the AD9445 outputs are LVDS compatible, and the pin assignment for the device is as defined in Table 7.
Duty Cycle Stabilizer
The DCS circuit is controlled by the DCS MODE pin; a CMOS logic low (AGND) on DCS MODE enables the DCS, and logic high (AVDD1, 3.3 V) disables the controller.
RF ENABLE
The RF ENABLE pin is a CMOS-compatible control pin that optimizes the configuration of the AD9445 analog front end. The crossover analog input frequency for determining the RF ENABLE connection differs for the 105 MSPS and 125 MSPS speed grades. For the 125 MSPS speed grade, connecting the RF ENABLE to AGND optimizes SFDR performance for appli-cations with analog input frequencies 210 MHz, this pin should be connected to AVDD1 for optimum SFDR performance. Connecting this pin to AVDD1 reconfigures the ADC, thereby improving high IF and RF spurious performance. Operating in this mode increases power dis-sipation from AVDD2 by 150 mW to 200 mW. For the 105 MSPS speed grade, connecting RF ENABLE to AGND optimizes SFDR performance for applications with analog input frequencies 230 MHz, this pin should be connected to AVDD1 to optimize performance.
Table 10. Digital Output Coding
Code VIN+ VIN Input Span = 3.2 V p-p (V)
VIN+ VIN Input Span = 2 V p-p (V)
Digital Output Offset Binary (D13D0)
Digital Output Twos Complement (D13D0)
16,383 +1.600 +1.000 11 1111 1111 1111 01 1111 1111 1111 8192 0 0 10 0000 0000 0000 00 0000 0000 0000 8191 0.000195 0.000122 01 1111 1111 1111 11 1111 1111 1111 0 1.60 1.00 00 0000 0000 0000 10 0000 0000 0000
AD9445
Rev. 0 | Page 29 of 40
EVALUATION BOARD Evaluation boards are offered to configure the AD9445 in either CMOS or LVDS mode only. This design represents a recommended configuration for using the device over a wide range of sampling rates and analog input frequencies. These evaluation boards provide all the support circuitry required to operate the ADC in its various modes and configurations. Complete schematics are shown in Figure 67 through Figure 70. Gerber files are available from engineering applications demon-strating the proper routing and grounding techniques that should be applied at the system level.
It is critical that signal sources with very low phase noise (
AD9445
Rev. 0 | Page 30 of 40
OPTIONAL
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Figure 67. AD9445 Evaluation Board Schematic
AD9445
Rev. 0 | Page 31 of 40
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0548
9-06
3
Figure 68. AD9445 Evaluation Board Schematic (Continued)
AD9445
Rev. 0 | Page 32 of 40
C960.1F
C970.1F
C840.1F
C460.1F
C220.1F
C590.1F
C930.1F
C940.1F
C950.1F
5V
GND
C600.1F
C100.1F
C610.1F
C750.1F
C270.1F
C900.1F
C500.1F
C300.01F
C280.1F
C350.1F
C320.1F
VCC
BYPASS CAPACITORS
GND
C31XX
C38XX
C29XX
C19XX
C17XX
C16XX
C15XX
C11XX
C14XX
VCC
GND
C370.1F
C480.1F
C180.1F
C530.1F
C520.1F
C580.01F
C5610F
+ C850.1F
5V
GND
C110XX
C108XX
C109XX
C72XX
C73XX
5V
GND
C210.1F
C200.1F
C6510F
+ C470.1F
C230.1F
DRVDD
DRGND
C6410F
+ C430.1F
C45XX
C49XX
C69XX
C70XX
DRVDD
DRGND
C5510F
+EXTREF
GND
0548
9-06
4
Figure 69. AD9445 Evaluation Board Schematic (Continued)
AD9445
Rev. 0 | Page 33 of 40
0548
9-06
5
RSO
16IS
O220
R8
R7
R6
R5
R4
R3
R1
R2
RSO
16IS
O220
8765431 2
16 15 14 13 12 11 10 9
RZ4
8765431 2
16 15 14 13 12 11 10 9
RZ5
D1O
D0O
D2O
D4O
D5O
D6O
D7O
D3OD8O
D9O
D10
O
D11
O
D12
O
D13
O
D14
O
D15
O
GN
D5
VCC
6VC
C5
GN
D4
END
D4Y
D3Y
D2Y
D1Y
ENC
C4Y
C3Y
C2Y
C1Y
GN
D3
VCC
4VC
C3
GN
D2
B4Y
B3Y
B2Y
B1Y
ENB
A4Y
A3Y
A2Y
A1Y
ENA
GN
D1
VCC
2VC
C1
GN
D
D4B
D4A
D3B
D3A
D2B
D2A
D1B
D1A
C4B
C4A
C3B
C3A
C2B
C2A
C1B
C1A
B4B
B4A
B3B
B3A
B2B
B2A
B1B
B1A
A4B
A4A
A3B
A3A
A2B
A2A
A1B
A1A
3334353637383940414243444546474849505152535455565758596061626364
3231302928272625242322212019181716151413121110987654321
U8
SN75
LVD
S386
D15
_C/D
14_Y
D14
_C/D
12_Y
D13
_C/D
10_Y
D12
_C/D
8_Y
D11
_C/D
6_Y
D10
_C/D
4_Y
D9_
C/D
2_Y
D3_
C
D15
_T/D
15_Y
D14
_T/D
13_Y
D13
_T/D
11_Y
D12
_T/D
9_Y
D11
_T/D
7_Y
D10
_T/D
5_Y
D9_
T/D
3_Y
D8_
T/D
1_Y
D8_
C/D
0_Y
D7_
TD
7_C
D6_
TD
6_C
D5_
CD
5_T
D4_
TD
4_C
D3_
T
D2_
TD
2_C
D1_
TD
1_C
D0_
TD
0_C
DR
VDD
DR
VDD
DR
GN
D
DR
GN
D
DR
GN
D
DR
VDD
DR
VDD
DR
GN
DD
RVD
DD
RVD
DD
RG
ND
DR
VDD
DR
VDD
DR
VDD
DR
VDD
DR
GN
DP1P3P5P7P9P1
1
P13
P15
P17
P19
P21
P23
P25
P27
P29
P31
P33
P35
P37
P39
P2P4P6P8P10
P12
P14
P16
P18
P20
P22
P24
P26
P28
P30
P32
P34
P36
P38
P40
P6C
40M
S
13579111315171921232527293133353739
246810121416182022242628303234363840
D14
_C/D
12_Y
D12
_C/D
8_Y
D10
_C/D
4_Y
D8_
C/D
O_Y
DR
B
D7_
C
D4_
C
D3_
C
D2_
C
D5_
C
D6_
C
D9_
C/D
2_Y
D11
_C/D
6_Y
D13
_C/D
10_Y
D1_
C
DO
R_C
DR
GN
D
D15
_C/D
14_Y
DR
GN
D
D0_
C
D14
_T/D
13_Y
D12
_T/D
9_Y
D10
_T/D
5_Y
D8_
T/D
1_Y
DR
D7_
T
D4_
T
D3_
T
D2_
T
D5_
T
D6_
T
D9_
T/D
3_Y
D11
_T/D
7_Y
D13
_T/D
11_Y
D1_
T
DO
R_T
/DO
R_Y
DR
GN
D
D15
_T/D
15_Y
DR
GN
D
D0_
TR
8
R7
R6
R5
R4
R3
R1
R2
EN_3
_44Y3YG
ND
VCC2Y1Y
EN_1
_2
4B4A3B3A2B2A1B1A
910111213141516
87654321
U15
SN75
LVD
T390
R19 0 R10 0
DR
B
DO
R_CD
R
DO
R_T
/DO
R_Y
DR
OD
RVD
D
DR
VDD
DR
GN
D
OR
OD
RVD
D
C76
0.1
FC
820.
1F
C77
0.1
FC
780.
1F
DR
VDD
DR
GN
D
P1P3P5P7P9P11
P13
P15
P17
P19
P21
P23
P25
P27
P29
P31
P33
P35
P37
P39
P2P4P6P8P10
P12
P14
P16
P18
P20
P22
P24
P26
P28
P30
P32
P34
P36
P38
P40
P7C
40M
S
13579111315171921232527293133353739
246810121416182022242628303234363840
D15
O
D13
O
D11
O
D9O
D8O
D7O
D4O
D3O
D2O
D5O
D6O
D10
O
D12
O
D14
O
D1O
DR
O
DR
GN
DD
RG
ND
GN
DN
DR
GN
D
OR
O
DR
GN
D
D0O
Figure 70. AD9445 Evaluation Board Schematic (Continued)
AD9445
Rev. 0 | Page 34 of 40
Table 11. AD9445-125 Baseband Customer Evaluation Board Bill of Materials Item Qty. Reference Designator Description Package Value Manufacturer Mfg. Part No. 1 7 C4, C6, C33, C34, C87,
C88, C89 Capacitor TAJD 10 F Digi-Key Corporation 478-1699-2
2 44 C2, C3, C5, C7, C8, C9, C10, C11, C12, C15, C20, C21, C22, C23, C26, C27, C28, C32, C35, C38, C40, C42, C43, C46, C47, C48, C50, C52, C53, C59, C60, C76, C77, C78, C82, C84, C85, C86, C90, C91, C94, C95, C96, C97
Capacitor 402 0.1 F Digi-Key Corporation PCC2146CT-ND
3 2 C30, C58 Capacitor 201 0.01 F Digi-Key Corporation 445-1796-1-ND 4 4 C39, C56, C64, C65 Capacitor TAJD 10 F Digi-Key Corporation 478-1699-2 5 1 C51 Capacitor 805 10 F Digi-Key Corporation 490-1717-1-ND 6 1 CR1 Diode SOT23M5 Digi-Key Corporation MA3X71600LCT-ND 7 1 CR2 Diode SOT23M5 Digi-Key Corporation MA3X71600LCT-ND 8 20 E1, E2, E3, E4, E5, E6,
E9, E10, E14, E18, E19, E20, E24, E25, E26, E27, E30, E31, E36, E41
Header EHOLE Mouser Electronics 517-6111TG
9 2 J1, J4 SMA SMA Digi-Key Corporation ARFX1231-ND 10 1 L1 Inductor 0603A 10 nH Coilcraft, Inc. 0603CS-10NXGBU 11 3 L3, L4, L5 EMIFIL
BLM31PG500SN1L 1206MIL Mouser Electronics 81-BLM31P500S
12 1 P4 PJ-002A PJ-002A Digi-Key Corporation CP-002A-ND 13 1 P7 Header C40MS Samtec, Inc. TSW-120-08-L-D-RA 14 1 R3 Resistor 402 3.74 k Digi-Key Corporation P3.74KLCT-ND 15 1 R8 Resistor 402 50 Digi-Key Corporation P49.9LCT-ND 16 4 R10, R19, R39, L2 Resistor 402 0 Digi-Key Corporation P0.0JCT-ND 17 1 R11 BRES402 402 1 k Digi-Key Corporation P1.0KLCT-ND 18 2 R28, R35 Resistor 402 33 Digi-Key Corporation P33JCT-ND 19 2 RZ4, RZ5 Resistor array 16PIN 22 Digi-Key Corporation 742C163220JCT-ND 20 2 T3, T5 Transformer ADT1-1WT Mini-Circuits ADT1-1WT 21 1 U1 AD9445BSVZ-125 SV-100-3 Analog Devices, Inc. AD9445BSVZ-125 22 1 U14 ADP3338-5 SOT-223HS Analog Devices, Inc. ADP3338-5 23 2 U3, U7 ADP3338-3.3 SOT-223HS Analog Devices, Inc. ADP3338-33 24 1 U8 SN75LVDT386 TSSOP64 Arrow Electronics, Inc. SN75LVDT386DGG 25 1 U15 SN75LVDT390 SOIC16PW Arrow Electronics, Inc. SN75LVDT390PW 26 2 R4, R6 Resistor 402 36 Digi-Key Corporation P36JCT-ND 27 2 C1, C44, C551 Capacitor TAJD 10 F Digi-Key Corporation 478-1699-2 28 23 C13, C14, C16, C17,
C18, C19, C29, C31, C36, C37, C41, C45, C49, C61, C69, C70, C72, C73, C75, C93, C108, C109, C1101
CAP402 402 XX
29 1 C981 Capacitor 805 10 F Digi-Key Corporation 490-1717-1-ND 30 E151 Header EHOLE Mouser Electronics 517-6111TG 31 J51 SMA SMA Digi-Key Corporation ARFX1231-ND 32 P61 Header C40MS Samtec, Inc. TSW-120-08-L-D-RA 33 2 R1, R21 BRES402 402 XX 34 3 R5, R7, R91 BRES402 402 XX 35 1 U21 ECLOSC DIP4(14)
AD9445
Rev. 0 | Page 35 of 40
Item Qty. Reference Designator Description Package Value Manufacturer Mfg. Part No. 36 4 H1, H2, H3, H41 MTHOLE6 MTHOLE6 37 2 T1, T21 Balun transformer SM-22 M/A-COM ETC1-1-13 38 2 P21, P221 Term strip PTMICRO4 Newark Electronics 1 Parts not populated.
Table 12. AD9445-125 IF Customer Evaluation Board Bill of Materials Item Qty. Reference Designator Description Package Value Manufacturer MFG_PART_NO 1 7 C4, C6, C33, C34, C87,
C88, C89 Capacitor TAJD 10 F Digi-Key Corporation 478-1699-2
2 44 C2, C3, C5, C7, C8, C9, C10, C11, C12, C15, C20, C21, C22, C23, C26, C27, C28, C32, C35, C38, C40, C42, C43, C46, C47, C48, C50, C52, C53, C59, C60, C76, C77, C78, C82, C84, C85, C86, C90, C91, C94, C95, C96, C97
Capacitor 402 0.1 F Digi-Key Corporation PCC2146CT-ND
3 2 C30, C58 Capacitor 201 0.01 F Digi-Key Corporation 445-1796-1-ND 4 4 C39, C56, C64, C65 Capacitor TAJD 10 F Digi-Key Corporation 478-1699-2 5 1 C51 Capacitor 805 10 F Digi-Key Corporation 490-1717-1-ND 6 1 CR1 Diode SOT23M5 Digi-Key Corporation MA3X71600LCT-ND 7 1 CR2 Diode SOT23M5 Digi-Key Corporation MA3X71600LCT-ND 8 20 E1, E2, E3, E4, E5, E6,
E9, E10, E14, E18, E19, E20, E24, E25, E26, E27, E30, E31, E36, E41
Header EHOLE Mouser Electronics 517-6111TG
9 2 J1, J4 SMA SMA Digi-Key Corporation ARFX1231-ND 10 1 L1 Inductor 0603A 10 nH Coilcraft, Inc. 0603CS-10NXGBU 11 3 L3, L4, L5 EMIFIL BLM31PG500SN1L 1206MIL Mouser Electronics 81-BLM31P500S 12 1 P4 PJ-002A PJ-002A Digi-Key Corporation CP-002A-ND 13 1 P7 Header C40MS Samtec, Inc. TSW-120-08-L-D-RA 14 1 R3 Resistor 402 3.74 k Digi-Key Corporation P3.74KLCT-ND 15 1 R8 Resistor 402 50 Digi-Key Corporation P49.9LCT-ND 16 4 R10, R19, R39, L2 Resistor 402 0 Digi-Key Corporation P0.0JCT-ND 17 1 R11 BRES402 402 1 k Digi-Key Corporation P1.0KLCT-ND 18 2 R28, R35 Resistor 402 33 Digi-Key Corporation P33JCT-ND 19 2 RZ4, RZ5 Resistor array 16PIN 22 Digi-Key Corporation 742C163220JCT-ND 20 1 U1 AD9445BSVZ-125 SV-100-3