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CHAPTER 4. GEODA-SARAS T/R MODULE IMPLEMENTATIONFIVE ELEMENT CELL AND PANEL CONVERSION MODULE
2-Way 0ºPower Splitter
Linsertion = 0.5 dB
G = 13 dB
SIMPLE RECEIVER CHAIN INTERFERENCE STUDY (Part I)
L = 0.15 dB
Radiating Element 30 dB Coupler Diplexer LNA
G = 13 dB
T Filter LNA
G = 13 dB
2-Way 0ºPower Splitter
Linsertion = 0.5 dBLsplit = 3 dB
PolarizingAttenuator
2-Way 90ºPower Splitter
SPDTSwitcher
L = 0.95 dB
T Filter LNA
Phase Shifter
L = 3.2 dB
LT = 35 dB LR = 1 dBLI = 20 dB
PT_Interference = +17.00 dBmPR_Interference = -87.20 dBmPI_Interference = -62.00 dBm
PT_Interference = +16.85 dBmPR_Interference = -87.35 dBmPI_Interference = -62.15 dBm
PT_Interference = -18.15 dBmPR_Interference = -88.35 dBmPI_Interference = -82.15 dBm
PT_Interference = -5.15 dBmPR_Interference = -75.35 dBmPI_Interference = -69.15 dBm
LT = 10 dBLR = 1.5 dBLI = 1.5 dB
PT_Interference = -5.15 dBmPR_Interference = -75.3 dBmPI_Interference = -69.15 dBm
PT_Interference = -15.15 dBmPR_Interference = -76.85 dBmPI_Interference = -70.65 dBm
PT_Interference = -2.15PR_Interference = -63.85 dBmPI_Interference = -57.65 dBm
PT_Interference = -5.65 dBmPR_Interference = -67.35 dBmPI_Interference = -61.15 dBm
PT_Interference = -7.65 dBmPR_Interference = -69.35 dBmPI_Interference = -63.15 dBm
PT_Interference = -3.00 dBmPR_Interference = -56.20 dBmPI_Interference = -50.00 dBm
PT_Interference = -6.20 dBmPR_Interference = -59.40 dBmPI_Interference = -53.20 dBm
PT_Interference = -8.20 dBmPR_Interference = -61.40 dBmPI_Interference = -55.20 dBm
PT_Interference = -8.70 dBmPR_Interference = -61.90 dBmPI_Interference = -55.70 dBm
PT_Interference = -2.70 dBmPR_Interference = -55.90 dBmPI_Interference = -49.70 dBm
Attenuator
Lmin = 2 dB
Lmin = 2 dB
3-Way 0ºPower Splitter
Linsertion = 1 dBGcombination = 7 dB
LT = 10 dBLR = 1.5 dBLI = 1.5 dB
PT_Interference = -5.05 dBmPR_Interference = -66.75 dBmPI_Interference = -60.55 dBm
PT_Interference = -6.00 dBmPR_Interference = -67.70 dBmPI_Interference = -61.50 dBm
PT_Interference = -16.00 dBmPR_Interference = -69.20 dBmPI_Interference = -63.00 dBm
PT_Interference = -3.00 dBmPR_Interference = -56.20 dBmPI_Interference = -50.00 dBm
PT_Interference = -7.65 dBmPR_Interference = -69.35 dBmPI_Interference = -63.15 dBm
SPDTSwitcher
L = 0.95 dB
SPDTSwitcher
L = 0.95 dB
SPDTSwitcher
L = 0.95 dB
RXBPF
PT_Interference = -2.70 dBmPR_Interference = -55.90 dBmPI_Interference = -49.70 dBm
PT_Interference = -3.65 dBmPR_Interference = -56.85 dBmPI_Interference = -50.65 dBm
PT_Interference = -4.60 dBmPR_Interference = -57.80 dBmPI_Interference = -51.60 dBm
PT_Interference = -5.55 dBmPR_Interference = -58.75 dBmPI_Interference = -52.55 dBm
PT_Interference = -45.55 dBmPR_Interference = -60.95 dBmPI_Interference = -97.55 dBm
LT = 40 dBLR = 2.2 dBLI = 45 dB
Linsertion = 0.4 dBGcombination = 3 dB
S1 A1
R1
RAC
RA C1-RXA
C1-RXA C1-RX1
AR1
128
4.5. SIGNAL-FLOW STUDY IN RX AND TX CHAINS
SIMPLE RECEIVER CHAIN INTERFERENCE STUDY (Part II)SPDT
Switcher
GT = 15.5 dBGR = 16.5 dB
LNA
G = 13 dB
RXBPF LNA
G = 13 dB
IF Mixer
G= 8.2 dB
IFBPF
GT = 15.5 dBGR = 16.5 dB
IF Amplifier IF Amplifier
LT = 40 dBLR = 2.2 dBLI = 45 dB
PT_Interference = -22.50 dBmPR_Interference = -37.90 dBmPI_Interference = -74.50 dBm
PT_Interference = -62.50 dBmPR_Interference = -40.10 dBmPI_Interference = -119.50 dBm
PT_Interference = -49.50 dBmPR_Interference = -27.10 dBmPI_Interference = -106.50 dBm
PT_Interference = -50.45 dBmPR_Interference = -28.05 dBmPI_Interference = -107.45 dBm
PT_Interference = -42.25 dBmPR_Interference = -19.85 dBmPI_Interference = -99.25 dBm
LT = 55 dB LR = 55 dBLI = 7.5 dB
PT_Interference = -42.25 dBmPR_Interference = -19.85 dBmPI_Interference = -99.25 dBm
PT_Interference = -97.25 dBmPR_Interference = -74.85 dBmPI_Interference = -106.75 dBm
PT_Interference = -99.25 dBmPR_Interference = -76.85 dBmPI_Interference = -108.75 dBm
PT_Interference = -83.75 dBmPR_Interference = -60.35 dBmPI_Interference = -92.25 dBm
PT_Interference = -68.25 dBmPR_Interference = -43.85 dBmPI_Interference = -75.75 dBm
PT_Interference = -32.55 dBmPR_Interference = -47.95 dBmPI_Interference = -84.55 dBm
PT_Interference = -34.55 dBmPR_Interference = -49.95 dBmPI_Interference = -86.55 dBm
PT_Interference = -35.50 dBmPR_Interference = -50.90 dBmPI_Interference = -87.50 dBm
PT_Interference = -22.50 dBmPR_Interference = -37.90 dBmPI_Interference = -74.50 dBm
PT_Interference = -45.55 dBmPR_Interference = -60.95 dBmPI_Interference = -97.55 dBm
LNA
G = 13 dB
Attenuator
Lmin = 2 dB L = 0.95 dB
SPDTSwitcher
L = 0.95 dB
IF
IF
IF
Attenuator
Lmin = 2 dB
C1-RX2 C1-RF
IF1
IF1 IF2
Figure 4.30: Receiver Interferences.
Garray =4π
λ2Ae (4.6)
GHexagonal Array = 30.4 dB (4.7)
On the other hand, the total equivalent noise temperature in the receiver is given
by the sum of three contributions: the added noise due to transmitter amplification
stage, the receiver chain noise, and the antenna noise. The first two contributions have
already been calculated in 4.5.1 and 4.5.2. Considering a clear sky scenario, the antenna
temperature at the working frequency is between 5K and 20K. Thus, total equivalent
noise temperature is presented in Eq. 4.8.
129
CHAPTER 4. GEODA-SARAS T/R MODULE IMPLEMENTATIONFIVE ELEMENT CELL AND PANEL CONVERSION MODULE
S1
A1
AR
1
R1
RA
C
RA
C1-R
XA
C1-R
X1
C1-R
X2
C1-R
F
IF1
IF2
Inte
rfer
ence
Pow
er[d
Bm
]
Figure 4.31: Receiver Interference Graph.
Ttotalmin = Tamin + Treceiver + Ttransmittermin = 192.1 + 0.4 + 5 = 197.5 K
Ttotalmax = Tamax + Treceiver + Ttransmittermin = 192.1 + 28.7 + 20 = 240.8 K(4.8)
Obtaining a G/T factor depicted in Eq. 4.9; which is higher than the required G/T
sensitivity, fulfilling the 4.1 dB/K technical specifications.
G/Tmin = GTtotalmax
= 7.4 dB/K
G/Tmax = GTtotalmin
= 6.6 dB/K(4.9)
4.6 Array Factor: Gain Loss Due to Phase Quantization
Error
As previously discussed in Chapter 2, the use of digital phase shifters in active antennas
with RF beamforming implies a gain loss. This gain loss is found in every system
involving phase signal errors, which may cause non-coherent RF beamforming. The
maximum gain loss is determined by the minimum digital phase shift step. For the case
understudy, the maximum gain loss due to phase quantization error must be lower than
0.5 dB for any system configuration. After a market research, it is selected the MAPS-
130
4.6. ARRAY FACTOR: GAIN LOSS DUE TO PHASE QUANTIZATION ERROR
2-Way 0ºPower Splitter
l = 1.12T = 35.4 K
g = 20T = 75.0 K
SIMPLE RECEIVER CHAIN EQUIVALENT TEMPERATURE STUDY (Part I)
L = 0.15 dB
Radiating Element 30 dB Coupler Diplexer LNA
g = 20 T = 75.0 K
T Filter LNA2-Way 0º
Power Splitter
l = 1.12T = 35.4 K
PolarizingAttenuator
2-Way 90ºPower Splitter
SPDTSwitcher
l = 1.24T = 70.9 K
T Filter LNA
Phase Shifter
l = 2.1T = 315.9 K
l = 1.26T = 75.0 K
l = 1.41T = 119.6 K
Attenuator
lmin=1.58;Tmin=169.6 Klmax=56.2;Tmax=16017.9K
lmin=1.58; Tmin=169.6 Klmax=3.55; Tmax=738.9 K
3-Way 0ºPower Splitter
l = 1.26T = 75.0 K
l = 1.41T = 119.6 K
SPDTSwitcher
l = 1.24T = 70.9 K
SPDTSwitcher
l = 1.24T = 70.9 K
SPDTSwitcher
l = 1.24T = 70.9 K
RXBPF
Te_min
gmax
Te_max
gmin
Te_min = 75.0 Kgmax = 0.8
Te_max = 75.0 Kgmin = 0.8
Te_min = 169.5 Kgmax = 15.9
Te_max = 169.5 Kgmin = 15.9
Te_min = 169.5 Kgmax = 15.9
Te_max = 169.5 Kgmin = 15.9
Te_min = 177.0 Kgmax = 11.3
Te_max = 177.0 Kgmin = 11.3
Te_min = 183.7 Kgmax = 225.2
Te_max = 183.7 Kgmin = 225.1
Te_min = 183.9 Kgmax = 201.0
Te_max = 183.9 Kgmin = 201.0
Te_min = 184.7 Kgmax = 127.2
Te_max = 187.5 Kgmin = 56.6
Te_min = 187.9 Kgmax = 1323.1
Te_max = 194.8 Kgmin = 588.9
Te_min = 188.2 Kgmax = 630.0
Te_max = 195.4 Kgmin = 280.4
Te_min = 188.5 Kgmax = 398.8
Te_max = 252.5 Kgmin = 5.0
Te_min = 188.5 Kgmax = 356.0
Te_max = 259.6 Kgmin = 4.5
Te_min = 188.8 Kgmax = 282.6
Te_max = 276.4 Kgmin = 3.5
Te_min = 184.9 Kgmax = 115.7
Te_max = 188.0 Kgmin = 51.5
Te_min = 185.5 Kgmax = 93.3
Te_max = 189.4 Kgmin = 41.5
Te_min = 186.8 Kgmax = 66.2
Te_max = 192.3 Kgmin = 29.4
Te_min = 187.9 Kgmax = 1323.1
Te_max = 194.8 Kgmin = 588.9
Te_min = 184.7 Kgmax = 127.2
Te_max = 187.5 Kgmin = 56.6
Te_min = 188.8 Kgmax = 282.6
Te_max = 276.4 Kgmin = 3.5
Te_min = 189.0 Kgmax = 227.9
Te_max = 296.5 Kgmin = 2.9
Te_min = 189.3 Kgmax = 183.8
Te_max = 321.3 Kgmin = 2.3
Te_min = 189.7 Kgmax = 148.2
Te_max = 352.2 Kgmin = 1.9
Te_min = 191.0 Kgmax = 89.3
Te_max = 455.3 Kgmin = 1.1
l = 1.66T = 191.3 K
l = 1.1T = 28.0
S1 A1
R1
RAC
RA C1-RXA
C1-RXA C1-RX1
AR1
g = 20T = 75.0 K
131
CHAPTER 4. GEODA-SARAS T/R MODULE IMPLEMENTATIONFIVE ELEMENT CELL AND PANEL CONVERSION MODULE
SIMPLE RECEIVER CHAIN EQUIVALENT TEMPERATURE STUDY (Part II)SPDT
Switcher
g = 44.7T = 315.9 K
LNA
g = 20T = 75.0 K
RXBPF LNA
g = 20T = 75.0 K
IF Mixer
g = 6.6T = 3039.6 K
IFBPF
g = 44.7T = 315.9 K
IF Amplifier IF Amplifier
l =1.66T = 191.3 K
l = 5.6T = 1340.8 K
Te_min = 192.1 Kgmax = 1822.8
Te_max = 1651.7 Kgmin = 6.4
Te_min = 192.1 Kgmax = 1098.1
Te_max = 1681.5 Kgmin = 3.9
Te_min = 192.1 Kgmax = 21962
Te_max = 1700.9 Kgmin = 77.3
Te_min = 192.1 Kgmax = 17711.3
Te_max = 1701.8 Kgmin = 62.3
Te_min = 192.1gmax = 116894.5
Te_max = 1750.6 Kgmin = 411.2
Te_min = 192.1 Kgmax = 116894.5
Te_max = 1750.6 Kgmin =411.2
Te_min = 192.1 Kgmax = 20874.0
Te_max = 1753.9 Kgmin = 73.4
Te_min = 192.1 Kgmax = 13211.4
Te_max = 1972.0 Kgmin = 1.3
Te_min = 192.1 Kgmax = 590549.8
Te_max = 2213.8 Kgmin = 58.4
Te_min = 192.1 Kgmax = 26397577.3Te_max = 2219.2 K
gmin = 2610.6
Te_min = 191.8 Kgmax =1785.6
Te_max = 522.5 Kgmin = 22.3
Te_min = 191.9 Kgmax = 1130.1
Te_max = 1239.4 Kgmin = 0.4
Te_min = 192.0 Kgmax = 911.4
Te_max = 1417.7 Kgmin = 0.3
Te_min = 192.1 Kgmax =1822.8
Te_max = 1651.7 Kgmin = 6.4
Te_min = 191.0 Kgmax = 89.3
Te_max = 455.3 Kgmin = 1.1
LNA
g = 20T = 75.0 K
Attenuator
lmin=1.58;Tmin=169.6 Klmax=56.2;Tmax=16017.9K
l = 1.24T = 70.9 K
SPDTSwitcher
l = 1.24T = 70.9 K
IF
IF
IF
Attenuator
lmin=1.58;Tmin=169.6 Klmax=56.2;Tmax=16017.9K
C1-RX2 C1-RF
IF1
IF1 IF2
Figure 4.32: Receiver Equivalent Noise Temperature.
010143 4-bits digital phase shifter from M/A-COM. Figures 4.34-4.36 show a gain loss
study of the three possible antenna architecture RF beamforming configuration: single
cell, 3 cell combination, and whole panel. None of the configurations exceed 0.1 dB losses,
fulfilling the specification. It is important to note that, a larger number of elements per
array implies a greater uniformity gain.
132
4.6. ARRAY FACTOR: GAIN LOSS DUE TO PHASE QUANTIZATION ERROR
AR
1
R1
RA
C
RA
C1-R
XA
C1-R
X1
C1-R
X2
C1-R
F
IF1
IF2
Equiv
alen
t N
ois
e T
emper
ature
[K
]100
76
52
28
4
-20
Rec
eiver
Gai
n [
dB
]
Figure 4.33: Equivalent Noise Temperature vs Gain.
GEODA-SARAS CELL ARRAY
!"
xz
y
xy
z
!"
xz
y
[dB]
Figure 4.34: Cell Gain Loss Due to Phase Quantization.
133
CHAPTER 4. GEODA-SARAS T/R MODULE IMPLEMENTATIONFIVE ELEMENT CELL AND PANEL CONVERSION MODULE
3 GEODA-SARAS CELL ARRAY
xz
y
!"
xz
y
xy
z
!"
[dB]
Figure 4.35: 3 Cell Combination Gain Loss Due to Phase Quantization.
GEODA-SARAS PANEL ARRAY
!"
xz
y
xy
z
!"
xz
y
[dB]
Figure 4.36: Panel Gain Loss Due to Phase Quantization.
134
4.7. CONCLUSIONS
4.7 Conclusions
The presented Chapter comes to the following main conclusions:
An exhaustive study of the state of the art of the GEODA antenna has been presented
in Section 1.4.2, laying the groundwork for its current concept. Firstly, as depicted in
Section 1.4.2, a successful single circular polarization active receiver phased array for
satellite communications working at 1.7 GHz was implemented. Its basic array was a
triangular panel composed of 45 radiating elements divided into subarray cells of threes.
By using 60 triangular panels, a geodesic structure could be built; covering a +5o to +90o
elevation in the whole 360o azimuth field of regard. Each radiating element has a control
phase block with which is possible to implement an RF beamforming. Thus, the antenna
is an RF/digital beamforming hybrid solution, in which the hardware beamforming adds
the contributions of all of the cells compounding a panel. After validation, the antenna
evolved to a new concept, in which it was provided with the transmission capability
by introducing a T/R module per radiating element (GEODA-GRUA). GRUA project
was born with the aim of creating a novel GEODA with double circular polarization in
both, transmission and reception, modes. The mechanical structure and the radiating
elements were reused in order to reduce costs. Hence, a T/R module was designed,
constructed and optimized, improving size and behavior.
Subsequently, in order to improve the antenna competence; an adaptive flat antenna
for ground stations able to solve the communication problems not only in the orbital
process but in the launch process has been presented, GEODA-SARAS. As many sate-
llite constellations allow to establish S-band links, increasing data link bit rate; 2.025
GHz to 2.120 GHz is the current transmission band, and 2.2 GHz to 2.3 GHz is the
current reception band. The antenna is able to work simultaneously in transmission
and reception modes with dual circular polarization. The antenna structure becomes
a flat architecture based on a regular hexagon composed of 6 planar triangular arrays
(panels). Each panel is integrated by 45 radiating elements, grouped in subarray cells
of fives. Every hexagonal array of 6 panels provides one full transmitter and two full
independent receiver systems. These 6 panel array antenna can implement any greater
structure composed of regular hexagons. Hence a huge phased array dome antenna
similar to the original GEODA can be built. In this case, the active antenna is also
considered as a hybrid architecture where the signal is RF beamfomed and then pro-
cessed to be combined and treated as required. The difference respect GEODA original
solution lies in the way the RF beamforming is performed. Now, each panel is provided
with an RF receiver beam switching network, which allows to receive and digitalize the
135
CHAPTER 4. GEODA-SARAS T/R MODULE IMPLEMENTATIONFIVE ELEMENT CELL AND PANEL CONVERSION MODULE
signal of: a single cell, or a triplet of cells, or a whole panel. Thus, in this new antenna
approach, sub-array cells are not only a physical division that simplifies the antenna de-
sign and enhances its replaceability, but also individual full receiver chains which could
be RF/digital beam-formed.
The implementation of this novel hexagonal flat array has been presented exhaus-
tively. The architecture technical skills and the main blocks compounding it has been
described.
Each cell has associated a cell module, which allows to control not only the amplitude
and phase of the transmitted/received signal but also the polarization of the signal. Each
of the five radiating elements is provided with: a T/R module, which filters and isolates
the transmitted/received signal and amplifies it; a polarization network, which selects
the polarization signal underwork; and a phase and amplitude control block, which allows
to govern the phase and amplitude of the signals to transmit/receive. Additionally, a
combiner/divider module per cell sums/divides the received/transmitted signal within
a cell.
Each panel is related to a conversion module, which performs the tasks of: am-
plifying, filtering and splitting the transmission signal to the nine cell per panel; and
combining, filtering, amplifying, and IF converting the received signal.
The calibration system is embedded in both, cell module and panel module. It allows
to verify the proper behavior of each of the blocks compounding the cell module and
panel module.
Every commercial component has been presented, verifying its performance. More-
over the implementation of the cell module and panel module has been depicted.
An analysis of the transmitting and receiving chain behaviors in many interesting
situations has been presented. In the transmitter chain, the study resolves: the mini-
mum transmitter input signal for the maximum transmitter output, the minimum and
maximum transmitter chain gain, and the noise added in the receiver due to transmit-
ting amplification process. Regarding receiver chain, the study deals with: the receiver
dynamic range, the receiver chain interference, the maximum and minimum receiver
chain gain, the receiver equivalent noise temperature, and the G/T receiver chain fac-
tor. The study shows a proper performance of the proposed architecture, which fulfills
the technical specifications.
Finally, a study of the gain loss due to the phase quantization error related to the
4 bit digital phase shifter is depicted. The analysis shows that the system meets the
predefined performance specifications.
The future task will be to verify the expected performance by measuring both, cell
136
4.7. CONCLUSIONS
module and panel conversion module. Furthermore, a triangular panel and a whole 6
panel hexagon will be measured.
137
CHAPTER 4. GEODA-SARAS T/R MODULE IMPLEMENTATIONFIVE ELEMENT CELL AND PANEL CONVERSION MODULE
138
Chapter 5
Conclusions
5.1 Framework
This thesis has been carried out in the Grupo de Radiacion of the Departamento de
Senales, Sistemas y Radiocomunicaciones in the ETSI de Telecomunicacion of the Uni-
versidad Politecnica de Madrid from October 2009 to May 2014 under the supervision
of Dr. Manuel Sierra Perez and Dr. Jose Manuel Fernandez Gonzalez.
As it is well known, international research stages promote the exchange of knowledge
and strengthen ties between the different research centers. Hence, part of the reported
work in this manuscript has been carried out during a three-month research stay (April
- June 2012) in the European Space Operations Centre (ESOC) supported by COST-
VISTA action IC1102. The centre serves as the main mission control centre for the
European Space Agency (ESA), and it is located in Darmstadt (Germany).
The contributions presented in this manuscript have been reflected in public research
projects:
• Project title: Communication systems for emergency environments
(SICOMORO) TEC2011-28789-C02-01.
Financial institution: Ministerio de Educacion y Ciencia.
Research institution: Universidad Politecnica de Madrid.
Research in chief: Belen Galocha Iraguen.
139
CHAPTER 5. CONCLUSIONS
• Project title: Caracterizacion de Canales Radio, Optimizacion y Ca-
librado de la Antena GEODA para Comunicaciones Es-
paciales (CROCANTE) TEC2008-06736-C03-01.
Financial institution: Ministerio de Educacion y Ciencia.
Research institution: Universidad Politecnica de Madrid.
Research in chief: Leandro de Haro y Ariet.
5.2 Novel Contributions
The recent emergence of new practical, low-cost, and highly reliable solid state de-
vices has broken the barrier of cost/complexity of phased array antennas, making active
phased arrays a viable future option not only for military but for civilian applications.
Therefore, the study and implementation of novel low-cost and highly efficient solid
state phased arrays capable of controlling signal phase/amplitude accurately is one of
the great challenges of our time. This thesis faces this challenge, proposing innova-
tive electronic beam steering networks and transmitter/receiver (T/R) modules using
affordable solid state components, which could integrate fair reconfigurable phased array
antennas working in L and S bands.
Original contributions of this thesis are highlighted below:
• A simple method for the design and optimization of phased array antenna cost/
performance for radar applications: The study applied to the space surveillance
awareness (SSA) radar shows that the use of an ingenious deployment strategy
when huge phased array antennas are implemented is vital to reduce costs. A
huge phased array radar for space applications has been study by using newly ESA
Matlab simulator tool. Key points of the study are: the minimum antenna area
and maximum distance between elements without grating lobes in the scanned
area, and maximum pulse width to detect minimum range per elevation angle.
The study reveals that European power amplifier technology should provide wider
waveform pulse width to reduce the number of elements compounding the array.
• A novel phase shifter power splitter/combiner network: Previous events involving
commercial phase shifter cost fluctuations highlight the need for an exhaustive
study of different hardware techniques to govern the phase signal per radiating
element in active reconfigurable antennas. After comparing three different RF
steering techniques alternatives, the study shows that the newly low-cost phase
shifter power splitter/combiner network fulfills the technical requirements of the
140
5.3. FUTURE WORK
systems with a good cost/performance rate. In order to verify the proposed design
the two main parts compounding any phase shifter power splitter/combiner net-
work have been built, obtaining a proper behavior. These measurements validate
the feasibility of these kind of novel networks.
• A quasi-orthogonal 4x3 switching beam-former for triangular arrays of three radia-
ting elements: Intrinsic features of orthogonal lossless networks limit the number
of provided beams to the number of radiating elements and impose the relation
between those beams. Therefore, the research leads to consider the possibility
of using dissipative networks, which are capable of providing a higher number of
beams than the number of radiating elements compounding the cell. The novel
quasi-orthogonal beam-former supplies three orthogonal beams in a desired θ0 ele-
vation angle and a fourth one in the broadside steering direction. The analysis
provides the relation between θ0 elevation angle and the network component, show-
ing which components must be used in a network to reach a specific θ0 elevation
angle with a defined array. Prototypes of the network verify its behavior.
• A newly T/R module chain for GEODA-SARAS phased array antenna. GEODA
antenna has been evolving through the years: The new approach dates from 2011,
when the European Space Agency signed a collaboration agreement. Nowadays,
it is desired to design an adaptive flat antenna for ground stations able to solve
the communication problems not only in the orbital process but in the launch pro-
cess too. The antenna must be able to work simultaneously in transmission and
reception modes with dual circular polarization. A thorough description of all the
components compounding GEODA-SARAS T/R module RF chains is presented.
Signal flow throw the system analyzing critical situations such as maximum trans-
mitted power (testing the chain unsaturation), minimum and maximum receiving
signal (verifying sensitivity range), maximum receiver interference signals (assur-
ing a proper reception), and G/T factor (fulfilling the technical specification) probe
a proper behavior. The system is built and under test.
5.3 Future Work
• To apply genetic algorithms to randomize the location of the radiating element of
the array in order to minimize the number of radiating elements per array aperture.
• To built a whole phase shifter power splitter/combiner network using the validated
141
CHAPTER 5. CONCLUSIONS
basic structures in order to verify its proper behavior.
• A recent study shows that it is possible to obtain a similar basic 4x3 quasi-
orthogonal beam-former governed only by a single central phase shifter. The
θ0 elevation angle is directly related to the relative phase shift introduced by the
phase shifter body. A prototype should be built in order to verify mathematical
analysis.
• To verify and calibrate the performance of the GEODA-SARAS basic modules,
cell module and panel conversion module. To measure a triangular panel and a
whole 6 panel hexagon.
5.4 Publications
This PhD thesis has given the following publications.
5.4.1 Book Chapters
• M. A. Salas Natera, A. Garcıa Aguilar, J. Mora Cueva, J. M. Fernandez, P. Padilla
de la Torre, J. Garcıa-Gasco Trujillo, R. Martınez Rodrıguez-Osorio, M. Sierra-
Perez, L. De Haro Ariet, and M. Sierra Castaner. ”New Antenna Array Archi-
tectures for Satellite Communications,” in Advances in Satellite Communications
edited by Masoumeh Karimi and Yuri Labrador, ISBN:978-953-307-562-4, Jul.
2011.
5.4.2 Journal Publications
• J. Garcıa-Gasco Trujillo, A. Noval Sanchez de Toca, I. Montesinos Ortego, J.M.
Fernandez Gonzalez, M. Sierra Perez. ”Design and Implementation of a Quasi-
Orthogonal Switching Beam-Former for Triangular Arrays of Three Radiating
Elements,” in IEEE Transactions on Antennas and Propagation, Vol. 61, pp.
5028-5035, Oct. 2013.
5.4.3 Conference Contributions
International
• J. Garcıa-Gasco Trujillo, A. Noval Sanchez de Toca, I. Montesinos Ortego, A.
Garcıa-Aguilar, M. Sierra Perez. ”Study of a New Beam Forming Network for
142
5.4. PUBLICATIONS
Triangular Arrays of Three Radiating Elements,” in 2012 IEEE International Sym-
posium on Antennas and Propagation - APS, Chicago, EE.UU, Jul. 2012.
• J. Garcıa-Gasco Trujillo, A. Noval Sanchez de Toca, I. Montesinos Ortego, M.
Sierra Perez. ”On the design and measurement of a novel non-orthogonal multi-
beam network for triangular arrays of three radiating elements,” in 6th European
Conference on Antennas and Propagation - EUCAP 2012, Prague, Czech Repub-
lic, Mar. 2012.
• A. Noval Sanchez de Toca, J. Garcıa-Gasco Trujillo, M. Sierra Perez. ”Study of
an electronic steering antenna with a staggered phase shifter configuration,” in
6th European Conference on Antennas and Propagation - EUCAP 2012, Prague,
Czech Republic, Mar. 2012.
• J. Garcıa-Gasco Trujillo, M. Salas Natera, I. Montesinos Ortego, M. Arias Campo,
M. Sierra Perez, R. Martınez. ”GEODA-GRUA: Adaptive Multibeam Conformal
Antenna for Satellites Communications,” in 30th URSI General Assembly and
Scientific Simposium of International Union of Radio Science, Istanbul, Turkey,
Aug. 2011.
• J. Garcıa-Gasco Trujillo, M. Sierra Perez, A. Novo Garcıa, M. Vera-Isasa. ”3x3
Multibeam Network for a Triangular Array of Three Radiating Elements: Design
and Measurement,” in EUROCON 2011, Lisbon, Portugal, Apr. 2011.
• J. Garcıa-Gasco Trujillo, M. Sierra Perez. ”GEODA-GRUA: Multibeam Network
Design and Measurement for Triangular Array of Three Radiating Elements,” in
5th European Conference on Antennas and Propagation - EUCAP 2011, Rome,
Italy, Apr. 2011.
• A. Novo Garcıa, M. Vera-Isasa, J. Garcıa-Gasco Trujillo, M. Sierra Perez. ”6x3
Microstrip Beam Forming Network for Multibeam Triangular Array,” in PIERS
2011, Marrakesk, Morocco, Mar. 2011.
National
• J.M. Inclan Alonso, A. Noval Sanchez de Toca, J. Garcıa-Gasco Trujillo, J.M.
Fernandez Gonzalez, M. Sierra Perez. ”Radiating Element of GEODA-SARAS,”
in XXVIII Simmposium Nacional de la Union Cientıfica Internacional de Radio -
URSI 2013, Santiago de Compostela, Spain, Sep. 2013.
143
CHAPTER 5. CONCLUSIONS
• J. Garcıa-Gasco Trujillo, A. Noval Sanchez de Toca, I. Montesinos Ortego, J.M.
Fernandez, M. Sierra Perez. ”Diseno y Medida de una Novedosa Red Multihaz
Conmutada de Cuatro Haces para Arrays Triangulares de Tres Elementos Radi-
antes,” in XXVII Simmposium Nacional de la Union Cientıfica Internacional de
Radio - URSI 2012, Elche, Spain, Sep. 2012.
• J. Garcıa-Gasco Trujillo, M. Salas Natera, I. Montesinos Ortego, M. Arias Campo,
R. Martınez, M. Sierra Perez. ”Progresos en Sub-Sistemas RF y Control de la
Antena Adaptativa Multihaz GEODA,” in XXVI Simmposium Nacional de la
Union Cientıfica Internacional de Radio - URSI 2011, Leganes, Spain, Sep. 2011.
• A. Noval Sanchez de Toca, J. Garcıa-Gasco Trujillo, M. Sierra Perez. ”Red Mul-
tihaz de Desfase Escalonado para el Control de un Array de Antenas,” in XXVI
Simmposium Nacional de la Union Cientıfica Internacional de Radio - URSI 2011,
Leganes, Spain, Sep. 2011.
• J. Garcıa-Gasco Trujillo, M. Arias Campo, I. Montesinos Ortego, M. Sierra Perez.
”Diseno del modulo T/R de la antena GEODA-GRUA,” in XXV Simmposium
Nacional de la Union Cientıfica Internacional de Radio - URSI 2010, Bilbao,
Spain, Sep. 2010.
144
Appendix A
Space Situational Awareness
Phased Array Radar Study
Two different deployment strategics of the SSA phased array antenna radar have been
evaluated, considering assumptions listed in Table A.1.
Table A.1: SSA Phased Array Radar AssumptionsParameter Value
Frequency Band 1.2 GHzNumber of Transmitter Arrays 6Transmitter Array Shape Rectangular ArrayNumber of Receiver Arrays 3Receiver Array Shape Circular ArrayField of Regard
A Deflection Angle from -60o to +60o
B Deflection Angle from +20o to +40o
Minimum Radar Cross Section dmin = max
(h2ph2refdref , 5 cm
)where href = 2000 Km, dref = 32 cm
Detection Probability 98 %Signal to Noise Ratio 18.45 dBPeak Power per Transmitter 1 kWReceiving Antenna Area Twice the Transmitting Antenna AreaPhased Array Antenna Gain G = 4π
λ2Aeff
System Noise Temperature 152.7 KTotal System Losses 3.13 dB
Case 1 considers the radar as an integration of three identical triplets integrated by
145
APPENDIX A. SPACE SITUATIONAL AWARENESS PHASED ARRAY RADARSTUDY
two transmitter antennas and one receiver antenna. Each triplet should cover the whole
specified FoR. Hence, once one triplet is built and verified, the other two would be a
copy of the tested one. This strategy provides a good behavior since the first triplet is
built, which does not fulfill the entire requirements but give a significantly approach.
Its main drawback is that the system would be oversized when the three triplets were
installed, increasing the cost of the whole architecture.
Case 2 evaluates the implementation of the whole radar by designing each triplet ad-
hoc to its associated FoR, optimizing each triplet individually. This would be cheaper,
because there would be much less radiating elements. Its main drawback is that this
strategy is much more risky because three different triplet should be designed and built.
Table A.2 presents the results in terms of number of elements per transmission and
reception arrays for cases 1 and 2. It is important to remark that the best solution
for both cases requires a maximum pulse width of 2.74 ms with 1kW of peak power.
Nowadays, European technology is able to provide 1 kW of peak power within a 1
ms maximum time pulse width. Hence, European technology limits this phased array
optimization. Considering European technology limitations (maximum pulse width of 1
ms with 1kW of peak power), case 2 has also been studied and shown in Table A.2 as
Case 2’; showing the need of a strong research on transmitters with higher peak power
and wider pulses, in order to reduce system cost.
Table A.2: Number of Elements per Transmission and Reception ArraysCase NElements Tx NElements Rx SNRWorstCase
1 23446 29683 18.45 dB2 34452 44778 18.51 dB2’ 48204 62622 18.52 dB
Worst Case Scenario Phased Array Simulation
After designing the full phased array antenna, its performance must be verified. To that
end, the worst case scenario for case 1 strategy is evaluated by using Matlab tool available
at ESA-ESOC. To simulate the case under study, it is specified: signal characteristics,
transmitter/receiver properties, radiation propagation effects, and target skills.
Firstly an LFM pulse signal is generated, RF beamformed, and emitted by the
transmitter. Part of the transmitted signal is reflected by the target, and detected by the
receiver antenna. Once received signal is RF beamformed, the IQ data is obtained. This
IQ data is introduced into the matched filter, which is a replica of the transmitted pulse
146
waveform. The matched filter output signal would show maximum peaks that could be
related to the possible detected targets. If pulse integration technic is activated; pulses
would be summed coherently, enhancing SNR ratio. Then, the data flow is treated by
the CFAR process that consists of three parts: hits detection with CFAR algorithm to
select possible targets, hits association to different targets to determine real targets, and
target coordinates estimation to locate the target with monopulse processing. Finally,
targets are detected and located.
After simulation, the system under study detects the target with a good location
accuracy; as shown Matlab simulation results presented in Table A.3. Such a great
angular accuracy is obtained thanks to the phased array narrow beam patterns, as
shown in Fig. A.1.
Table A.3: Phased Array Antenna Radar AccuracyReal Target Detected Target Accuracy
Azimuth [deg] 154.1500 154.1158 0.0342Elevation [deg] 43.3400 43.3152 0.0248Range [Km] 1460.0324 1460.000 0.0324
0.8
0.4
-0.4
-0.8
-0.8 -0.4 0.4 0.8U
V
(a) Transmitter Radiation Pattern
0.8
0.4
0
-0.4
-0.8 -0.4 0.4
V
(b) Receiver Radiation Pattern
Figure A.1: Phase Array Radiation Pattern.
147
APPENDIX A. SPACE SITUATIONAL AWARENESS PHASED ARRAY RADARSTUDY
148
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