MOEL 113LOW- NOISE

PREAMPLIFIER

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BEFORE OPERATING INSTRUMENT

NG AND SERVICE MANUAL

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MODEL 113 LOW- NOISE

PREAMPLIFIER

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OPERATING AND SERVICE MANUAL

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MODEL 113 LOW-NOISE

PREAMPLIFIER

OPERATING AND INSTRUCTION MANUAL

(;;n~EGc..G PRINCETON APPLIED RESEARCH

Copyright © 1983 EG&G PRINCETON APPLIED RESEARCH Printed In U.S.A.

SHOULD YOUR EQUIPMENT REQUIRE SERVICE WARRANTY

A. Contact the factory (609/452-2111) or your local factory EG&G PRINCETON APPLIED RESEARCH warrants each in-representative to discuss the problem. In many cases it strument of its manufacture to be free from defects in material Qwill be possible to expedite servicing by localizing the and workmanship. Obligations under this Warranty shall beproblem to a particular plug-in circuit board. limited to replacing, repairing or giving credit for the purchase

price, at our option, of any instrument returned, freightB. If it is necessary to send any equipment back to the fac- prepaid, to our factory within ONE year of delivery to the

tory, we need the following information. original purchaser, provided prior authorization for such returnhas been given by our authorized representative.

(1) Model number and serial number.This Warranty shall not apply to any instrument which our in-

(2) Your name (instrument user). spection shall disclose to our satisfaction, has become defec-tive or unworkable due to abuse, mishandling, misuse, acci-

(3) Your address. dent, alteration, negligence, improper installation or othercauses beyond our control. Instruments manufactured by

(4) Address to which instrument should be returned. others, and included In or supplied with our equipment, are notcovered by this Warranty but carry the original manufacturer’s

(5) Your telephone number and extension. warranty which is extended to our customers and may be morerestrictive. Certain subassemblies, accessories or com-

(6) Symptoms (in detail, including control settings). ponents may be specifically excluded from this Warranty, inwhich case such exclusions are listed in the Instruction

(7) Your purchase order numberfor repair charges (does Manual supplied with each instrument.not apply to repairs in warranty).

We reserve the right to make changes in design at any time(8) Shipping instructions (if you wish to authorize ship- without incurring anyobligation to install same on units

ment by any method other than normal surface previously purchased. 1

transportation).THERE ARE NO WARRANTIES WHICH EXTEND BEYOND THE

C. U.S. CUSTOMERS—Ship the equipment being returned DESCRIPTION HEREIN. THIS WARRANTY IS IN LIEU OF, ANDto: EXCLUDES ANY AND ALL OTHER WARRANTIES OR REPRE-

SENTATIONS, EXPRESSED, IMPLIED OR STATUTORY, IN-EG&G PRINCETON APPLIED RESEARCH CLUDING MERCHANTABILITY AND FITNESS, AS WELL AS7 Roszel Road ANY AND ALL OTHER OBLIGATIONS OR LIABILITIES OF(Off Alexander Road, East of Route 1) EG&G PRINCETON APPLIED RESEARCH, INC_UDING, BUTPrinceton, New Jersey NOT LIMITED TO, SPECIAL OR CONSEQUENTIAL DAMAGES.

NO PERSON, FIRM OR CORPORATION IS AUTHORIZED TOD. CUSTOMERS OUTSIDE OF U.S.A.—To avoid delay in ASSUME FOR EG&G PRINCETON APPLIED RESEARCH ANY D

customs clearance of equipment being returned, please ADDITIONAL OBLIGATION OR LIABILITY NO“ EXPRESSLYcontact the factory or the nearest factory distributor for PROVIDED FOR HEREIN EXCEPT IN WRITING DULY EXE-complete shipping information. CUTED BY AN OFFICER OF EG&G PRINCETON APPLIED

RESEARCH.E. Address correspondence to:

EG&G PRINCETON APPLIED RESEARCHP. O. Box 2565Princeton, NJ 08540

Phone: 609/452-2111TELEX: 84 3409

3

SHOULD YOUR EQUIPMENT REQUIRE SERVICE

A. Contact the factory (609/452·2111) or your local factory representative to discuss the problem. In many cases it will be possible to expedite servicing by localizing the problem to a particular plug·in circuit board.

B. If it is necessary to send any equipment back to the fac· tory, we need the following information.

(1) Model number and serial number.

(2) Your name (instrument user).

(3) Your address.

(4) Address to which instrument should be returned.

(5) Your telephone number and extension.

(6) Symptoms (in detail, including control settings).

(7) Your purchase order number for repair charges (does not apply to repairs in warranty).

(8) Shipping instructions (if you wish to authorize ship· ment by any method other than normal surface transportat ion).

C. U.S. CUSTOMERS-Ship the equipment being returned to:

EG&G PRINCETON APPLIED RESEARCH 7 Roszel Road (Off Alexander Road, East of Route 1) Princeton, New Jersey

D. CUSTOMERS OUTSIDE OF U.SA-To avoid delay in customs clearance of equipment being returned, please contact the factory or the nearest factory distributor for complete shipping information.

E. Address correspondence to:

EG&G PRINCETON APPLIED RESEARCH P. O. Box 2565 Princeton, NJ 08540

Phone: 609/452·2111 TELEX: 84 3409

WARRANTY

EG&G PRINCETON APPLIED RESEARCH warrants each in-strument of its manufacture to be free from defects in material ~ and workmanship. Obligations under this Warranty shall be limited to replacing, repairing or giving credit for the purchase price, at our option, of any instrument returned, freight prepaid, to olJr factory within ONE year of delivery to the original purchaser, provided prior authorization for such return has been given by our authorized representative.

This Warranty shall not apply to any instrument which our in· spection shall disclose to our satisfaction, has become defec· tive or unworkable due to abuse, mishandling, misuse, acci· dent, alteration, negligence, improper installation or other causes beyond our control. Instruments manufactured by others, and included in or supplied with our equipment, are not covered by this Warranty but carry the original manufacturer's warranty which is extended to our customers and may be more restrictive. Certain subassemblies, accessories or com­ponents may be specifically excluded from this Warranty, in which case such exclusions are listed in the Instruction Manual supplied with each instrument.

We reserve the right to make changes in design at any time without incurring any obligation to install same on units previously purchased.

THERE ARE NO WARRANTIES WHICH EXTEND BEYOND THE DESCRIPTION HEREIN. THIS WARRANTY IS IN LIEU OF, AND EXCLUDES ANY AND All OTHER WARRANTIES OR REPRE· SENTATIONS, EXPRESSED, IMPLIED OR STATUTORY, IN· ClUDING MERCHANTABILITY AND FITNESS, AS WELL AS ANY AND ALL OTHER OBLIGATIONS OR LIABILITIES OF EG&G PRINCETON APPLIED RESEARCH, INCLUDING, BUT NOT LIMITED TO, SPECIAL OR CONSEQUENTIAL DAMAGES. NO PERSON, FIRM OR CORPORATION IS AUTHORIZED TO ASSUME FOR EG&G PRINCETON APPLIED RESEARCH ANY ~ ADDITIONAL OBLIGATION OR LIABILITY NOT EXPRESSLY PROVIDED FOR HEREIN EXCEPT IN WRITING DULY EXE-CUTED BY AN OFFICER OF EG&G PRINCETON APPLIED RESEARCH.

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TABLE OF CONTENTS

r Section Page

CHARACTERISTICS 1-1 1:1 Introduction 1-1 1.2 Specifications 1-1

II INITIAL CHECKS 11-1 2.1 Introduction 11·1 2.2 Equipment Needed 11·1 2.3 Procedure 11-1

III OPERATING INSTRUCTIONS 111-1 3.1 I ntrodu cti on 111-1 3.2 Noise and Source Resistance 111-1 3.3 Grounding 111-2 3.4 Signal Voltage and Gain 3.5 Dc Zero Adjustment 111-2 3.6 Overload Fast Recovery 111-3 3.7 Low-Pass/High·Pass Filters 111-3 3.8 Single-Ended/Differential Operation 111-3 3.9 Common-Mode Rejection and Dc Zero Adjustments 111-4 3.10 Maximum Input Signal Consistent with Linear Operation 111-4 3.11 Battery Operation, Test, and Charging 111·5 3.12 Rack Mounting 111-5 3.13 Using a Signal Input Transformer 111·6 3.14 Use of the Model 113 in Bio-Medical Applications 111-12

,...,.. IV . CIRCUIT DESCRIPTION IV-l 4.' Block Diagram Discussion IV-l

4.1A Input Coupling Circuit IV-1 4.1B Ground·Loop Suppression IV-1 4.1C Gain Determination IV-1 4.10 Rolloff Filter Circuit IV-' 4.1 E Overload Fast-Recovery Circuit IV-2 4.1 F Power Supply IV-2

4.2 Circuit Descriptions IV-2 4.2A Differential Preamplifier (A 1) IV-2 4.2B Output Amplifier (A2) IV-3 4.2C Power Supply Circuit IV-3 4.2D Battery Test Circuit IV-3

V ALIGNMENT PROCEDURE V-l 5.1 Introduction V-l 5.2 Preliminary V·l 5.3 Equipment Needed V·1 5.4 A2 FET Gate Source Zero Adj. V·1 5.5 Common-Mode Rejection Adj. V-l 5.6 Gain Calibration V-' 5.7 Low Frequency Rolloff Compensation V-2 5.8 High Frequency Rolloff Compensation V·2 5.9 Battery Test Calibrate V-2

VI TROUB LESHOOTI NG VI-l 6.1 Introduction VI-l 6.2 Procedure VI·' ,.. 6.3 Printed Circuit Soldering VI·l

\,,~ VII SCHEMATICS V 11-'

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VI-1

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FIGURES

ypical Recovery Time vs Low Frequency Rolloff . . . '

_P Filter Normalized Amplitude Transfer Curve . . .

HP Filter Normalized Amplitude Transfer Curve . . .

_P/HP Filter Normalized Phase Transfer Curve . . .

Typical Common Mode Rejection Characteristics . . . . . . . . . . .

Vlaximum Differential Input to Model 113 . . . . . . . . . . . . . . .

Vlodifying the AM-1 Transformer for Use with the Model 113 Preamplifier . . .

Frequency Response of Typical Model AM-1 Transformer . . . . . . . . .

Noise Figure Contours for Typical Model AM-1 Transformer . . . . . . .

Schematic of Model AM-1 Transformer (Unmodified) . . . ' .

Photographs of Model AM-1 Transformer . . . . . . . . .

Frequency Response of Typical Model AM-2 Transformer . . . .

Noise Figure Contours for Typical Model AM-2 Transformer . . .

Model AM-2 Schematic, Turns Ratio 1:100 . . . . . . . . .

Phot0ofModelAM-2 ................ .

Frequency Response of Typical Model 190 Transformer . .

Noise Figure Contours for Typical Model 190-113 System . . .

Ground-Loop Current Path . . IVSolder Removal byWicking . . VI1

..Vl1

Typical Noise Figure Contours for the Model 113 . . ll 1 , Dll-3II4II4ll-4II4

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Model190Schematic ............... ..lll-10Photograph of Model 190 Transformer . . . . Ill-10B-H Curve & Waveform . . . . . . . . . Ill-10Degaussing Waveforms . . . . . Ill-11

Number

1-1 1-2 1-3 1-4 1-5 1-6 1-7 1-8 1-9A 1-98 1-10 1-11 1-12A 1-128 1-13 1-14 1-15 1-16

11-17 11-18 11-19 11-20 V-l

VI-l

FIGURES

Typical Noise Figure Contours for the Model 113 Typical Recovery Time vs Low Frequency Rolloff LP Filter Normalized Amplitude Transfer Curve HP Filter Normalized Amplitude Transfer Curve LP/HP Filter Normalized Phase Transfer Curve Typical Common Mode Rejection Characteristics Maximum Differential Input to Model 113 Modifying the AM-l Transformer for Use with the Model 113 Preamplifier Frequency Response of Typical Model AM-l Transformer . Noise Figure Contours for Typical Model AM-l Transformer Schematic of Model AM-l Transformer (Unmodified) Photographs of Model AM-l Transformer ....... . Frequency Response of Typical Model AM-2 Transformer . Noise Figure Contours for Typical Model AM-2 Transformer Model AM-2 Schematic, Turns Ratio 1: 100 ..... Photo of Model AM-2 . . . . . . . . . . . . . . . Frequency Response of Typical Model 190 Transformer Noise Figure Contours for Typical Model 190-113 System Model 190 Schematic . . . . . . . Photograph of Model 190 Transformer B-H Curve & Waveform Degaussing Waveforms . . Ground-Loop Current Path Solder Removal by Wicking

• Page

111-' ~. 1-3 1-4 1-4 1-4

I 1-4 I 1-5 I 1-6 I 1-6 I 1-6 111-7 111·7 111-8 111-8 111-8 111-9 111-9 111-9

111-10 111-10 111-10 111-11 IV-l VI-l

. VI-l

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EIOI.I.ON M.EI=IVS

SAFETY NOTICE (Read Before Operating Instrument)

A. INTRODUCTION The Model 113 to which this instruction manual applies has been supplied in a safe condition. This manual contains some information and warn­ings that have to be followed by the user to ensure safe operation and to retain the instrument in a safe condition.

The described apparatus has been designed for indoor use.

B. INSPECTION Newly received apparatus should be inspected for shipping damage. If any is noted, notify EG&G PARC and file a claim with the carrier. Be sure to save the shipping container for inspection by the carrier.

WARNING! THE PROTECTIVE GROUNDING COULD BE RENDERED INEFFECTIVE IN DAMAGED Ap· PARATUS. DAMAGED APPARATUS SHOULD NOT BE OPERATED UNTIL ITS SAFETY HAS BEEN VERIFIED BY QUALIFIED SERVICE PER­SONNEL. DAMAGED APPARATUS WAITING FOR SAFETY VERIFICATION SHOULD BE TAGGED TO INDICATE TO A POTENTIAL USER THAT IT MAY BE UNSAFE AND THAT IT SHOULD NOT BE OPERATED.

C. SAFETY MECHANISM As defined in IEC Publication 348 (Safety Require­ments for Electronic Measuring Apparatus), the Model 113, when operated from the ac line, is Class I apparatus, that is, apparatus that depends on connection to a protective conductor to earth ground for equipment and operator safety. Before any other connection is made to the apparatus, the protective connection is made via the earth ground prong of the power cord plug. The power cord plug shall only be inserted in a socket outlet provided with the required earth ground contact. The protective action must not be negated by the use of an extension cord without a protective con­ductor, by use of an "adapter" that doesn't main­tain earth ground continuity, or by any other means.

WARNING! ANY INTERRUPTION OF THE PROTECTIVE CON­DUCTOR INSIDE OR OUTSIDE THE APPRATUS OR DISCONNECTION OF THE PROTECTIVE EARTH TERMINAL MAY MAKE THE APPARATUS DANGEROUS. INTENTIONAL INTERRUPTION IS PROHIBITED.

The power cord plug provided is of the type illus­trated in Figure 1. If the provided plug is not com­patible with the available power sockets, the plug or power cord should be replaced with an approv­ed type of compatible design.

WARNING! IF IT IS NECESSARY TO REPLACE THE POWER CORD OR TH E POWER CORD PLUG, TH ERE· PLACEMENT CORD OR PLUG MUST HAVE THE SAME POLARITY AS THE ORIGINAL. OTHER­WISE A SAFETY HAZARD FROM ELECTRICAL SHOCK, WHICH COULD RESULT IN INJURY OR DEATH, MIGHT RESULT.

When operated from its internal battery with the line cord disconnected, the Model 113 could be considered Class III apparatus, that is, apparatus in which protection against electric shock relies on supply at safety extra-low voltage (SELV) and in which voltages higher than those of SELV are not generated. When operated battery powered and with the line cord disconnected, the voltage levels inside the Model 113 will nofexceed ± 12 V. This does not take into account the possibility of higher voltages being applied via the signal input or output cables.

D. POWER VOLTAGE SELECTION Before plugging in the power cord, make sure that the instrument is set for operation from the voltage of the ac power supply.

CAUTION! THE APPRATUS DESCRIBED IN THIS MANUAL MAY BE DAMAGED IF IT IS SET FOR OPERATION FROM 110 V AC AND TURNEDON WITH 220 V AC APPLIED TO THE POWER INPUT CONNECTOR.

The line voltage is selected by means of a rear· panel switch. FOR SAFETY, UNPLUG THE

E

L

L= LINE OR ACTIVE CONDUCTOR (ALSO CALLED "LIVE" OR "HOT")

N =NEUTRAL OR IDENTIFIED CONDUCTOR

E = EARTH OR SAFETY GROUND

Figure 1. POWER CORD PLUG WITH POLARITY INDICATIONS

POWER CORD WHEN CHANGING THE LINE with normal heart functioning. However, recentVOLTAGE SETTING. Depend'ng on the switch research has shown that dangerexists at far lowerposition, either “115” or “230” (both are printed on current levels than was previously suspected. Asthe switch) will be visible to the operator. For a consequence of this increased awareness, andoperation from a line voltage of nominally 115 V after a careful analysis of the Model 113 design,ac, the switch should be set so that “115” shows. EG&G Princeton Applied Research CorporationFor operation from a line voltage of nominally feelsthat it cannot recommend the Model 113for230 V ac, “23O” should show. use in applications involving human subjects or

patients. In certain situations involving specificconditions of grounding, internal component

E. LINE FUSE failure, or excessive common-mode input, theThe Model 113 line fuse is located inside the in- high input impedance of the Model 113 could failstrument. To check or replace the fuse, it is first and potentially dangerous currents could flownecessary to remove the top cover and also the through the subject.shield mounted on the inside of the rear panel.The fuse should be a slow-blow type rated at However, the reader should not get the impres-either 1/16 A (115 V Operation) or 1/32 A (230 V sion that the Model 113 is in any wayadangerousoperation). The voltage rating should be 125 V or instrument to use in ordinary applications. Thosehigher in the Case 01 115 V Operation and 250 V or characteristics that necessitate the advisoryhiélherththe eeee Qt 230V0DeFeti0i1-9h|YeBU$$ against the instrument’s use in bio-medical ap-MDL OF equh/eteht thee Sheuld be USed- plications with humans are common to most other

preamplifiers as well. In fact, with its low internalwA|=tNiN(;i supply voltages, capability for internal battery

TO AVOID THE POSSIBILITY o|= A SAFETY HAZ- power with epinpieie independence of the ep line.ARD FRQM E|_ECTR|CA|_ SHQCK wi-ii(3i-i (3QUi_|3 and extremely high input impedance under normalREsui_T |N INJURY OR DEATH, |)|$(;()Ni\|EcT operating conditions, the Model 113 is probablyTHE PQWER CORD BEFQRE REM()V|NG QR |i\|- one of the safest preamplifiers available for$"i'Ai_i_|N(3 A FU$E_ i3E(;Ati$E QF Ti-ii; PQTEN- general use. For all practical purposes, it can beT|A|_ HAZARD, Ti-ii; FUSE Si-|()U|_[) BE CHECKED considered to be completely harmless. The maxi-AND/OR CHANGED BY A QUALIFIED SERVICE mum internei Supply vpitepee eppiied tp the em-"|'E(3i-i|\ii(3iAN ()Ni_Y_ plifiers are only i 12 V. Even these low voltages

can only appear at the input under very specificA prooeoure for geinino eooeee to the fuse operating conditions, and then generallyforonlyafollows. few milliseconds. A person inadvertently touching

the input under these conditions would, in(1) Remove the top oover_ it is eeoureo by e general, not even be aware that there was any

single screw on the bottom surface ofthetop- Vettege there at ett ehd hY he etfeteh Qt the im-oover “tip” et the reer of the inetrument_ with agination could the operator of the instrument bethe screw removed, the cover simply slides ie9eTded ee hethg ih ehY dehgehback to where it can be freed from the instru-ment_ The preamplifier can be used in biological appli-

cations involving animal subjects. However, if the(2) Remove the shield attached to the inside of eppiieeiipn ie pne in whieh ekin reeieienee is

the rear panel. This shield is secured by a dreetivredueed prbvpeeeed.tne pperetprie advis-einoie eorew at its oenter_ with the ehieio ed to observe the following recommendations ifremoveo, the iuee hoioer, iooeteo oireotiy unnecessary risk to the experimental animal istoabove the Line Voltage Selector switch, he evetdetibecomes accessible. 1

(1) Turn the amplifier power on BEFORE making(3) After oheokino eno, it eppropriete, ohenging any connections to the experimental animal.

the fuse, remount the shield and top coverbefore plugging in the line cord and operating (2) set the thput Ceuhtthg ewttehee 01 the Medetthe inetrument_ 113 to GND before making any connections to

the experimental animal. Do not transfer fromthe GND settings until after the connectionsare completed.

F. USE OF THE MODEL 113 IN 1

BIO-MEDICAL APPLICATIONS (3) Do not turn the power switch on or off whileIn the past few years, safety in bio-medical ap- the instrument is connected to the experi-plications has been a matter of growing concern mental animal.to both the users and suppliers of electronicsequipment. It has long been known that electrical It may prove helpful to consider the reason forcurrents passing through the heart can interfere these precautions. By understanding them, the

3

—_---up

POWER CORD WHEN CHANGING THE LINE VOLTAGE SETTING. Depending on the switch position, either "115" or "230" (both are printed on the switch) will be visible to the operator. For operation from a line voltage of nominally 115 V ac, the switch should be set so that "115" shows. For operation from a line voltage of nominally 230 V ac, "230" should show.

E. LINE FUSE The Model 113 line fuse is located inside the in­strument. To check or replace the fuse, it is first necessary to remove the top cover and also the shield mounted on the inside of the rear panel. The fuse should be a slow-blow type rated at either 1/16 A (115 V operation) or 1/32 A (230 V operation). The voltage rating should be 125 V or higher in the case of 115 V operation and 250 V or higher in the case of 230 V operation. Only a BUSS MDL or equivalent fuse should be used.

WARNING! TO AVOID THE POSSIBILITY OF A SAFETY HAZ­ARD FROM ELECTRICAL SHOCK WHICH COULD RESULT IN INJURY OR DEATH, DISCONNECT THE POWER CORD BEFORE REMOVING OR IN­STALLING A FUSE. BECAUSE OF THE POTEN­TIAL HAZARD, THE FUSE SHOULD BE CHECKED ANDIOR CHANGED BY A QUALIFIED SERVICE TECHNICIAN ONLY.

A procedure for gaining access to the fuse follows.

(1) Remove the top cover. It is secured by a Single screw on the bottom surface of the top­cover "lip" at the rear of the instrument. With the screw removed, the cover simply slides back to where it can be freed from the instru­ment.

(2) Remove the shield attached to the inside of the rear panel. This shield is secured by a Single screw at its center. With the shield removed, the fuse holder, located directly above the Line Voltage Selector switch, becomes accessible.

(3) After checking and, if appropriate, changing the fuse, remount the shield and top cover before plugging in the line cord and operating the instrument.

F. USE OF THE MODEL 113 IN BIO·MEDICAL APPLICATIONS

In the past few years, safety in bio-medical ap­plications has been a matter of growing concern to both the users and suppliers of electronics equipment. It has long been known that electrical currents passing through the heart can interfere

with normal heart functioning. However, recent research has shown that danger exists at far lower current levels than was previously suspected. As a consequence of this increased awareness, and after a careful analysis of the Model 113 deSign, EG&G Princeton Applied Research Corporation feels that it cannot recommend the Model 113 for use in applications involving human subjects or patients. In certain situations involving specific conditions of grounding, internal component failure, or excessive common-mode input, the high input impedance of the Model 113 could fail and potentially dangerous currents could flow through the subject.

However, the reader should not get the impres­sion that the Model 113 is in any way a dangerous instrument to use in ordinary applications. Those characteristics that necessitate the adviSOry against the instrument's use in bio-medical ap­plications with humans are common to most other preamplifiers as well. In fact, with its low internal supply voltages, capability for internal battery power with complete independence of the ac line, and extremely high input impedance under normal operating conditions, the Model 113 is probably one of the safest preamplifiers available for general use. For all practical purposes, it can be considered to be completely harmless. The maxi­mum internal supply voltages applied to the am­plifiers are only ± 12 V. Even these low voltages can only appear at the input under very specific operating conditions, and then generally for only a few milliseconds. A person inadvertently touching the input under these conditions would, in general, not even be aware that there was any voltage there at all and by no stretch of the im­agination could the operator of the instrument be regarded as being in any danger.

The preamplifier can be used in biological appli­cations involving animal subjects. However, if the application is one in which skin resistance is greatly reduced or bypassed, the operator is advis­ed to observe the following recommendations if unnecessary risk to the experimental animal is to be avoided.

(1) Turn the amplifier power on BEFORE making any connections to the experimental animal.

(2) Set the Input Coupling switches of the Model 113 to GND before making any connections to the experimental animal. Do not transfer from the GND settings until after the connections are completed.

(3) Do not turn the power switch on or off while the instrument is connected to the experi­mental animal.

It may prove helpful to consider the reason for these precautions. By understanding them, the

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operator may be better able to safely carry out electrical monitoring of experimental animals, not only where the input amplifier is the Model 113, but where other preamplifiers are used as well.

(1) Turn-On Transients

When the amplifier is first turned on, all cir­cuits do not instantly assume their quiescent operating state. Instead, a finite time is re­quired for the common-mode loop amplifier to set the input stages to their proper operat­ing point. During this interval (which varies from a few milliseconds to a second or more depending on the source impedance), the source-gate junction of one input transistor or the other is forward-biased. In this state, the transistor does not exhibit a high im­pedance, but instead appears as a low im­pedance from the input of the instrument to the output of the common-mode amplifier.

(2) Power Transformer

The power transformer in the Model 113 is of very high quality and is unlikely to fail during the life of the instrument. Nevertheless, the possibility of such a failure, however remote, must be considered. Should a short develop, and if the instrument were being used with in­complete or improper ground returns (com­mon in many buildings and installations), a dangerous situation would exist.

(3) Internal Component Failure

The input transistors of the Model 113 are junction-type field-effect transistors. Al­though they exhibit an extremely high input resistance when properly biased, their resis­tance can drop to a few ohms if their operat­ing current or bias is out of the normal operat­ing range sufficiently to give a simple forward biased diode junction from the gate to either the source or the drain. There are several possible internal component failures which, though unlikely, could bring about this condi­tion. Should it occur, the input of the ampli­fier would be connected through a low im­pedance directly to the instrument's power supply.

(4) Excessive Common-Mode Input

As stated in the specifications, the common­mode input limit of the Model 113 is 1 V rms. Higher levels "turn on" low conduction paths at the input of the preamplifier to protect the input circuits, and thereby lower the input im­pedance.

Again, it should be emphasized that, even though EG&G Princeton Applied Research Corporation does not recommend the Model 113 for use with human subjects, its use in all other applications is recommended without reservation.

G. VENTILATION With a power consumption of only 5 watts when operated from the ac line, and even less when bat­tery operated, the Model 113 does not have any special ventilation requirements. It can be operated on a bench or in a rack (rack mounting kits can be purchased from the factory), the only constraint being that the ambient temperature be in the range of 15°C to 45 °C.

H. DEFECTS AND ABNORMAL STRESSES

Whenever it is likely that the protection provided by the connection to earth ground has been im­paired, the apparatus shall be made inoperative and secured against any unintended operation. The protection is likely to be impaired if, for exam­ple, the apparatus:

(1) Shows visible damage,

(2) Fails to perform the intended measurements,

(3) Has been subjected to prolonged storage under unfavorable conditions,

(4) Has been subjected to severe transport stresses.

Such apparatus should not be used until its safety has been verified by qualified service personnel.

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SECTION I

CHARACTERISTICS

1.1 INTRODUCTION

The Model 113 Low-Noise Preamplifier provides high gain, low noise amplification of wideband signals from dc to 300 kHz. Adjustable high and low frequency rolloffs allow the bandwidth to be reduced. Two inputs, with individual coupling switches, allow either differential or single-ended operation. Calibrated gain is switch selectable from x10 to X104 in a 1·2-5 sequence, and an uncalibrated gain vernier provides x1 to x2.5 range expansion.

The unit may be powered either from the ac line or from its own batteries. The nickel-cadmium batteries recharge automatically during line operation.

Other features include an overload fast-recovery switch, special circuitry that reduces the effects of ground-loop currents, front-panel dc zeroing and common mode rejec­tion screwdriver controls, and battery test provisions.

The Model 113 is well suited for use as a preamplifier for other Princeton Applied Research signal processing instru­ments.

1.2 SPECIFICATIONS

(1) INPUTS

Two channels, each with a three position switch to provide for ac or dc coupled, single-ended or differen­tial operation. I nput connectors are BNC type.

/

\-1

(2) INPUT IMPEDANCE

(a) Ac coupled: through 0.1 J.1F, shunted to ground with 100 megohms and 15 pF in parallel.

(b) Dc coupled: 1 gigohm, shunted by 15 pF.

(3) MAXIMUM INPUT WITHOUT DAMAGE

(a) Dc coupled: Common-Mode, ±10 V; Differen­tial, ±7.5 V.

(b) Ac coupled: coupling capacitors can withstand 200 V. Transients which pass through coupling capacitors cannot exceed dc coupled operation limits.

(4) MAXIMUM INPUT SIGNAL CONSISTENT WITH LINEAR OPERATION (see Subsection 3.10)

(a) Common mode: 1 V rms.

(b) Differential mode (gains of 10 to 100): ±500 mY.

(c) Differential mode (gains of 200 through 10 k): ±50 mY.

(5) COMMON MODE REJECTION (11) OUTPUT VOLTAGE

FREQUENCY FOR GAIN > 200 FOR GAIN < 200 10 volts pk-pk ahead of 600 ohms.

dc to 100 Hz 120 dB (min) 100 dB (min) (12) OUTPUT IMPEDANCE1 kHz 100 dB 80 dB

10 kHz 80 dB 60 dB 600 ohms.100 kHz 60 dB 40 dB

(13) OVERLOAD RECOVERY

(6) GA|N Resets immediately with spring-loaded front-paneltoggle. See Figure Ill-2 for characteristic recovery

x10 to x104 calibrated gain settings. Accuracy of data-calibrated gains is i2% when gain vernier is in the (14) P()\/\/ER REQU|RE|\/|E|\|TScalibrate position. Gain vernier provides uncalibratedgain F8099 eXl3>an$i0n 01 LID ‘£0 X2-5(fT\ilmUm)- (a) Rechargeable nickel-cadmium batteries provide

approximately 30 hours operation bet\/veen(7) FREQUENCY RESPONSE charges. A front-panel, three-position, spring-

loaded toggle switch and test lamp permit test ofRolloff frequencies are switch selectable. Front panel each of the -[W0 in-[ema| bat-(erie5_switch markings indicate 3 dB point of 6 dB/octaverolloff curve. Rolloffs are selectable as follows: (b) AC |ine Operation; 195-125 \/ ac or 210-259 \/

ac, 50-60 Hz, 5 watts. Internal batteries will(8) I-OW FFBQUBHCVI d¢ P050100 and 0-03 HZ ‘E0 I recharge automatically while unit is connected to

kHz positions in 1-3-10 sequence. ac power line_

(b) High Frequency: 3 Hz to 300 kHz in 1-3-10 (15) DIMENSIONSsequence.

8.6" W x 4.1" H x11.3" D (21.8 cm x 10.4 cm x 28.7(8) NOISE cm).

At 10 Hz with a 2 megohm source impedance, noise (16) WEIGHTfigure is 0.3 dB maximum. At 1 kHz with a 1 megohmsource impedance, noise figure is 0.2 dB maximum. 4 pounds (1.8 kg).See Section Ill for further discussion and noise figurecontours. (17) ACCESSORIES

(9) DC DRIFT If the source impedance is less than 100 ohms, bestlow-noise performance will be obtained if a Model

(a) Referred to input (dc coupling): maximum 10 AM-1, AM-2, or 190 input transformer is used. Both‘I-IV/QC Or I688 than 10 /1V/24 hours at constant the AM-1 and the AM-2 have 1:100 turns ratios. Theambient temperature. A front panel screwdriver AM-1 has a 3 dB bandwidth Qf fr()m 1 kHz to 10 kHzcontrol provides for dc Zeroing. at 10 ohms source impedance, and the AM-2 has a

bandwidth of from 1 kHz to 150 kHz with a 1 ohm(bl Referred to Output: less than 1 mv/CC’ or less source. The Model 190 has a 1:10:100 turns ratio. The

than 1 mv/24 hours at Constant ambmnt tern‘ three dB bandwidth is from 0.25 Hz to 500 Hz with a

peratum 1 ohm source. See Section lll for further detailsregarding these transformers.

(10) DISTORTION Flanges are available for mounting on a single unit ortwo units side by side in a 19" relay rack. See

Typicaldistortion is less than 0.01%. Subsection III-12 for the part numbers of theseflanges.

I-2

(5) COMMON MODE REJECTION

FREQUENCY

dc to 100 Hz 1 kHz

10 kHz 100 kHz

(6) GAIN

FOR GAIN> 200

120 dB (min) 100 dB BOdB 60 dB

FOR GAIN < 200

100 dB (min) BO dB 60 dB 40 dB

x10 to X104 calibrated gain settings. Accuracy of calibrated gains is ±2% when gain vernier is in the calibrate position. Gain vernier provides uncalibrated gain range expansion of up to x2.5 (minimum).

(7) FREQUENCY RESPONSE

Rolloff frequencies are switch selectable. Front panel switch markings indicate ~ dB point of 6 dB/octave roll off curve. Rolloffs are selectable as follows:

(a) Low Frequency: dc position and 0.03 Hz to kHz positions in 1-3-10 sequence.

(b) High Frequency: 3 Hz to 300 kHz in 1-3-10 sequence.

(B) NOISE

At 10 Hz with a 2 megohm source impedance, noise figure is 0_3 dB maximum_ At 1 kHz with a 1 megohm source impedance, noise figure is 0.2 dB maximum_ See Section III for further discussion and noise figure contours.

(9) DC DRIFT

(a) Referred to input (dc coupling): maximum 10 "IlV/C or less than 10 IlV/24 hours at constant ambient temperature. A front panel screwdriver control provides for dc zeroing.

(b) Referred to output: less than 1 mV/C, or less than 1 mV/24 hours at constant ambient tem­perature.

(10) DISTORTION

Typical distortion is less than 0.01%.

1-2

(11) OUTPUT VOLTAGE

10 volts pk-pk ahead of 600 ohms.

(12) OUTPUT IMPEDANCE

600 ohms.

(13) OVERLOAD RECOVERY

Resets immediately with spring-loaded front-panel toggle. See Figure 111-2 for characteristic recovery data.

(14) POWER REQUIREMENTS

(a) Rechargeable nickel-cadmium batteries provide approximately 30 hours operation between charges. A front-panel, three-position, spring­loaded toggle switch and test lamp permit test of each of the two internal batteries.

(b) Ac line operation: 105-125 V ac or 210-250 V ac, 50-60 Hz, 5 watts. I nternal batteries will recharge automatically while unit is connected to ac power line.

(15) DIMENSIONS

B.6" W x 4.1" H x 11.3" D (21.B cm x 10.4 cm x 2B.7 cm).

(16) WEIGHT

4 pounds (1.B kg).

(17) ACCESSORIES

If the source impedance is less than 100 ohms, best low-noise performance will be obtained if a Model AM-1, AM-2, or 190 input transformer is used. Both the AM-1 and the AM-2 have 1: 100 turns ratios. The AM-1 has a 3 dB bandwidth of from 1 kHz to 10 kHz at 10 ohms source impedance, and the AM-2 has a bandwidth of from 1 kHz to 150 kHz with a 1 ohm source. The Model 190 has a 1: 1 0: 1 00 turns ratio. The three dB bandwidth is from 0.25 Hz to 500 Hz with a 1 ohm source. See Section III for further details regarding these transformers.

Flanges are available for mounting on a single unit or two units side by side in a 19" relay rack. See Subsection 111-12 for the part numbers of these flanges.

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S)lO3H3 'lVl.l.lNIll NOLLOHS

SECTION II

INITIAL CHECKS

2.1 INTRODUCTION

The following procedure is provided to facilitate initial performance checking of the Model 113. In general, the procedure should be performed after inspecting the instru­ment for shipping damage (any noted to be reported to the carrier and to Princeton Applied Research Corporation), but before using it experimentally. Should any difficulty be encountered in carrying out these checks, contact the factory or one of its representatives.

2.2 EQUIPMENT NEEDED

(1) General purpose laboratory oscilloscope.

(2) Signal generator capable of providing a 1 V pk-pk sinewave at 1 Hz, 100 Hz, and 1 kHz.

2.3 PROCEDURE

(1) Make sure the rear-panel slide switch is in the position indicating the line voltage to be used (115 V ac or 220 Vac).

(2) Plug the line cord into the rear of the instrument and into the power receptacle.

(3) Press the power switch so that it remains depressed.

(4) Push the spring-loaded battery test toggle to the left, then push it to the right. The green indicator should light for both positions.

(5) Make the following initial control settings:

(a) Gain: x10; Cal.: fully counterclockwise (turn until the switch "clicks").

11-1

(b) Coupling: A input AC, B input GND.

(c) Low Frequency Rolloff control: 1 Hz.

(d) High Frequency Rolloff control: 1 kHz.

(6) Connect the oscilloscope to the output BNC jack_

(7) Set the signal generator to 1 Hz, 1 V pk-pk, and connect it to the A input BNC jack. (Use the oscilloscope to make the signal generator amplitude settings, to obtain consistency between input settings and output readings.)

(8) Monitor the output; the output level should be 7 V pk-pk.

(9) Set the signal generator to 100 Hz, 1 V pk-pk. Monitor the output; the output level should be ten times the input level.

(10) Set the signal generator to 1 kHz, 1 V pk-pk. Monitor the output; the output level should be 7 V pk-pk.

(11) Press the OVL recovery button; the output should decrease to a low level, typically 50 mV. However, the absolute signal amplitude can vary considerably from unit to unit.

(12) Return the power switch to the OFF (out) position.

This completes the initial checks. If the instrument per­formed as indicated, one can be reasonably sure that it is operating properly.

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SNOl.I.3H.I.SNl 9NI.l.V!:l3dOIII NOLLOHS

SECTION III OPERATING INSTRUCTIONS

3.1 INTRODUCTION

To obtain optimum performance from the Model 113, care must be exercised in selecting the signal source impedance, in selecting the bandwidth, and in ground loop considera­tions, all of which are discussed below.

Fundamentally, the instrument is powered as required either from the self-contained batteries or from the ac line, and the signal to be ampl ified is applied to the input connector(s); the amplified signal is available at the output jack through a resistance of 600 ohms.

NOTE: Before operating from ac line power, make sure the rear-panel switch is in the position indicating the line voltage to be used, and be sure the proper size line fuse is installed (1/16 A for 115 V operation or 1/32 A for 230 V operation). Operating from too high a line voltage will blow the line fuse and possibly damage the power transformer and circuit components.

3.2 NOISE AND SOURCE RESISTANCE

Best amplifier performance is often regarded to be realized under those conditions where it least decreases the overall signal-to-noise ratio. In many instances the thermal noise generated by the signal source resistance is the dominant factor in determining the input signal-to-noise ratio. In this respect, amplifier noise performance can be specified by the amount of noise the amplifier adds to the amplified source thermal noise; expressed in decibels, this is called the "Noise Figure":

(1) Noise Figure =

20 I total rms noise voltage at the ampl ifier output 0910 gain x source thermal noise voltage (rms) dB

where the Source Thermal Noise = V4KTRl'lf volts rms = E, and

K = Boltzmann's constant, 1.38 x 10-23 joules/K T = absolute temperature in kelvins M = equivalent noise bandwidth in Hz R = source resistance in ohms (differential source

resistance for Model 113; if used single-ended, set the coupling selector for th.e unused input to ground, and regard this part of input resistance to be zero).

The total output noise may be converted to an equivalent input noise by dividing by the amplifier gain. The noise figure, expressed in these terms, becomes:

(2) Noise Figure =

20 I total rms noise voltage referred to amp. input dB 0910 source thermal noise voltage (rms)

II 1-1

Each ampl ifier has its own characteristic noise figure, wh ich varies as a function of frequency and source resistance. These figures are obtained experimentally, and plotted

graphically. Figure 111-1 is a typical set of noise figure contours for the Model 113.

30dB

--'_---l, 10 -1 10- 1 00 IO~ ~ IO~

FREQUfNr i .N Hz

Figure 111-1. TYPICAL NOISE FIGURE CONTOURS

FOR THE MODEL 113

In using these contours, the total equivalent rms input noise is usually the quantity of interest. This can be obtained from the graph and equation (3):

(3) Total equivalent rms input noise voltage = source thermal noise x antilog NF/20 volts rms

The equivalent noise bandwidth used in determining the source thermal noise is a function of the external circuitry and/or the amplifier bandwidth. When operating dc coupled (LF rolloff to DC), the equivalent noise bandwidth of the M113 is simply the HF rolloff frequency multiplied by 1T/2. If the LF rolloff frequency setting is other than dc, the equivalent noise bandwidth is given by the formula:

where: uted by the transformers, the results obtained using a

transformer hardly resemble the ideal theoretical results as

f2 is the setting of the HF Rolloff Control, and to use noise figure contours and amplitude transfer curves

ENB is the equivalent noise bandwidth in Hz, predicted in the example. When ug a transformer, it is best Qft is the setting of the LF Rolloff Control. obtained empirically for the individual transformer. Sub

section 3.11 contains such data for the transformers.

If the two frequency settings are far apart, the equivalentnoise bandwidth to a close approximation is simply 1r/2 33 GROUNDiNGtimes the HF rolloff frequency. '

_ The Model 113 is specifically desi ned to have a hi h de reeSup.hOSe_ one _ihtehded tO_ Operate the Modei its ih of immunity to the effects of gtiound-loop curretnts. itfhecon unction with t h . . - . .tm ted t 50 in expegmeh t att htisehts ahsoutlge signal ground side of the input connectors is connected to. p a _ O .0 ms’ ah Suppose i‘ 'S_ h_OWh t at t e chassis ground through a 10 ohm resistor. To maintaininformation re u edf th d b l . . . . .q ir rom e experiment is situate e ow

_ _ ground-loop immunity, avoid shorting the input grounds to3 S.ihCe. tits soutge tthetmet)hotgsegorhttiisutihe te_tt_he chassis ground at the amplifier end of the cables. To furtherbo ad _dOtirie. is, eheh deg Oh, ahh W|i_Ft 'nt ti amp iliet reduce the effects of ground-loop currents, use an input

an Wt is minimize ysettihet e to O Cohtto to cable that is short and has a high conductivity outerdc and the HF toiiott ‘?°"‘F'°' to 3 kH,Z' DC Coupling is used‘ conductor. (For a discussion of the circuit desi n with9h : . . . .T e source thetmai noise ih this Case is respect to grounding considerations, see Section IV).

E =\/4x1.38 >< 10-” X 2.9x 102x 50>< 3 X103X1.57= 6 i X to-s V rms CAUTION: The power rating of the 10 ohm resistor is %

i watt. Avoid excessive ground-to-ground current to avoidFrom Figure lll-1, the noise figure for the Model 113 at a burning out this reststtmcenter frequency of 1500 Hz and a source resistance of 50ohms is 18 dB. Substituting these values into equation (3): when the Signet is aepned to the input via a transformer,

totai equivaient input noise operate the amplifier single-ended. That is, place one inputZ 61 X to-s X ibis/20 selector to the ground position, and connect the trans-

eieev former to the other input (ac couple); connect onetransformer lead to the outer shell of the BNC connector

Occasionally the dc component is not required, so that the and eenneet the other transformer ieed to the Centerhest heise Dettetmehee eeh he 8Chie\/ed With the help 0t eh conductor of the connector. Connecting this way avoids theinput transformer. This is possible by taking advantage of nrebiem Qt etatie energe bui|d-up at tne inputs due te nothe property of a transformer to multiply the source greund return_resistance by the square of the turns ratio and the voltageby the ratio. With atransformer inserted between the signal 3_4 $|G|\|AL \/()|_TAGE AND GAINsource and the amplifier input we can increase the effectivesource resistance to a value that reduces the noise figure toless than 0.05 dB. From Figure lll-1, the source resistance With the Vetiehie 9eih eehttei ih the eeiihtated hesitiehshould be about 1 megohm. The transformer turns ratio, ieewii the hesitieh et the geih Seieetet eeetiteteiy Sets thetor this inibedanee inerease, is W: t40_ -|-herntai gain to the indicated level. Intermediate levels of gain maysource noise at the amplifier input is equal to the noise be ehteihed ieV use et the tiheeiibteteei Vetiehie Qeihgenerated by the 50 bhrn sbtiree inuitibiied by the turns control. If it is desired to accurately set an intermediateratio. With a noise figure near zero, the total equivalent rms ievei et geihl ephiy eh ihhtit Sighei to the ethpiitiet ihptitinput nbise is aisb edtiai to the nbise generated by the 50 and, using an ac voltmeter, proportionally adjust the outputdhrn sbtiree nitiitibiied by the turns ratio! I 70 tiv rrns_ signal level to a corresponding value between the levels ofAlthough the numerical value of equivalent input noise is the two tixed geih 5ettih95 hteeketihg the desired 9aih-much larger than before, the signal-to-noise ratio isisub-stantially increased. This can be seen by considering all ofthe transformed source signal voltage as appearing at the The maximum Output that the aihphtiet Cah provide is toamplifier input terminals, because the Model 113 input t/hits pea_k'tO'heak (through 600 Ohms ihto ah Opeh Circuit)"teeietenee is mueh ieteet than the 1 meeehm etesenteei by For maximum input voltages, refer to the specifications and

the transformer; the signal-to-noise ratio is equal to the to Suhsectioh 3'i0'maximum possible value: esig/E x antilog NF/20) E esie/E.In this example the transformer increases the signal-to-noiseratio by a factor of 8.

3.5 DC ZERO ADJUSTMENTPrinceton Applied Research Corporation manufacturestransformers for use in low level, low frequency applica- The dc zero adjustment may need to be touched Cip as thetions. Characteristics and details regarding the use of some Qeih is ehehgeti ih Dettietliet, it the ediustmeht is titst madeof these transformers are discussed in Subsection 3.11. Wheh 0Detetih9 at e i0W Qeih, t0ii0Wed ietet hV ttehstet teBecause the transformers have so much influence in high-Qeih Opetetiehi it is impetteht that the de Zero bedetermining bandwidth, and because of the noise contrib- Cheeked, ahd, it heeessetV. teedlusted as required-

lll-2

where:

ENB is the equivalent noise bandwidth in Hz, f2 is the setting of the HF Rolloff Control, and fl is the setting of the LF Rolloff Control.

If the two frequency settings are far apart, the equivalent noise bandwidth to a close approximation is simply 1T/2 times the HF rolloff frequency.

Suppose one intended to operate the Model 113 in conjunction with an experiment that presents a source impedance of 50 ohms, and suppose it is known that the information required from the experiment is situated below 1 kHz. Since the source thermal noise contributing to the total noise is dependent on bandwidth, the amplifier bandwidth is minimized by setting the LF rolloff control to dc and the HF rolloff cuntrol to 3 kHz. Dc coupling is used. The source thermal noise in this case is:

E =)4 x 1.38 x 10 23 x 2.9 x 10 2 X 50 x 3 x 10 3 x 1.57

= 6.1 x 10-8 V rms

From Figure 111-1, the noise figure for the Model 113 at a center frequency of 1500 Hz and a source resistance of 50 ohms is 18 dB. Substituting these values into equation (3):

total equivalent rms input noise = 6.1 X 10-8 X 101 8 / 20

= 0.5 pV rms

Occasionally the dc component is not required, so that the best noise performance can be achieved with the help of an input transformer. This is possible by taking advantage of th e property of a transforme r to multi ply the sou rce resistance by the square of the turns ratio and the voltage by the ratio. With a transformer inserted between the signal source and the amplifier input we can increase the effective source resistance to a val ue that reduces the noise figure to less than 0.05 dB. From Figure 111-1, the source resistance should be about 1 megohm. The transformer turns ratio, for this impedance increase, is VR2/R 1 = 140. Thermal source noise at the amplifier input is equal to the noise generated by the 50 ohm source multiplied by the turns ratio. With a noise figure near zero, the total equivalent rms input noise is also equal to the noise generated by the 50 ohm source multiplied by the turns ratio, = 70 pV rms. Although the numerical value of equivalent input noise is much larger than before, the signal-to-noise ratio is sub­stantially increased. This can be seen by considering all of the transformed source signal voltage as appearing at the amplifier input terminals, because the Model 113 input resistance is much larger than the 1 megohm presented by the transformer; the signal-to-noise ratio is equal to the maxi~um possible value: esig/E x antilog N F /20) .::= esig/E. In thiS example the transformer increases the signal-to-noise ratio by a factor of 8.

Princeton Applied Research Corporation manufactures transformers for use in low level, low frequency applica­

tions. Characteristics and details regarding the use of some of these transformers are discussed in Subsection 3.11. Because the transformers have so much influence in determining bandwidth, and because of the noise contrib-

111-2

uted by the transformers, the results obtained using a transformer hardly resemble the ideal theoretical results as predicted in the example. When ug a transformer, it is best to use noise figure contours and amplitude transfer curves obtained empirically for the individual transformer. Sub­section 3.11 contains such data for the transformers.

3.3 GROUNDING

The Model 113 is specifically designed to have a high degree of immunity to the effects of ground-loop currents. The signal ground side of the input connectors is connected to chassis ground through a 10 ohm resistor. To maintain ground-loop immunity, avoid shorting the input grounds to chassis ground at the ampl ifier end of the cables. To further reduce the effects of ground-loop currents, use an input cable that is short and has a high conductivity outer conductor. (For a discussion of the circuit design with respect to grounding considerations, see Section IV).

CAUTION: The power rating of the 10 ohm resistor is 'h watt. Avoid excessive ground-to-ground current to avoid burning out this resistor.

When the signal is applied to the input via a transformer, operate the ampl ifier single-ended. That is, place one input selector to the ground position, and connect the trans­former to the other input (ac couple); connect one transformer lead to the outer shell of the BNC connector and connect the other transformer lead to the center conductor of the connector. Connecting this way avoids the problem of static charge build-up at the inputs due to no ground return.

3.4 SIGNAL VOLTAGE AND GAIN

With the variable gain control in the calibrated position (ccw), the position of the gain selector accurately sets the gain to the indicated level. Intermediate levels of gain may be obtained by use of the uncalibrated variable gain control. If it is desired to accurately set an intermediate level of gain, apply an input signal to the amplifier input and, using an ac voltmeter, proportionally adjust the output signal level to a corresponding value between the levels of the two fixed gain settings bracketing the desired gain.

The maximum output that the amplifier can provide is 10 volts peak-to-peak (through 600 ohms into an open circuit). For maximum input Voltages, refer to the specifications and to Subsection 3.10.

3.5 DC ZERO ADJUSTMENT

The dc zero adjustment may need to be touched up as the gain is changed. In particular, if the adjustment is first made when operating at a low gain, followed later by transfer to high-gain operation, it is important that the dc zero be checked, and, if necessary, readjusted as required.

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25~--------------~--------------_r--------------~

Overload ~ sufficient input to saturate the output stage of the first amplifier.

20

-: (.)

Data taken with the input coupling switch in the dc position.

In the ac coupling position, a 0.1 J.lF capacitor in' series with a 100 megohm resistor is added (RC ~ 10 seconds).

ILl (/)

GAIN X 2K - X 10

Minimum Recovery Time is available when the input coupling is dc and the Low Frequency Rolloff switch set at dc.

ILl 15 ::f

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5

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Absolute Maximum I nput Voltage (differ· ential or common mode):

ac coupling ~ 115 V, 60 Hz dc coupling ~ ±20 V

.01 .03 0.1 0.3 1.0 LOW FREQUENCY ROLL-OFF SETTING (Hz)

Figure 111-2. TYPICAL RECOVERY TIME VS LOW FREQUENCY ROLLOFF

3.6 OVERLOAD FAST RECOVERY

If the input signal exceeds the level indicated in the specifications (Section I). the amplifier will saturate and remain disabled until coupling and filter capacitors dis· charge (see the recovery time data, Figure 111-2). Pressing the spring·loaded overload recovery toggle causes fast discharge of the capacitors so that normal operation can be resumed immediately.

3.7 LOW-PASS/HIGH-PASS FILTERS

Series low·pass and high·pass filters are incorporated to provide bandpass characteristics. Minimizing the bandwidth minimizes the source thermal noise. In addition, the filters can be used to eliminate unwanted signals (such as dc, high frequency, or 60 Hz pickup). The following figures are normalized amplitude and phase transfer characteristics.

If one or both Coupling switches are set to the AC Coupling position, the LF ROLLOFF switch should not be left in the DC p.osition. If it is left in the DC position, output voltage

111-3

offsets resulting from the input offset current (100 pA max) may occur. At high gains, the offset could exceed full scale.

3.8 SINGLE-ENDED/DIFFERENTIAL OPERATION

The amplifier may be operated differentially or single· ended. For single·ended operation, simply place the unused input coupling switch to the ground position, and place the signal·input switch to ac or de coupling as desired.

For differential operation, place both coupling switches in ac or dc positions or one in dc and the other in ac, as appropriate. The output voltage is equal to the gain times the difference of the voltages at the A and B inputs.

Remember that the two signal grounds (tied together internally) are connected to chassis ground through a 10 ohm resistor. For maximum ground-loop rejection, avoid shorting the signal ground to chassis ground.

I 1 I

To do zero adjustment, place both coupling switches inthe ground position, set the L.F. Rolloff switch to DC, +80 . -

and set the gain switch to the position to be used. Then ~

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i i Figure Ill-5. LP/HP FILTER NORMALIZED

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inputs are driven by the same large signal, no trace of thatFigure |||_4_ HP HL-I-ER NQRMAUZED signal should appear at the output. The signal at the output

AMPLITUDE TRANSFER cunvE should result from the differential input signal only. Real

Ill-4

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3.9 DC ZERO ADJUSTMENT

To do zero adjustment, place both coupling switches in the ground position, set the L.F. Rolloff switch to DC, and set the gain switch to the position to be used. Then adj ust the front-panel zero potentiometer for 0 V at the output.

TOTAL GAIN

0.6

~ ~LP

0.4 f:=--

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o 0.1

GAIN x jEout I x ~ E ,n L P [E;;;I HP

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figure 111-3. LP FILTER NORMALIZED AMPLITUDE TRANSFER CURVE

0.8

0.6

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0.2

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100

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111-4

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130 dB

120 dB

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80 dB

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Figure 111-5. LP/HP FILTER NORMALIZED PHASE TRANSFER CURVE

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FREQUENCY IN H l

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3.10 MAXIMUM INPUT SIGNAL CONSISTENT WITH LINEAR OPERATION

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amplifiers, including the Model 113, do not exhibit com­plete immunity to common mode signals_ However, as

stated in the COMMON MODE REJECTION specification the immunity, though finite, is very great indeed. Thi~ immunity only holds for common mode signals of 1 V rms or less. With higher common mode signals, input circuits become non-linear and a very great degradation in common mode signal rejection occurs. This is the meaning of the Common Mode Maximum Input Signal specification.

To appreciate the meaning of the Differential Mode Maximum Input Signal specifications, it is necessary to distinguish between attenuated differential input signal and unattenuated differential signal. Attenuated input signals are those at a frequency wh ich is attenuated by either the High Pass Filter or the Low Pass Filter_ The frequencies affected by these filters depend on the setting of the corresponding Front-panel switches. Unattenuated signals are those at a frequency which is unaffected by the filters. The maximum output capability of the Model 113 is 10 V pk-pk. Clearly, for an unattenuated signal, the maximum differential input one can apply is 10IG V pk-pk, where G is the selected gain. At frequencies where the filters begin to have some effect, greater differential input signals can be applied. The further one moves into the region of filter influence, going either higher or lower in frequency, the larger the differential input signal can be. However, a limit is reached where any further increase in· input signal, regardless of frequency, will cause non-linear operation and performance degradation_ This limit, which is a function of the Gain switch setting, is given by the two Differential Mode Maximum input signal specifications. For gains of 10 to 100, the absolute maximum one can apply is 1 V pk-pk. For gains of 200 to 10,000, the absolute maximum differential signal one can apply is 100 mV pk-pk. It should be clear that if the frequency component of interest is not being maxima!ly attenuated by the High Pass or Low Pass Filter, the maximum input will be lower. Figure 111-7 illustrates these relationships.

c:

> oK ... I

LOW FREQ. ROLLOFF

LIMIT FOR UNATT£NUATED SIGNALS (GAIN' 100) AS

DETERMINED BYiG

~ 10mV~--------~~~~-L------------~

Figure 111-7_ MAXIMUM DIFFERENTIAL INPUT TO MODEL 113

111-5

3.11 BATTERY OPERATION TEST AND CHARGI NG' ,

The Model 113 has rechargeable batteries good for up to 30 hours of operation when fully charged. I f they are not fully charged, or if the Model 113 is driving a load having an impedance of less than 10 kS1, a shorter operating period will result. To operate from battery power, set the Power switch to ON, but do not plug in the line cord. When the period of battery powered operation is completed, be sure to set the switch to OF F to prevent running down the batteries.

To check the batteries, push the spring-loaded test switch to the left and to the right. If the green indicator lights, the corresponding battery is charged. If it remains out, the batteries need charging. Battery charging takes place when­ever the Power switch is set to OF F with the I ine cord plugged in. Beginning from the fully discharged state, it takes anywhere from 24 to 36 hours to fully recharge the batteries. I n general, one should follow each period of battery operation with a charging period of equal or greater duration.

NOTE: When the power switch is set to ON with the line cord plugged in, the batteries "trickle charge" at a rate very much lower thal1 that obtained with the switch set to OFF. For this reason, it is better to charge with the switch set to OFF.

The batteries used in the Model 113, should they require replacement, can be ordered from Princeton Applied Research Corporation. The part number is 4000-0016-04 Specification #710311 A. '

When the batteries are being recharged (instrument plugged in but with Power switch in OFF position), there is no time limit, that is, there is no possibility of overcharge with subsequent battery damage due to the charging being maintained for too long a time.

3.12 RACK MOUNTING

The Model 113 may be mounted in a standard 19" relay rack, either singly or two units side by side. The following mounting accessories are available from the factory:

Single mounting: Panel, rack mounting, part number 1415-0553-08

Double (side-by-side) mounting:

Coupling, rear, part number 1415-0555-14 Coupling, front, part number2517-0217-19 Screw, coupling, part number 2517-0218-18

Flanges are required for both types of rack mounting. Most

units are shipped with the flanges, but if the unit to be mounted does not have them, order part number 1402-0008-20 (two for each type mounting).

3_13 USING A SIGNAL INPUT Figure lll-9A is a family of amplitude transfer curvesTRANSFQRMER for a typical Model AM-1 wired for a 1:100 turns

ratio, and Figure lll-9B is the corresponding family ofHOW a Signa| input transformer can improve |OW_nOise noise figure contours. In the transformer-amplifierperformance was discussed in Subsection 3.2. There it was system’ the noise ngure ootenneo _nonn n|'9B ore"indicated that a transformer often has a bandwidth narrow demmetesl ad. Therefore, this noise -figure can becompared with the amplifier it is being used with, and that regarded as tne system overen no'se n9ure' HoWe_Ver'the transformer adds its own noise to the total noise. For the nansformee frequency response and tne amonnerthis reason, it is best to have noise figure contours and response set Yvnn tne ronon eontro's must be eom'amplitude transfer curves for the transformer. Princeton o'neo to ootem tne system overen response enereeter'

_ IApplied Research Corporation manufactures three mag 'st'es'netically shielded signal transformers that may be used withthe Model 113: the Models AM-1, AM-2, and 190. Data foreach of these transformers follows. §lso ,,‘,§‘, 283222 _-__" 42 IOOQ SOURCE — * *

(1) Model AM-1 3.1,. . _l- \Z so _L \

A general-purpose frequency response and changeable Fturns ratio render the AM-1 the most versatile of thethree transformers. NOTE: The outer connector, asthe transformer comes from the factor is wired for a

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differential output with separate ground return (see F"E°“E"°*Figure Ill-8A). When using the transformer with theModel 113, one half of the secondary will be shorted Figure |||-9A_ FREQUENCY RESPQNSE QF TYP|CA|_to ground, if the Model 113 is operated single-ended as MODEL AM-1 TRANSFORMERrecommended in Subsection 3.3, unless the outputconnector is rewired. To use the full 1:100 turns ratio

I From Figure lll-9B, for a turns ratio of 1:100, thertne Center tap W're must be removed from p'n I optimum source resistance is between 10 and 100(ground), and the wire going to pin 3 removed from ohms. If a source resistance in another range is to bepi" 3 and reeenneeted to pl" 1' as shew" In Figure used, the operator may consider changing the turnsI“'8B- ratio to shift the lowest noise-figure resistance range to

that being used. The source resistance scale of Figurelll-9B should be multiplied by the factor 104N2,

mm ourrur mm moo outrur where N is the step-up turns ratio being used.||: g Required wiring and scaling information is given in1- -Q» ‘I Figure Ill-10.

SCI-IEMATIC OF UNMOOIFIED SCHENATIC OF MODIFIEDAM—I AM-1

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Figure Ill-8. MODIFYING THE AM-1 TRANSFORMER Figure III-9B. NOISE FIGURE CONTOURS FORFOR USE WITH THE MODEL 113 PREAMPLIFIER TYPICAL MODEL AM-1 TRANSFORMER

6

3.13 USING A SIGNAL INPUT TRANSFORMER

How a signal input transformer can improve low-noise performance was discussed in Subsection 3_2_ There it was indicated that a transformer often has a bandwidth narrow compared with the amplifier it is being used with, and that the transformer adds its own noise to the total noise. For this reason, it is best to have noise figure contours and amplitude transfer curves for the transformer. Princeton Applied Research Corporation manufactu res three mag­netically shielded signal transformers that may be used with the Model 113: the Models AM-1, AM-2, and 190. Data for each of these transformers follows.

(1) Model AM-1

A general-purpose frequency response and changeable turns ratio render the AM-1 the most versatile of the three transformers. NOTE: The outer connector, as the transformer comes from the factory, is wired for a differential output with separate ground return (see Figure 11I-8A). When using the transformer with the Model 113, one half of the secondary will be shorted to ground, if the Model 113 is operated single-ended as recommended in Subsection 3.3, unless the output connector is rewired. To use the full 1: 100 turns ratio, the center tap wire must be removed from pin 1 (ground), and the wire going to pin 3 removed from pin 3 and reconnected to pin 1, as shown in Figure 111-8B.

SCHEMATIC OF UNMODIFIED AM-'

I NTERNAL CONNECTIONS OF

UNMODIFIED AII-'

A

SCHEMATIC OF MODIFIED AM-'

IlfttUT OUTI'UT

INTERNAL CONNECTIONS OF

MODIFIED AM-'

B

Figure 111-8. MODIFYING THE AM-1 TRANSFORMER FOR USE WITH THE MODEL 113 PREAMPLIFIER

111-6

Figure 111-9A is a family of amplitude transfer curves for a typical Model AM-1 wired for a 1:100 turns ratio, and Figure 111-98 is the corresponding family of noise figure contours. In the transformer-amplifier system, the noise figure obtained from 111-98 pre­dominates, and, therefore, this noise 'figure can be regarded as the system overall noise figure. However, the transformer frequency response and the amplifier response set with the rolloff controls must be com­bined to obtain the system overall response character­istics.

g 430

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toon SOURCE - --~oon SOURCE········

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--- -- \

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, ... ...... , • '0

, .0 . FREOUENCY

Figure 111-9A. FREQUENCY RESPONSE OF TYPICAL MODEL AM-' TRANSFORMER

From Figure 111-98, for a turns ratio of 1:100, the optimum source resistance is between 10 and 100 ohms. If a source resistance in another range is to be used, the operator may consider changing the turns ratio to shift the lowest noise-figure resistance range to that being used. The source resistance scale of Figure 111-98 should be multiplied by the factor 104 N2 ,

where N is the step-up turns ratio being used. Required wiring and scaling information is given in Figure 111-10.

50°r=~r=~~==~~~~~3~d~B~~~~~ check frequency response curves

'" above before operating in shaded . o region . ~ 10 2 ~~~=-tr--~~~====~dB~====~~

IdB

3dB

B

10dB

I 0 - 1 L. ___ -'--~::::::=:::::±== 15dB

10 10 2 10 3

FREQUENCY (HZ)

Figure 111-9B. NOISE FIGURE CONTOURS FOR TYPICAL MODEL AM-1 TRANSFORMER

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Sch ema tic o f Model ~1-1 Trans forme r, shololIl fo r 1:100 t u r ns rat i o .

Th e pr i mary may be rewir ed for o t h e r t u rn s ratios as f o l lo l.'s:

Turns Ra t io (lI S ) Op t imun Source R Co nnect Inpu t To Tie

51. 1 -- -------------- 120 ohms 1 , 4 , -59 . 7 ----------- ----- 80 1 , 10 2 -72 . 3 - - ----- ---------- 60 9 & 10 , -79.3 ----- ----------- 50 1 , 4 9 - 3 .

1e2 -------- -------- 30 1 , , 1 - 3. 145 ---------------- 13 9 , , 9 - 3. 177 - ------ --------- 9 1 , 4 9 -354 - --- ------- ----- 2.5 1 & 9 9 - 4 .

Figure 111-10. SCHEMATIC OF MODEL AM-l TRANSFORMER (UN-MODIFIED)

3 3 J 2 2 2 10 1

- 10 - 4 - 10

- 10

An output cable, made up with connectors, and an input connector are supplied with each AM-1 manu­

factured . When ordering the transformer remember to specify which instrument it is to be used with , so that the proper connector can be provided at the amplifier end of the cable. When making up cables for connect­ing to the input and to the output, use Cannon brand audio connectors type XLR-3-11C or XL-3-11C, or equ ivalent. Coaxi al cab I e sh ou Id be used, preferably of short length and of the low-noise variety (Amphenol RG/U type 21 -537 or 21-541). Figure 111-8B indicates that the center conductor of the output cable should be wired to pin 2 and the shield wired to pin 1. A BNC connector should be installed at the amplifier end of the cable.

Note the resonance peak at the high frequency end of the transformer response curve (Figure 111-9A). If the input signal has frequency components in this range the ampl ifier may b~ prematurely overloaded by them, particularly at high signal or gain levels. If high frequency signal components cause such problems the operator may consider prefiltering the signal or chang­ing the source impedance to flatten the response curve in this range.

CAUTION: Be careful to avoid applying a signal to the primary such that will cause insulation breakdown of the secondary or damage to the input circuit of the amplifier.

CAUTION: Avoid passing excessive dc current through the primary of this transformer. More than 200 /lA will nagnetize the core. Core magnetization will cause thE transformer to saturate prematurely for one polarity f ac signal, resulting in distortion of high level signals, md a magnetized transformer is usually

111-7

noisy and microphonic, causing low level distortion as

well. See paragraph (4) for a discussion of this distortion and a procedure for degaussing the trans­former. Do not measure winding resistance with an ohmmeter; ohmmeter current is sufficient to magne­tize the core.

~\~~g

~ --. -~ - ,.. .~~ .... . --.-....

Figure 111-11. PHOTOG RAPHS OF MODEL AM-l TRANSFORMER

(2) M°de| AM'2 wired to pin 3. A BNC connector should be installed

at the amplifier end of the cable.The AM-2 is best for high frequency applications. Theturns ratio of this transformer is 1:100. Figure Ill-12Ais a family of amplitude response curves for a typicalModel AM-2, and Figure lll-12B is the correspondingfamily of noise figure contours. In the transformer- ®\ %1T~'§eie°>'::‘eE-cetggws 1

amplifier system, the noise figure obtained from ~Figure lll 12B predominates, and therefore, this noisefigure can be regarded as the system overall noise '-

_ii’ — 1

figure. However, the transformer frequency response 5 9 , ‘ : ‘

. . . . 9 l 9

6and amplifier frequency response set with the rolloff é

controls must be combined to obtain the system Q Q. . 9 ° V

overall response characteristics

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OUTPUT

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9 no ion SOURCE - -- - '\ Figure Ill-13. MODEL AM-2 SCHEMATIC,

E0UT/E~TURN

QO

O5

O

E100 '°°°s°°"°‘_‘;3r-" --- .... .. / TURNS RATIO 1:100

'" so ,

t e .to the primary such that will cause insulation break-down of the secondary or damage to the input circuit

' /' . T F\ .". \/ -"' ’ \\ 1

. .

V TOP,-' ,° \\ '\ '._ \ CAUTION: Be very careful to avoid applying a signal

40$ 2 5 10* 2 5 105 2 5 10° O1 ‘EH6 amplifier.FREQUENCY

NOTE: Because the Model AM-2 has a ferrite core,

Fi9“'°'"'12A' FREQUENCY RESPONSE OF TYHCAL core ma netization will not occur as a result of dc

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MODEL AM-2 TRANSFORMER g . . .

current. However, excessive dc current in the primary,along with the ac signal, may result in premature

IO a saturation of the core and distortion of the signal.

( MOde|

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IIIIIIIIIJI; ‘IjIjIjIjijIfI§5E crating in shaded region :jIjIjIjIjIjIjIjIjIjIjI'I'I'Ij._._"IjIjIjIjIjIjIjI _. "

5dV I 5 The Model 190 is the best transformer to use at very

low frequencies and where good low-noise perfor-

ldB mance is required at low frequencies. This transformerT -‘ r has two primary windings, P1, with a P1 :P3 turns ratio

MB of 121000, and P2, with a P2:P3 turns ratio of. 1:100.

~' / Only one of these primaries should be connected at a\ eds ‘ "t time, and the unused winding left open. Figure lll-15|O-r \* / is a family of amplitude transfer curves for the Model

03 3,rQ3 |Q4 3, Q4 |Q5 190, and Figure lll-16 is the corresponding family ofnoise figure contours. The noise figure contours are

transformer-amplifier system contours, so separate

noise figures do not have to be combined. However,

FREQUENCY(Hz)

Figure Ill-12B. NOISE FIGURE CONTOURS FOR ‘ the transformer frequency response and the amplifier

TYP'cA|- MODEL AM"? TRAN$F°RMER frequency response set with the rolloff controls mustbe combined to obtain the overall system response

An output cable, made up with connectors, and an eharaeterietreeinput connector are supplied with each AM-2 manu-factured. When ordering the transformer remember to Note the reeenanee peak at the high frequeney end of

specm’ which i"$'"'~'me0t it is to be used With’ 5° that the transformer response curve. If the input signal has

the proper connector can be provided at the amplifier frequency eernpenente in this range the annpher may

end of the cable. When making up cables for connect- he prematureh, ever|eaded by them, partieu|ar|y at

509 T0 T09 i0PU’f 80d ‘E0 the QUTPUT, U59 (380000 bFa0d high signal or gain levels. If high frequency signal

W050 ¢0009C'E0F$ W09 X|-R'3"11C OF Xl-"3419, Or components cause such problems the operator may

eqUiVa|90'I- C08Xia| Cab|e $00U|d be Used, PF9f9rab|V Of consider prefiltering the signal or changing the source

50°" |<'-‘09'E0 30d QT the |°W'0°i$9 Va09'IV lAf0D0900| impedance to flatten the response curve in this range.

RG/U type 21-537 or 21-541). Figure Ill-13, theschematic, indicates that the center conductor of the The geggndary winding has 3 neon lamp Qgnnegted

OUTPUT Cable $00U|d be Wired Y0 D50 2 80d the Shield across it. If too large a signal is applied to the primary,

Ill-8

--—---.__

l

l

(2) Model AM-2

The AM-2 is best for high frequency applications. The turns ratio of this transformer is 1: 1 00. Figure 111-12A is a family of amplitude response curves for a typical Model AM-2, and Figure 111-12B is the corresponding family of noise figure contours. In the transformer­amplifier system, the noise figure obtained from Figure 111-12B predominates, and, therefore, this noise figure can be regarded as the system overall noise figure. However, the transformer frequency response and amplifier frequency response set with the rolloff controls must be combined to obtain the system overall response characteristics.

g L~O ::: 120

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Figure 111-12A. FREQUENCY RESPONSE OF TYPICAL MODEL AM-2 TRANSFORMER

FREQUENCY (HZ)

Figure 111-12B. NOISE FIGURE CONTOURS FOR TYPICAL MODEL AM-2 TRANSFORMER

An output cable, made up with connectors, and an input conne~tor are supplied with each AM-2 manu­factured. When ordering the transformer remember to specify which instrument it is to be used with, so that the proper connector can be provided at the amplifier end of the cable. When making up cables for connect­ing to the input and to the output, use Cannon brand audio connectors type XLR-3-11C or XL-3-11C, or equivalent. Coaxial cable should be used, preferably of short length and of the low-noise variety (Amphenol RG/U type 21-537 or 21-541). Figure 111-13, the schematic, indicates that the center conductor of the output cable should be wired to pin 2 and the shield

111-8

wired to pin 3. A BNC connector should be installed at the amplifier end of the cable.

BOTH CONNE CTORS CANNON XLR -3-9JT

Figure 111-13. MODEL AM-2 SCHEMATIC, TURNS RATIO 1 :100

CAUTION: Be very careful to avoid applying a signal to the primary such that will cause insulation break­down of the secondary or damage to the input circuit of the amplifier.

NOTE: Because the Model AM-2 has a ferrite core, core magnetization will not occur as a result of dc current. However, excessive dc current in the primary, along with the ac signal, may result in premature saturation of the core and distortion of the signal.

(3) Model 190

The Model 190 is the best transformer to use at very low frequencies and where good low-noise perfor­mance is required at low frequencies. This transformer has two primary windings, P1, with a P1: P3 turns ratio of 1: 1 000, and P2, with a P2:P3 turns ratio of 1: 100. Only one of these primaries should be connected at a time, and the unused winding left open. Figure 111-15 is a family of amplitude transfer curves for the Model 190, and Figure 111-16 is the corresponding family of noise figure contours. The noise figure contours are transformer-amplifier system contours, so separate noise figures do not have to be combined. However, the transformer frequency response and the amplifier frequency response set with the rolloff controls must be combined to obtain the overall system response characteristics.

Note the resonance peak at the high frequency end of the transformer response curve. If the input signal has frequency components in this range the amplifier may be prematurely overloaded by them, particularly at high signal or gain levels. If high frequency signal components cause such problems the operator may consider prefiltering the signal or changing the source impedance to flatten the response curve in this range.

The secondary winding has a neon lamp connected across it. If too large a signal is applied to the primary,

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INPUT TRANSFORMER MODEL AM -2

Figure 111-14_ PHOTO OF MODEL AM-2

the lamp conducts to prevent the voltage induced in the secondary from damaging the transformer or amplifier input circuit_

An output cable, made up with connectors, is supplied with each Model 190 manufactured_ When ordering the transformer remember to specify which instru­ment it' is to be used with so that the proper connector can be provided at the amplifier end of the cable. When making up cables for connecting to the input and to the output, use BNC connectors and coaxial cable_ The coaxial cable should be short to keep capacitance low, and should be, preferably, low-noise cable (such as Amphenol RG/U type 21-537 or type 21-541)_

+1

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10 10 100 1000 10k

FREQUENCY Hz

Figure 111-15. FREQUENCY RESPONSE OF TYPICAL MODEL 190 TRANSFORMER

111-9

10'

10'

10'

10'

10' +-1-- -\-+---=""'-110-0::::'-""--+--;""';"

10 1==::::':=-I-=I-=;:;;::~:::E

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10 10' 10 '

FREQUENCY HI

Figure 111-16. NOISE FIGURE CONTOURS FOR TYPICAL MODEL 190-113 SYSTEM

The Outer Shells 01‘ The input BNC COHHBCIOFS are (4) Core Magnetization, Corresponding Distortion, and '

floating off ground (see 190 schematic, Figure Ill-17); Degausgingto maintain the common-mode rejection properties ofThe Transffmer. d0 "0? C0"eC'I the iut-Cable Shield Excessive current through a winding of a transformerY0 The TTa"$f°TmeT C359 9T°U"d- will permanently magnetize the core of most trans- “I

formers. This is true of the Models AM-1 and 190. TheModel AM-2 has a ferrite core which virtually will not

9 permanently magnetize. All transformer cores saturatePl -_> in magnetization (=B) after a given winding current

@ N has been reached (<1 H "' no. turns x i - ma netizin- " 9 9® $3 force, where i = current through winding). The voltage ~

’ induced in the secondary is proportional to dB/dt, soP2 the secondary voltage is distorted on that part of the

® _‘ Q . . .

®curve where B is not a linear function of H. Apermanently magnetized core saturates at a lower level

/77 of H, and thereby reduces the maximum signal currentTggjfm sssesssem that can be transformed without distortion. Figure

<,,.,.2,,,,,i,E,,,,.,,,, ,,,,s,,,,,.eE,,,,,,,t,,,,,';,,,,,,,,,2,,,,,,,, ,°,,,,,,,,_ Ill-19 shows a B-H curve and waveforms that graph-"sE“""°°°“"°‘ 'mm°'°"""°""" ically illustrate this core saturation and corresponding

distortion. Note that the B-H characteristic is actuallya loop; curves #1 and #2 of Figure lll-19A are only

i=ieu,ei|i_17_ MQDEL 190 SCHEMA-i-ic representative ”center /ines" of the correspondingloops. Actually, the loops are usually “squarish ovals",

CAU-i-i0Ni Avoid passing excessive de Current with different degrees of squareness for different core

through the primary of this tranformer. More than {“ateria|57 blft the details of the |°°p5 ale "_°t °f200 “A Wiii magnetize the eere_ Core magnetization interest in this discussion, only the general situation ofwill cause the transformer to saturate prematurely for the loops W'th respect to 5aturat'°n'one polarity of ac signal, resulting in distortion ofhigh-level signals, and a magnetized transformer is

usually noisy and microphonic, causing low level §§$§§:li§ii@“?§§§§"“'°"

distortion as well. See paragraph (4) for a discussion of A D..//

cui=iv£s#i 0 2 as "ceuren mics"0F INDIVIDUAL B-H LOOPS _.__ _ _..9 $*TURATE|-7 "Kilo" “this distortion and a procedure for degaussing the

E ,

transformer. Do not measure winding resistance with $‘Z’?i"é‘ii'2EB'

an ohmmeter,‘ ohmmeter current is sufficient to /ii3>i;;;~6~;i»;i§§E»i,~LTR~i>;i~;~,;,;ii;ivE=R-

magnetize the core. A H T

2 I

IF CORE lS PERMANENTLY MQGNETIZEDTHE SIGNAL PAST THIS POINT SKTURATESTHE WE, $ TTMT MAXIMUM Sl_GNlL

...._ _ _ _ __ AMPLITUDE IS REUJCED.ASSUME SIGNAL LEVEL ISNOT LARGE ENOUGH TO MAKECORE GO INTO THIS REGION

CURRENT SATURATES CORE ABOVE THIS LEVEL/lF CORE IS PERMANENTLY MAGNETIZED.

Ii . PRIMARY CURRENT

i ‘ I i= I slim!

B 1 ' _’WHEREM =2wl

l

/'Zirur PEAK son one POLARITY ONLY

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5 cone (WORKING on cuavcdlzi.

C ‘ i l I

A \ CORRESPONDING INDUCED

' SECONDARY VOLTAGE I QD i 08/di oi; iiilcosiiii

i \/ EXCEPT IN DISTORTED REGION

DISTORTED REGION J9

Figure Ill-18. PHOTOGRAPH OF MODEL 190TRANSFORMER Figure Ill-19. B-H CURVE & WAVEFORM

lll-10

The outer shells of the input BNC connectors are floating off ground (see 190 schematic, Figure 111-17); to maintain the common-mode rejection properties of the transformer, do not connect the input-cable shield to the transformer case ground.

P I~ • ~ P2~ -~

CASE ~ TERNINALl

NaTES : I. TURNS RAllO PI : P2:P3;.1:IO:10CX) 2.DC RESISTANCE PI8I42 ",0; P2S11l.SA; S3W32kA 3. FREOt.£NCY RESPONSE (PI DRIVEN FROM 50 "'A SOURCE

OR P2 DRIVEN FROM 5A SOURCE) WITH ± ICl8 FROM 320 fillHI' TO 500 Hr • •. SELf INOJCTANCE REFERRED TO PI-3.08_H

Figure 111-17. MODEL 190 SCHEMATIC

s.

CAUTION: Avoid passing excessive dc current through the primary of this tranformer. More than 200 pA will magnetize the core. Core magnetization will cause the transformer to saturate prematurely for one polarity of ac signal, resulting in distortion of high-level signals, and a magnetized transformer is usually noisy and micropholJic, causing low level distortion as well. See paragraph (4) for a discussion of this distortion and a procedure for degaussing the transformer. Do not measure winding resistance with an ohmmeter; ohmmeter current is sufficient to magnetize the core.

A .... PRINCETON APPLIED RESEARCH

MOOEl190 LOW NOISE TRANSFORMER

Figure 111-18. PHOTOGRAPH OF MODEL 190 TRANSFORMER

111-10

(4) Core Magnetization, Corresponding Distortion, and Degaussing

Excessive current through a winding of a transformer will permanently magnetize the core of most trans­formers. This is true of the Models AM-1 and 190. The Model AM.2 has a ferrite core which virtually will not permanently magnetize. All transformer cores saturate in magnetization (=B) after a given winding current has been reached (0:: H = no. turns x i = magnetizing force, where i = current through winding). The voltage induced in the secondary is proportional to dB/dt, so the secondary voltage is distorted on that part of the curve where B is not a linear function of H. A permanently magnetized core saturates at a lower level of H, and thereby reduces the maximum signal current that can be transformed without distortion. Figure 111-19 shows a B-H curve and waveforms that graph­ically illustrate this core saturation and corresponding distortion . Note that the B-H characteristic is actually a loop; curves #1 and #2 of Figure 11I-19A are only representative "center lines" of the corresponding loops. Actually, the loops are usually "squarish ovals", with different degrees of squareness for different core materials; but the details of the loops are not of interest in this discussion, only the general situation of the loops with respect to saturation.

8' AMOJNT CI MAGNETIZATION H • MAGNETIZING FOR(:(

CURVES# I a 2 ARE "CENTER LI NES " OF INDIVIDUAL B-H LOOPS

A

B

c

D

,--- ASSU-;'; SIGNAL LEVEL IS

"" NOT L.ARGE ENOuGH TO MAKE CORE GO INTO THIS REGION

,I' COAE IS PERMANENTLY MNlN(TlztO THE SIGNAl. PAST THIS POINT SA'NUm THE OOAE, so THill IrIWtIMUM SI,"Al AMPLlTUOE IS MOOCED. •

PAt .... fIY CURRENT

ill ..... t

WHERE ... 1 Z".t

I

I FLAT PEAK FOR ONE POLARITY ONLY

CORRE~DING B OF PERMANENTLV MAGNETIZED COM: fWQflKING ON CURY£#2I-

CORRESPONOlNG INOUC€D

SECONDARY VOLTAQ£ • CIt

dB/ dl oc ... 1COh,1 ---t-- t------':r-; -+----,t--- EXCEPT IN DISTORTED REGION

DISTORT E D REGION

Figure 111-19. B-H CURVE & WAVEFORM

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A magnetized transformer is usually noisy and micro­phonic compared to when it is not magnetized. This noise is the most objectional characteristic of a magnetized transformer because it affects low level signals. The distortion of high level signals described here is not usually an operating problem because the signal is seldom so large, but high level distortion is useful in determining the condition of the core and in monitoring the degaussing process.

Notice from Figure "1-19A that as long as the core IS

not magnetized the transformer works on a loop around center-I ine #1 and thesignal can be of maxi­mum amplitude. If the core becomes permanently magnetized, the transformer works on a loop around center-line #2 (or equivalent for opposite polarity), and, if the same maximum signal current is applied, the core becomes saturated at one of the peaks of the signal. B, C, and D of Figure 111-19 show a primary signal current, corresponding core magnetization, and corresponding induced secondary voltage for a magnetized-core transformer with large signal input. Notice that the permanently magnetized core saturates

sooner for one polarity of signal and later for the other polarity.

To demagnetize (degauss) the transformer, it is neces­sary to pass a relatively large ac current through the primary and to very slowly decrease this current. The degaussing current is initially large enough to mag­netize the core in the direction of each corresponding polarity excursion of this current, and overrides the initial magnetization. The object of decreasing the current slowly is so that each successive magnetization is slightly less than the preceding one of the opposite polarity. As the current is decreased, the core is less magnetized until it is no longer magnetized at all. Figures 111-20A, B, and C illustrate the secondary waveforms as the transformer becomes demagnetized. IMPORTANT: Use a LOW FREQUENCY degaussing current, 1 Hz or so, to avoid inducing excessively high voltage in the secondary, and monitor the secondary with a high impedance oscilloscope. The Model 190's secondary is protected with a neon lamp, but the Model AM-1 could suffer insulation breakdown if the operator is not careful.

DISTORTION AT ONLY EVERY 2!!:!Ef! ZERO ~SSING INDICATES PRIMARY CURRENT SATURATES CORE IN ONE DIRECTION ONLY. OONTlNUE TO INCREASE PRIMARY CURRENT UNTlL WAVEFORM

A ~-----"~----r-------" ...... -----,.....-- RESEMBLES B.

B

c

DlSlORTION AT EVERY ZERO CROSSING INDICATES CORE SATURATES FOR BOTH POLARITY EXCURSIONS OF

-'-:...----.:.....;:-----..,-c.----~---__;.,.__- DEGAUSSI NG CURRENT.

Figure 111-20. DEGAUSSING WAVEFORMS

111-11

VERY SLOWLY DECREASE DEGAUSSING

CURRENT UNTI L WAVEFORM APPEARS

UNOISTORTEO, IF WAVEFORM GOES BACK

TO A,REPEAT PROCEDURE USING HIGHER INITIAL CURRENT_

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SECTION IV

CIRCUIT DESCRIPTION

4.1 BLOCK DIAGRAM DISCUSSION

Refer to the Block and Wiring diagram on page VII-2_ Note that the Model 113 is composed, essentially, of two operational amplifiers in tandem, with associated coupling, interstage LP/HP filter circuits, overload recovery circuit, and battery charging and test circuits_

4.1A INPUT COUPLING CIRCUIT

Individual input coupling switches select the inputs direct­Iy, through dc blocking capacitors, or select ground, and apply the selected inputs to the corresponding field-effect input transistors of ALI n the ac positions, the 100 megohm bleeders, R4 and R6, keep charge from building up on the capacitors, which would otherwise render the amplifier inoperative by offsetting the input FET's to cutoff_ In the dc positions the signals go directly to the FET's, so that no bleeder is needed_ (When in a dc position, if the signal source cannot bleed off charge, then the operator should provide an external bleeder.) The ground positions are convenient to use when setting the zero control, and when using the ampl ifier single-ended the coupling switch for the unused input should be set to the ground position.

t 4.1B GROUND-LOOP SUPPRESSION

A typical amplifier hook-up consists of a signal source or sources, amplifier, and readout device such as an oscillo­scope_ This type of hook-up usually has two ground connections between the signal source and amplifier: that which accompanies the power source and mounting rack, and that which accompanies the signal between ·the source and amplifier; see Figure IV-l. The two ground paths together form a loop that is exposed to varying environ­mental electric and magnetic fields. These fields, cutting the loop, generate emf's and currents in it. Various other sources of current in the loop may exist, sLlch as current due to battery action at the connectors, etc. A sign ificant

R (SIGNAL GROUND)

CHASSIS GROUND emf CHASSIS GROUND (DISTRIBUTED AROUND LOOP)

F~ureIV-l_ GROUN~LOOPCURRENTPATH

IV-l

part of the ground-loop voltage (V I) is developed across the signal ground path, especially i~ the chassis ground is very good (it usually is and should be). This portion of the ground-loop voltage is amplified along with the desired signal, and, at very low signal levels, can cause a great deal of trouble_ The Model 113 has provisions for eliminating this ground-loop voltage from the signal being amplified_

For doing this, the signal ground is not connected directly to chassis ground but to a 10 ohm resistor (R7) connected betWeen the insulated outer shells of the input BNC's and chassis ground. Since 10 ohms is very much greater than the signal ground and chassis ground resistances, virtually all of the ground-loop voltage develops across the resistor. The first amplifier stage amplifies, either differentially or single-ended with respect to signal ground, and does not, therefore, amplify these ground-loop voltages. The output signal is referenced to chassis ground, and is free of ground-loop components_

4.1C GAIN DETERMINATION

The gain switch selects either xl0 or xl00 gain of the first amplifier, either xO.l, xO.2, xO.5, or xl attenuation of an interstage attenuator, and either xl 0 or xl 00 gain of the second amplifier, as required to yield the gain marked at each position of the switch.

For the first four switch positions, the gain of Al is xl0. For the last six gain positions, the D section of the gain switch, Sl, connects pins 10 and 12 of the PC board, thereby changing the gain of A 1 to xl 00. How the gain of A 1 is determi ned is explained in the schematic discussion for A 1.

The interstage attenuator comprises R12 through -R15. The-: A section of the gain switch selects the required attenuation level. The series attenuator output resistors, R 16 through R 19, adjust the attenuator output impedance so that the attenuator presents the same impedance to the rolloff circuit for all switch positions.

For all gain-switch positions, the 500 ohm-4.5 kilohm feedback attenuator at the inverting input of A2 makes A2 operate with a gain of at least 10. I n the last three positions another 10: 1 attenuator, comprising R9 and R 10, is switched in by the F section of Sl to increase the gain to xl00. The gain vern ier, R 11, is also in th is feedback circuit_

4.10 ROLLOFF FILTER CIRCUIT

The high frequency and low frequency rolloff circuits are simple RC filters connected in tandem. The HF and LF roll off switches select different capacitors for each rolloff frequency of the corresponding filter. The H F rolloff filter is composed of the series resistance presented by the gain attenuator circuit (15.9 kilohms for all gain switch posi-

tions) and a shunt capacitor selected by the HF rolloff single-ended for each half of the circuit. But differential

switch. The LF rolloff filter is composed of the series signals cause the emitter-coupled pair, Q114A and Q1148,

capacitor selected by the LF rolloff switch and the 1.59 to provide equally and oppositely changing signal currents

megohm shunt resistor at the input to A2. The transfer to their collector circuits, and common-mode signals tend

curves for these filters are given in Section Ill. to cause equal changes in the collector currents of Q114A 1

and Q1148. Differential signals cause no change in the

emitter currents of Q114A and Q1148 but common mode

4-‘IE QVERI-OAD FAST-RECQVERY CIRCUIT signals do. Therefore the common-mode feedback signal is

taken from the emitter resistor 8146.

The overload recovery button, when pressed, turns on

FE-i-,5 Qiop and Qiop eenneeted pet‘/Veen eeen input pi Q116 shifts the Q114A collector voltage level for driving ,

A1 (Pp terminals 5 & 6) end stewed, and iuriie en e FET 0117. 0117 inverts the Q114A signal, and helps Q1148switch connected between the input of A2_and ground. drive the Compiementary Output pair Q118 and Q119_

Q105 and Q106 discharge the input capacitors, C1 and O Osin the Q114A nd Q114-B out uts this Wa CanCe|S

C2, and the FET switch between the input of A2 and pp 9 . a F.) . . V

ground discharges the LP and HP filter capacitors, °9‘“".‘°“'"?°?"e S'gna|s that may remam m tms part of thethereby providing fast Overload recovery circuit. This is because the common-mode feedback loop, in

keeping the voltage across 8146 constant, cancels the

4-1F POWER SUPPLY common-mode signal component that would otherwise

appear in the collector currents of Q114A and Q1148.

AC iine p0Wer is Stepped d0Wn bV e transformer! then C8108 temperature-compensates the emitter junction ofrectified. The + & — rectifier outputs are shunted with 12 V Q113_ QR112 and CR113 are forward biased diodes whose

nickel-cadmium batteries. Batteries across the dc supply Constant ()_6 V iunotion dr()p5 keep Q118 and Q119

outputs provide sufficient regulation so that other regu|a- forward biased. The primary gain-determining feedback is

tien i5 net needed When ee line p0Wer is u$eCl- it the taken from the output through 8131, and will be explained

batteries are in a state of discharge, the transformer-rectifier below,circuit will automatically charge them while operating fromac. For battery operation, the unit is simply not plugged Q111A and Q1118 compare the common-mode feedback

into the ac receptacle, so that the batteries alone provide voltage at the base of Q1118 to a reference voltage at the

power to the dc lines. For convenience in checking the base of Q111A, and provide corresponding equal and

batteries, a test circuit is provided. opposite signal currents to their collector circuits. Q113

inverts the Q111A collector signal to aid Q1118 in driving

4.2 CIRCUIT DESCRIPTIONS Q107 and Q108. Q107 and Q108 are complementarytransistors that drive the junction of 8123 and 8126,

4.2A DIFFERENTIAL PREAMPLIFIER (A1) providing balanced feedback to the sources of the inputFET's.

Refer to the schematic on page Vll-3. This circuit differen-tially amplifies the input signals at the gates of Q100 A &8. These field-effect transistors are involved in two over- The teedbeek eetien 0t en Operetienei ernpiitier i5 Sueh 85

lapping modes of operational amplifier feedbaok that to keep the summing point voltage equal to the reference

determine gain and prevent amplification of common-mode peint \/0ite9e- Sinee teedbeek i5 u$ueiiV taken ir0rn the

signals. output, this condition, being the only stable condition, is

taken advantage of in determining gain. In this circuit,

0102 provides constant current to 8108, thereby fixing the however, we really have twe dependent operational ameli-

voltage across 8108. 8105 and 8119 provide an average of tier i00p$ that determine Qein end pr0\/ide e0rnrn0n'nn0de

the source voltages of Q100 A & 8 to the base of Q103. reieeti0n-

Because Q103 and both sections of Q101 are forwardbiased (so that their emitter junctions have constant 0.6 V The tir5t ieedpeek eempenent We Wiii e0n$ider i5 the

across them, approximately), the source-drain voltagesof eerninen'rn0de teedheek trern Q107 end Qip8- C0rre-

Q100 A & 8 are held constant at approximately the voltage $p0ndin9 Currents threugh R123 end~ R126 drive the

across 8108 (5 V). C8101 and C8107 are input protective Spurees pi Q100 A 81 B te epuntereet the e0mrnen'rn0de

diodes reverse biased by the collector voltage of Q104. If eernpenent Oi the input $i9nei- in this i00p the be$e 0t

either input voltage becomes larger than about -3 \/, the Q111A is the reference point and the base of Q1118 is the

corresponding diode will conduct. The current path is summing D0int- The hi9h Qein Oi the i00p Causes the

through the Q104 collectorjunction and C8104 to ground. feedback te the Spureee t0 e0rnpieteiV eduntereet the

The gate junctions of the input FET's can handle positive e0rniTi0n'n10de edrnpenent Qt input $i9nei- in d0in9 5° itinput over-voltages without being damaged; they simply aide the teedpeek irern the Output in $eti5tVin9 thebeoome forward biased and oondnot_ requirements of the gain-determining loop, as will be seen

from the following discussion.

The drain currents of Q100A & 8 pass to the collectors ofQ101A & Q1018, and are developed as voltages for The gates of the two input FET's can be considered as the \-.

application to the bases of Q109A and Q1098. Q109A and reference points of two separate operational amplifiers, and

Q1098 are emitter followers which provide drive for the sources the corresponding summing points. Both of

Q114A and Q1148. Up to now amplification has been these operational amplifiers must be satisfied simulta-

IV-2

tions) and a shunt capacitor selected by the HF rolloff switch. The LF rolloff filter is composed of the series capacitor selected by the LF rolloff switch and the 1.59 megohm shunt resistor at the input to A2. The transfer curves for these filters are given in Section III.

4.1E OVERLOAD FAST·RECOVERY CIRCUIT

The overload recovery button, when pressed, turns on FET's 0105 and 0106 connected between each input of A 1 (PC terminals 5 & 6) and ground, and turtls on a FET switch connected between the input of A2 and ground. 0105 and 0106 discharge the input capacitors, Cl and C2, and the FET switch between the input of A2 and ground discharges the LP and H P filter capacitors, thereby providing fast overload recovery.

4.1 F POWER SUPPL Y

Ac line power is stepped down by a transformer, then rectified. The + & - rectifier outputs are shunted with 12 V nickel-cadmium batteries. Batteries across the dc supply outputs provide sufficient regulation so that other regula­tion is not needed when ac line power is used. If the batteries are in a state of discharge, the transformer-rectifier circuit will automatically charge them while operating from ac. F or battery operation, the un it is simply not plugged into the ac receptacle, so that the batteries alone provide power to the dc lines. For convenience in checking the batteries, a test circuit is provided.

4.2 CIRCUIT DESCRIPTIONS

4.2A DI FFERENTIAL PREAMPLIFIER (A 1)

Refer to the schematic on page VII-3. This circuit differen­tially amplifies the input signals at the gates of 0100 A & B. These field-effect transistors are involved in two over­lapping modes of operational amplifier feedback that determine gain and prevent amplification of common-mode signals.

0102 provides constant current to Rl0S, thereby fixing the voltage across R lOS. R 1 05 and R 119 provide an ave rage of the source voltages of 0100 A & B to the base of 0103. Because 0103 and both sections of 0101 are forward biased (so that their emitter junctions have constant 0.6 V across them, approximately), the source-drain voltages of 0100 A & B are held constant at approximately the voltage across RlOS (5 V). CR10l and CR107 are input protective diodes reverse biased by the collector voltage of 0104. If either input voltage becomes larger than about -3 V, the corresponding diode will conduct. The current path is through the Ql04 collector junction and CR104 to ground. The gate junctions of the input FET's can handle positive input over-voltages without being damaged; they simply become forward biased and conduct.

The drain currents of 0100A & B pass to the collectors of 0101A & 0101B, and are developed as voltages for application to the bases of 0109A and 01098. 0109A and 0109B are emitter followers which provide drive for 0114A and 0114B. Up to now amplification has been

IV-2

single-endeq for each half of the circuit. But differential signals cause the emitter-coupled pair, 0114A and 0114B, to provide equally and oppositely changing signal currents to their collector circuits, and common-mode signals tend "") : to cause equal changes in the collector currents of 0114A ~ and 0114B. Differential signals cause no change in the emitter currents of 0114A and 0114B but common mode signals do. Therefore the common-mode feedback signal is taken from the emitter resistor R146.

0116 shifts the 0114A collector voltage level for driving 0117.0117 inverts the 0114A signal, and helps 0114B drive the complementary output pair 011S and 0119. Opposing the 0114A and 0114B outputs this way cancels common-mode signals that may remain in this part of the circuit. This is because the common-mode feedback loop, in keeping the voltage across R146 constant, cancels the common-mode signal component that would otherwise appear in the collector currents of 0114A and 0114B. CR 1 OS temperature-compensates the emitter junction of 0113. CR112 and CR113 are forward biased diodes whose constant 0.6 V junction drops keep 011S and 0119 forward biased. The primary gain-determining feedback is taken from the output through R131, and will be explained below.

0111 A and 0111 B compare the common-mode feedback voltage at the base of 0111 B to a reference voltage at the base of 0111A, and provide corresponding equal and opposite signal currents to their collector circuits. 0113 inverts the 0111 A collector signal to aid 0111 B in driving 0107 and 01OS. 0107 and 010S are complementary transistors that drive the junction of R 123 and R 126, ...)/ providing balanced feedback to the sources of the input FET's.

The feedback action of an operational amplifier is such as to keep the summing point voltage equal to the reference point voltage. Since feedback is usually taken from the output, th is condition, being the only stable condition, is taken advantage of in determining gain. In this circuit, however, we really have two dependent operational ampli­fier loops that determine gain and provide common-mode rejection.

The first feedback component we will consider is the common-mode feedback from 0107 and 0 lOS. Corre­sponding currents through R 123 and. R 126 drive the sources of 0100 A & B to counteract the common-mode component of the input signal. In this loop the base of 0111 A is the reference point and the base of 0111 B is the summing point. The high gain of the loop causes the feedback to the sources to completely counteract the common-mode component of input signal. In doing so it aids the feedback from the output in satisfying the requirements of the gain-determining loop, as will be seen from the following discussion.

The gates of the two input FET's can be considered as the J', reference points of two separate operational amplifiers, and . the sources the corresponding summing points. Both of these operational amplifiers must be satisfied simulta-

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neously by the feedback from the output and the feedback from the common-mode circuit. The latter has already been discussed regarding 0111 A and 0111 B as the operational amplifier inputs for that loop, but it is now apparent that the common-mode loop involves all three operational amplifier inputs. Both feedbacks work together in satisfying the two FET operational amplifier input requirements, and the output loop depends on the common-mode feedback in determining gain.

R131, R126, R123, and R128 (and Rl06 and R120 in xl00 gain mode of A 1) comprise the feedback voltage divider that determines gain. Even though connected to the junctions of R126-R131 and R123-R128, the sources of 0100 A & B do not affect the divider ratio because the common mode feedback to the junction of R123 and R126 supplies the source currents. Therefore gain is equal to the ratio of the sum of R131 and R128 to the sum of R123 and R126, as can be seen by stating the equilibrium source-source voltage (across R 123 and R126) and deter­mining the output voltage required to force the required current through the divider network to establish this voltage. To see how the common-mode feedback is neces­sary for the gain-determining feedback's proper operation, aside from providing the source currents to avoid loading of the divider network, set as an example the gate voltage of 0100A at 0 V and the gate voltage of 0100B at +1 V. In this example the source voltage of 0100B must be +1 V and the source voltage of 0100A 0 V (not counting small source-gate drops, which are ignored here). Without the common-mode feedback it would be quite impossible for any value of output voltage to force current through the divider network that can satisfy the loop. However, the common-mode feedback to the junction of R 123 and R 126, in forcing current through these resistors, allows the gain loop to be satisfied with -10 V at the output.

4.2B OUTPUT AMPLIFIER (A2)

Refer to the schematic on page VII-4. CR200 through CR203 are input protective diodes, biased through R203 and R204. Notice that CR201 and CR203 are forward biased, and their forward bias voltages (about 0.6 V) reverse bias CR200 and CR202. This scheme fixes the maximum input voltage at two diode drops (about 1 V).

0201 is a field-effect transistor used as a switch for discharging the filter capacitors (see block diagram) when the OVL recovery button is pressed. During normal operation this switch is off and does not load the input signal.

The gates of field-effect transistors 0205 A & B are the reference and summing inputs of the A2 operational amplifier. The first stage of A2, comprising 0202, 0203A, 0203B, 0205 A & B, and 0206, is a differential stage with common-mode rejection. 0206 provides constant current to the common source point of 0205 A & B, and is primarily responsible for the common mode rejection of the first stage. 0202 provides constant current to R213, thereby fixing the voltage across R213 at about 3 V. 0203A and 0203B are forward biased, so th at -- because the emitter junction voltage of a forward biased silicon

IV-3

transistor is constant at about 0.6 V -- the source-drain voltages of 0205 A & B is held constant at approximately the voltage across R213. The differential·signal drain

currents of 0205 A & B pass to the collectors of 0203A and 0203B, where they are developed as signal voltages for application to 0207 A and 0207B.

0207A and 0207B are emitter followers which provide drive for 0209 and 0210. 0209 and 0210 are an emitter-coupled pair, which provide equally and oppositely changing signal currents to their collector circuits. 0211 shifts the 0209 collector voltage level for driving 0212. 0212 inverts the 0209 signal for helping 0210 drive the complementary output pair 0213 and 0214. CR204 temperature compensates the emitter junction of 0212. CR205 and CR206 are forward biased diodes whose constant 0.6 V junction drops keep 0213 and 0214 forward biased.

The operational amplifier adjusts its output voltage to whatever value is required to keep the summing point voltage equal to the reference poi nt voltage; therefore the gain of A2 is determined by feedback dividers R216-R217 and R9-R10 (see block diagram discussion, Subsection 4.1).

4.2C POWER SUPPL Y CIRCUIT

Refer to the schematic on page VII-5. Ac line power is stepped down by T400, and the low-voltage output of T400 is rectified by CR400 and CR401. S400 selects the transformer's ac line voltage. The + & - rectifier outputs are shunted with 12 V nickel-cadmium batteries. Batteries across the dc supply outputs provide sufficient regulation so that other regulation is not needed. If the batteries are in a state of discharge, the transformer·rectifier circuit will automatically charge them while operating from ac. A Zener-referenced divider circuit, comprising CR300, 0300, and associated resistors, provides several biasing voltages to the amplifier circuits.

4.20 BATTERY TEST CIRCUIT

0301 and 0302 are a Zener-referenced switch, to wh ich the battery test switch connects one battery at a time, applying the voltages in the same polarity for both batteries. If the batteries are charged sufficiently, 0302 conducts and lights the panel lamp. If a battery is low, the lamp remains out when the switch is pressed in the direction of the corresponding battery. Note that the power switch must be on for th is circuit to operate.

SECTION V SAFETY NOTICEWARNING! POTENTIALLY LETHAL VOLTAGES ARE PRESENT INSIDE THIS APPARATUS. THESE SER-VICE INSTRUCTIONS ARE FOR USE BY QUALIFIED PERSONNEL ONLY. TO AVOID ELECTRIC SHOCK,DO NOT PERFORM ANY SERVICING OTHER THAN THAT CONTAINED IN THE OPERATING INSTRUC-TIONS UNLESS YOU ARE QUALIFIED TO TO SO. Any adjustment, maintenance and repair of the openedapparatus under voltage shall be avoided as far as possible and, if unavoidable, shall be carried out onlyby a skilled person who is aware of the hazard involved. When the apparatus is connected to a powersource, terminals may be live, and the opening of covers or removal of parts is likely to expose live parts.The apparatus shall be disconnected from all voltage sources before it is opened for any adjustment,maintenance, or repair. Note that capacitors inside the apparatus may still be charged even if the ap-paratus has been disconnected from all voltage sources. Service personnel are thus advised to waitseveral minutes after unplugging the instrument before assuming that all capacitors are discharged. Ifany fuses are replaced, be sure to replace them with fuses of the same current and voltage rating and ofthe same type. The use of makeshift fuses and the short-circuiting of fuse holders are prohibited.

I —- 1 |— i 1 SECTION V SAFETY NOTICE WARNING! POTENTIALLY LETHAL VOLTAGES ARE PRESENT INSIDE THIS APPARATUS. THESE SER­VICE INSTRUCTIONS ARE FOR USE BY QUALIFIED PERSONNEL ONLY. TO AVOID ELECTRIC SHOCK, DO NOT PERFORM ANY SERVICING OTHER THAN THAT CONTAINED IN THE OPERATING INSTRUC­TIONS UNLESS YOU ARE QUALIFIED TO TO SO. Any adjustment, maintenance and repair of the opened apparatus under voltage shall be avoided as far as possible and, if unavoidable, shall be carried out only by a skilled person who is aware of the hazard involved. When the apparatus is connected to a power source, terminals may be live, and the opening of covers or removal of parts is likely to expose live parts. The apparatus shall be disconnected from all voltage sources before it is opened for any adjustment, maintenance, or repair. Note that capacitors inside the apparatus may still be charged even if the ap­paratus has been disconnected from all voltage sources. Service personnel are thus advised to wait several minutes after unplugging the instrument before assuming that all capacitors are discharged. If any fuses are replaced, be sure to replace them with fuses of the same current and voltage rating and of the same type. The use of makeshift fuses and the short-circuiting of fuse holders are prohibited.

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SECTION V ALIGNMENT PROCEDURE

5.1 INTRODUCTION

The Model 113 is a stable, reliable instrument which should give trouble-free service. If a component is replaced, however, alignment may be necessary, depending on what circuit the component belongs to. For locating components and testpoints mentioned in this section. refer to the photograph and the circuit-board layout diagram in Section VII.

5.2 PRELIMINARY

Before operating from ac line power, make sure the rear-panel switch is in the position indicating the line voltage to be used, and be sure the proper size line fuse is installed (1/16 A for 115 V operation or 1/32 A for 230 V operation, located on inside rear panel). Then connect the ac line power and energize the instrument.

NOTE: This alignment procedure assumes that no compo­nents in the instrument are defective. The technician should make sure of this by making the appropriate voltage and signal checks before and during alignment.

5.3 EQUIPMENT NEEDED

(1) Sinewave generator, 500 kHz range, low distortion.

(2) Oscilloscope, 500 kHz frequency response and mV /cm sensitivity.

(3) Precision rms voltmeter, 0.1 % accurate, such as Hewlett-Packard Model 400 EL.

(4) Dc voltmeter, capable of measuring 0 V to within 1 mV, and capable of measuring 11 V to within 50 mV.

(5) Variable dc supply, floating output, 12 V max.

(6) Attenuators, 2000: 1 and 10: 1,0.1% accurate.

5.4 A2 FET GATE SOURCE ZERO ADJ.

(1) Use a short clip-lead to connect the wiper of the HF Roll off switch to ground; connect at the switch.

(2) Set the Gain switch to 104 •

(3) Monitor the output BNC with the dc voltmeter.

(4) Adjust R211 for 0 V (±2 mV).

(5) Remove the clip-lead.

(' 5.5 COMMON-MODE REJECTION ADJ.

(1) Set both input coupling switches to their ground positions.

V-1

(2) Set the LF Rolloff switch to DC.

(3) Adjust the front panel dc zero control for 0 V dc at the output BNC.

(4) Monitor the output with the oscilloscope. If oscilla­tion is present, adjust C200 to just beyond the point where oscillation stops.

(5) Connect a 4 V pk-pk 100 Hz sinewave signal to the A and B inputs (common mode).

(6) Set both input coupling switches to DC.

(7) Set the gain switch to 10k.

(8) Set the HF Rolloff switch to 1 kHz.

(9) Adjust R118 (eMR ADJ.) for minimum 100 Hz out­put, as indicated by the oscilloscope.

(10) Adjust the signal generator to 2 V pk-pk, 100 kHz.

(11) Set the H F Rolloff control to 300 kHz.

(12) Adjust the gain as necessary to obtain a display on the oscilloscope (still connected to the output).

(13) Adjust Cl05 and Cl16 for minimum 100 kHz on oscilloscope.

(14) Adjust the signal generator to 2 V pk-pk, 300 kHz.

(15) Set the Model 113gaintol00.

(16) Adjust C1 08 for minimum signal output.

(17) Repeat steps 10 through 16 several times for optimum common-mode rejection.

5.6 GAIN CALIBRATION

(1) Connect the 2000: 1 attenuator to the output of the signal generator, and connect the output of the attenuator to the Model 113's A input.

(2) Set the 113's A input coupling switch to DC, the B coupling switch to GND, the HF Rolloff switch to 300 kHz, LF Rolloff switch to DC, and set the Gain switch to 2 k (cal).

(3) Monitor the output of the signal generator with the precision rms voltmeter; the attenuator must remain connected to the signal generator so that a change of load does not occur that would change the signal amplitude. Adjust the rnis voltage to 1 V (exactly) @

400 Hz.

(4) Connect the precision rms voltmeter to the 113's (2) Set the II3'S A input COUPIIDQ SWITCII t0 DC, the B

outputjack.

(5) Adjust R221 for exactly the same reading as set instep (3). NOTE: This adjustment trims the gain onlyin the 2 k, 5 k, and 10 k positions of the Gain switch.

coupling switch to GND, the HF Rolloff switch to 300

switch to 10 (cal).

(3) Monitor the output of the signal generator with theprecision rms voltmeter; the attenuator must remainconnected to the signal generator so that a change of

5'7 LOW Flag?/|l;EmgXT|::0§LOFF load does not occur that would change the signalO amplitude. Adjust the_rms voltage to 1 V (exactly) @

300 kHz.(1) Set the HF Rolloff control to 100 kHz, and set the LF

Rolloff to DC. (4) Connect the precision rms voltmeter to the Model113's output jack.

(2) Connect the signal generator to the 10:1 attenuator,and connect the attenuator output to the Model 113's (5) Adjust C26 (en the |_||: Reueff SW;-(eh) to preduee e

A input. voltmeter reading of 0.707 V rms.

(3) Set the A coupling switch to DC, the B couplingswitch to GND, and the gain switch to 10. 5'9 BATTERY TEST CALIBRATE

(1) Set the Power switch to OFF (pushbutton OUT) and(4) Monitor the 113's output with the precision rms the BATTERY -|-EST tOgg|e switch to either ~+~ or

voltmeter. "—". If the BATTERY TEST toggle switch is left inthe center (off) position, the external supply will be

(5) Adjust the signal generator to produce a reading of 1 shorted outV rms @ 10 kHz.

(2) Connect the negative terminal of the variable dc(6) Set the |_F Rollgff control to 1 kHz_ supply to the brown lead of the Battery Test lamp.

(7) Adjust C200 to obtain exactly the same voltage (3) Connect the positive lead of the supply to terminal

reading as in step (5) above. #37 of the PC board‘

(4) Slowly adjust the supply to the point where the lamp5.8 HIGH FREQUENCY ROLLOFF Comesm

COMPENSATION CAUTION: DO NOT EXCEED 13 V DC.

(1) Connect the 10:1, attenuator to the output of the (5) If necessary, adjust R309 until the test lamp comes onsignal generator, and connect the output of the at 11 V (i0.1 V) dc. The lamp should not come onattenuator to the Model 113's A input. below 10.7 V dc.

SECTION VI SAFETY NOTICEWARNING! POTENTIALLY LETHAL VOLTAGES ARE PRESENT INSIDE THIS APPARATUS. THESE SER-VICE INSTRUCTIONS ARE FOR USE BY QUALIFIED PERSONNEL ONLY. TO AVOID ELECTRIC SHOCK,DO NOT PERFORM ANY SERVICING OTHER THAN THAT CONTAINED IN THE OPERATING INSTRUC-TIONS UNLESS YOU ARE QUALIFIED TO TO SO. Any adjustment, maintenance and repair of the openedapparatus under voltage shall be avoided as far as possible and, if unavoidable, shall be carried out onlyby a skilled person who is aware of the hazard involved. When the apparatus is connected to a powersource, terminals may be live, and the opening of covers or removal of parts is likely to expose live parts.The apparatus shall be disconnected from all voltage sources before it is opened for any adjustment,maintenance, or repair. Note that capacitors inside the apparatus may still be charged even if the ap-paratus has been disconnected from all voltage sources. Service personnel are thus advised to waitseveral minutes after unplugging the instrument before assuming that all capacitors are discharged. Ifany fuses are replaced, be sure to replace them with fuses of the same current and voltage rating and ofthe same type. The use of makeshift fuses and the short-circuiting of fuse holders are prohibited.

V-2

kHz, the LF Rolloff switch to DC, and set the Gain \\

I

(4) Connect the precision rms voltmeter to the 113'5 output jack.

(5) Adjust R221 for exactlv the same reading as set in step (3). NOTE: This adjustment trims the gain only in the 2 k, 5 k, and 10 k positions of the Gain switch.

5.7 LOW FREQUENCY ROLLOFF COMPENSATION

(1) Set the HF Rolloff control to 100 kHz, and set the LF Rolloff to DC.

(2) Connect the signal generator to the 10: 1 attenuator, and connect the attenuator output to the Model 113'5 A input.

(3) Set the A coupling switch to DC, the B coupling switch to GND, and the gain switch to 10.

(4) Monitor the 113's output with the precision rms voltmeter.

(5) Adjust the signal generator to produce a reading of 1 V rms @ 10 kHz.

(6) Set the LF Rolloff control to 1 kHz.

(7) Adjust C200 to obtain exactly the same voltage reading as in step (5) above.

5.8 HIGH FREQUENCY ROLLOFF COMPENSATION

(1) Connect the 10: 1 attenuator to the output of the signal generator, and connect the output of the attenuator to the Model 113's A input.

(2) Set the 113'5 A input coupling switch to DC, the B coupling switch to GND, the HF Rolloff switch to 300 kHz, the LF Rolloff switch to DC, and set the Gain switch to 10 (cal).

(3) Monitor the output of the signal generator with the precision rms voltmeter; the attenuator must remain connected to the signal generator so that a change of load does not occur that would change the signal amplitude. Adjust the.rms voltage to 1 V (exactly) @

300 kHz.

(4) Connect the precision rms voltmeter to the Model 113's output jack.

(5) Adjust C26 (on the HF Rolloff switch) to produce a voltmeter reading of 0.707 V rms.

5.9 BATTERY TEST CALIBRATE

(1) Set the Power switch to OFF (pushbutton OUT) and the BATTE RY TEST toggle switch to either "+" or "-". If the BATTERY TEST toggle switch is left in the center (off) position, the external supply will be shorted out.

(2) Connect the negative terminal of the variable dc supply to the brown lead of the Battery Test lamp.

(3) Connect the positive lead of the supply to term inal #37 of the PC board.

(4) Slowly adjust the supply to the point where the lamp comes on.

CAUTION: DO NOT EXCEED 13 V DC.

(5) If necessary, adjust R309 until the test lamp comes on at 11 V (±0.1 V) dc. The lamp should not come on below 10.7 V dc.

SECTION VI SAFETY NOTICE WARNING! POTENTIALLY LETHAL VOLTAGES ARE PRESENT INSIDE THIS APPARATUS. THESE SER· VICE INSTRUCTIONS ARE FOR USE BY QUALIFIED PERSONNEL ONLY. TO AVOID ELECTRIC SHOCK, DO NOT PERFORM ANY SERVICING OTHER THAN THAT CONTAINED IN THE OPERATING INSTRUC· TIONS UNLESS YOU ARE QUALIFIED TO TO SO. Any adjustment, maintenance and repair of the opened apparatus under voltage shall be avoided as far as possible and, if unavoidable, shall be carried out only by a skilled person who is aware of the hazard involved. When the apparatus is connected to a power source, terminals may be live, and the opening of covers or removal of parts is likely to expose live parts. The apparatus shall be disconnected from all voltage sources before it is opened for any adjustment, maintenance, or repair. Note that capaCitors inside the apparatus may still be charged even if the ap· paratus has been disconnected from all voltage sources. Service personnel are thus advised to wait several minutes after unplugging the instrument before assuming that all capacitors are discharged. If any fuses are replaced, be sure to replace them with fuses of the same current and voltage rating and of the same type. The use of makeshift fuses and the short-circuiting of fuse holders are prohibited.

V-2

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SECTION VI TROUBLESHOOTING

6.1 INTRODUCTION

Although the Model 113 is a reliable instrument, occasional troubleshooting may be necessary; the procedures outlined in this section will be helpful. Once the problem is isolated to a specific circuit or component, or before attempting any troubleshooting, the user should contact Princeton Appl ied Research Corporation for advice on the relative merits of repairing the instrument himself, as opposed to returning it to the factory for repair. In any case, if the instrument is still in WARRANTY, it is particularly important that an authorized factory representative be contacted prior to attempting a field repair, as failure to do so could inval idate the Warranty.

6.2 PROCEDURE

To speed the troubleshooting process, try to determine any external causes of the trouble, and ascertain the symptoms when the amplifier is properly connected and tested. The set-up and procedure given in Initial Checks, Section II, will be helpful in determining the symptoms. Section IV, the Circuit Description, together with th.e layout diagrams and schematics (Section VII), should provide sufficient infor­mation for isolating the trouble. After checking the power supply Voltages, the two ampl ifier stages may be checked by comparing output signals against input signals. After signal checks isolate the trouble to one of the amplifier stages or to the overload circuit, voltage and resistance checks can then specifically pinpoint the trouble. When doing resistance checks, it is sometimes possible to locate a bad transistor by checking the diode action of the base and collector junctions. Wh ile doing voltage checks, it is usefu I to remember that the base-to-emitter voltage of a forward biased silicon transistor (or diode junction) is roughly 0.6 V, and that the collector voltage of a saturated transistor is less than the base voltage (measured with respect to the emitter).

When troubleshooting and replacement of bad components is completed, it will probably be necessary to adjust some of the amplifier trim-components. Section V, the Align­ment Procedure, should be consulted.

6.3 PRINTED CIRCUIT SOLDERING

If any components are removed from a printed-circuit board for inspection or replacement, be especially careful not to damage the foil. To remove components cleanly requires considerable care_ Either one of two methods can be used to remove the solder from a pad. One entails the use of a vacuum bulb operated solder remover, and the other the use of a "wick". Both methods give good results. A brief description of each follows.

METHOD #1

Removing solder by means of a solder-remover is a simple process. The required equipment includes a vacuum bulb

VI-'

operated solder remover (UNGAR type SOLDER-OFF #7805 recommended) and a good soldering iron of mod­erate power (WALL type 14HDG40120 with type W14KS tip). The solder must be removed from the pad on the side opposite the component. To remove a component, proceed as follows: Heat the pad on the side opposite the component. As soon as the solder flows, use the solder remover to remove the solder from the pad and hole. Take care not to heat any longer than necessary. After the solder has been removed, pull the lead through the hole from the component side of the board, using suitable long-nose pliers. If the lead is not free, continue to apply heat while pulling the lead from the hole. A component with leads which cannot be removed one at a time must have all of its leads free in the holes simultaneously; if it is not possible to free all of the leads in the holes, the component can be removed by apply ing heat to one of the leads and "rocking" the component to pull the lead through the hole as far as possible, and successively repeating this for each of the unfree leads until the component is free from the board. After the component has been removed, use the solder remover to completely clear all solder from the holes.

METHOD #2

Wicking is a method which uses a length of stranded wire or shielding braid as a wick to draw up the molten solder from the pad. Exceptionally clean work can be achieved by this method. Equipment required includes a good soldering iron (that recommended in Method #1 is excellent), a supply of stranded braid, and some rosin base soldering flux (ALPHA 346-35 or equivalent). Proceed as follows: Dip a few inches of stranded wire or shielding braid into the rosin-base soldering flux. Then place the wire or braid on top of the joint to be unsoldered, allowing some of the flux to flow over the joint. NOTE: Under no circumstances use an acid-base flux.

As shown in Figure VI-l, place a hot soldering iron on top of the stranded wire directly above the joint to be unsoldered. Within a few seconds, most of the solder in the joint will melt and flow quickly up the wick, leaving the joi nt area free of solder.

-===================~/ Figure VI-l. SOLDER REMOVAL BY WICKING

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l

Lift the soldering iron and remove the wick before it the component has been removed, use wicking to complete-

freezes to the joint. Cut off the “filled" end of the wick ly clear all solder from the holes.

(generally about ‘/2 inch should be removed). INSTALLING COMPQNENTS t,‘

ineleeet The i0in'E- ii enV Seidei remains. repeal The In returning the component or its replacement to the

Preeedufe as Fe<IlUiFed- Then, Wniie applying heat Te keel) board, make sure the leads are bent on the proper centers

the solder in the hole molten, pull the lead through the and that they don't angle in or out. If they do not pass

hole. Components with leads which cannot be removed one freely through the centers of the holes, they may catch the

at a time, such as transistors and trimpotentiometers, can edge of the foil and lift it. Bend and cut the leads afterbe removed by applying heat to one of the leads and inserting the component; then solder the leads with a hot“rocking" the component to pull the lead through the hole iron (no larger than 40 watts) and a good grade of rosin

as far as possible, and successively repeating this for each of core 60/40 solder. Be sure to apply heat no longer than

the leads until the component is free from the board. After necessary to achieve a good joint (usually a few seconds).

M

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VI-2

Lift the soldering iron and remove the wick before it freezes to the joint. Cut off the "filled" end of the wick (generally about % inch should be removed).

Inspect the joint. If any solder remains, repeat the procedure as required. Then, while applying heat to keep the solder in the hole molten, pull the lead through the

hole. Components with leads which cannot be removed one at a time, such as transistors and trimpotentiometers, can be removed by applying heat to one of the leads and "rocking" the component to pull the lead through the hole as far as possible, and successively repeating this for each of the leads until the component is free from the board. After

VI-2

the component has been removed, use wicking to complete­ly clear all solder from the holes.

INSTALLING COMPONENTS

In returning the component or its replacement to the board, make sure the leads are bent on the proper centers and that they don't angle in or out. If they do not pass freely through the centers of the holes, they may catch the edge of the foil and I ift it. Bend and cut the leads after inserting the component; then solder the leads with a hot iron (no larger than 40 watts) and a good grade of rosin core 60/40 solder. Be sure to apply heat no longer than necessary to achieve a good joint (usually a few seconds).

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Schematics, Table of

Components Location Oiagram

Block and Wiring Oiagram (4340·0·S0)

SECTION VII

SCHEMATICS

Oifferential Preamplifier Schematic (4332-0·S0, sheet')

Output Amplifier Schematic (4332-0·S0, sheet 2) . . .

Power Supply and Battery Test Circuit (4332-0·S0, sheet 3)

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APPENDIX A INSTALLATION INSTRUCTIONS FOR

DUAL RACK·MOUNTING KIT (1715·0008)

(1) Set the two Model 113's on a bench side by side.

(2) Remove the top cover of both units. The cover is secured by a single screw located on the under surface of the lip at the rear of the top cover. This screw is most easily removed by using a long screwdriver (or an extraordinarily short one). Once the screw has been remov­ed, simply slide the cover back to where it can be lifted free of the unit.

(3) Remove the bottom cover of both units. The bottom cover is held by the screws that secure the two rear rubber feet. When these screws are removed, the feet can be removed and the cover slid back and freed from the unit.

(4) From the sides that will be adjacent after mounting, remove the side decorative plate (secured by two screws) and the side panel. These will not be replaced. Do not remove the shim plates exposed when the decorative plates are removed.

(5) Using the two Allen head screws provided, secure the front coupling to one of the units. The shim plate exposed when the decorative strip was removed should be under the cou­pling.

(6) As shown in the photograph, install the lock­ing screw in the other instrument, taking care to retain the shim.

(7) Lock the front of the two units together by sliding the head of the locking screw into the coupling slot.

(8) Insert the rear mounting flange to secure the rear of the instruments together. The flange is simply pushed into the assembly from the rear.

(9) Reinstall the bottom and top covers, securing the assembly. The two instruments can now be picked up and handled. as a single assem­bly. This assembly can be mounted in any standard 19" rack. As long as the top and bot­tom covers of the individual instruments are secure, the two instruments will remain a single assembly. If the covers are removed, the two instruments will separate.

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