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Research ArticleEnergy-Efficiency Analysis of Per-Subcarrier Antenna Selectionwith Peak-Power Reduction in MIMO-OFDM Wireless Systems
Ngoc Phuc Le Le Chung Tran and Farzad Safaei
School of Electrical Computer and Telecommunications Engineering University of Wollongong Wollongong NSW 2522 Australia
Correspondence should be addressed to Ngoc Phuc Le pnl750uoweduau
Received 8 January 2014 Accepted 14 May 2014 Published 11 June 2014
Academic Editor Ahmad Safaai-Jazi
Copyright copy 2014 Ngoc Phuc Le et al This is an open access article distributed under the Creative Commons Attribution Licensewhich permits unrestricted use distribution and reproduction in any medium provided the original work is properly cited
The use of per-subcarrier antenna subset selection in OFDM wireless systems offers higher system capacity andor improved linkreliabilityHowever the implementation of the conventional per-subcarrier selection schememay result in significant fluctuations ofthe average power and peak power across antennas which affects the potential benefits of the system In this paper power efficiencyof high-power amplifiers and energy efficiency in per-subcarrier antenna selection MIMO-OFDM systems are investigated Todeliver the maximum overall power efficiency we propose a two-step strategy for data-subcarrier allocation This strategy consistsof an equal allocation of data subcarriers based on linear optimization and peak-power reduction via cross-antenna permutationsFor analysis we derive the CCDF (complementary cumulative distribution function) of the power efficiency as well as the analyticalexpressions of the average power efficiency It is proved from the power-efficiency perspective that the proposed allocation schemeoutperforms the conventional scheme We also show that the improvement in the power efficiency translates into an improvedcapacity and in turn increases energy efficiency of the proposed system Simulation results are provided to validate our analyses
1 Introduction
The last few years have seen an increasing demand for veryfast data speeds in wireless multimedia applications Mean-while reducing energy consumption in wireless networkshas become a problem of concern among academic andindustrial communities As a result high-speed systems withhigh-energy efficiency has emerged as a main stream fordesigning future wireless networks [1 2] The potential forimproving energy efficiency in wireless systems could be incomponent level link level or network level [1] From aphysical layer viewpoint it is well known that high-poweramplifier (HPAs) is a major source of RF (radio frequency)power consumption For example in mobile networks HPAsconsume up to 50ndash80 of overall power at a base station [13]Thus increasing power efficiency ofHPAs is of importanceto achieve high energy-efficient wireless networks
To date MIMO-OFDM (multi-input multi-outputorthogonal frequency division multiplexing) has beenconsidered as a key technique for high-speed wirelesstransmission [4] This is mainly because OFDM could
offer high spectral efficiency and robustness againstintersymbol interference in multipath fading channelsAlso an increase in capacity andor diversity gains could beachieved with MIMO [5 6] In fact MIMO-OFDM has beenadopted in current and future standards such as WiMAXWLAN 80211n or LTE-Advanced Among various MIMOschemes antenna selection appears to be promising forOFDM systems This MIMO scheme requires a low-costimplementation and small amount of feedback informationcompared to other precoding or beamforming methods [7]
Many research works have considered the applicationof antenna selection in OFDM systems for example see[8ndash12] To achieve a large coding gain resulting from thefrequency-selective nature of the channels a per-subcarrierantenna selection (ie selecting antennas on each subcarrierbasis) is applied [9] However as thismethod selects antennasindependently on each subcarrier a large number of datasymbols may be allocated to some antennas depending onthe channel condition As a result the peak power andaverage power of the signals on these antennas might bevery large whereas those on the other antennas might be
Hindawi Publishing CorporationInternational Journal of Antennas and PropagationVolume 2014 Article ID 313195 13 pageshttpdxdoiorg1011552014313195
2 International Journal of Antennas and Propagation
small The fluctuation of the powers clearly affects the powerefficiency of HPAs or distorts signals which in turn reducesthe potential benefits of the antenna selectionOFDM systems[13]
One possible approach to deal with the problem ofimbalance allocation of data subcarriers is selecting antennasunder a constraint that the number of data subcarriersallocated to each antenna is equal Some research workshave studied such a constrained selection approach in theliterature for example see [10ndash12] In [10] an ad hoc algo-rithm was developed to realize the constrained selectionscheme Meanwhile the authors in [11] considered linearoptimization to devise the constrained selection scheme Itwas shown that the selection scheme based on optimizationcould offer a better performance than the suboptimal solutionin [10] In [12] we generalized the approach in [11] to thesystem with an arbitrary number of multiplexed data streamsand analyzed the performance directly in nonlinear fadingchannels However all of these works only study the efficacyof the constrained selection scheme from error-performanceperspective Moreover even though the same number of datasubcarriers is allocated to each transmit antenna (ie allantennas have an equal average power) an occurrence of highpeak-to-average power ratio (PAPR) still affects the systemDespite an increasing concern about energy consumption inwireless networks to the best of our knowledge a research onenergy efficiency in the context of antenna selection MIMO-OFDM systems is still missing
It is also essential to emphasize the need of research onimproving energy efficiency in antenna selection MIMO-OFDM systems First per-subcarrier antenna selectionMIMO configurations need multiple active RF (radio fre-quency) chains which immediately raises a concern aboutenergy consumption compared to single RF-chain OFDMsystems Second OFDM inherently suffers from a high PAPRproblem which leads to a poor power efficiency of HPAs[13 14] In per-subcarrier antenna selection OFDM systemsthis effect is intuitively more serious due to a combinationof the high PAPR and power fluctuation resulting from animbalance allocation of data subcarriers This problem alsobecomes crucial in the OFDM systems where linear scaling(ie scale the peak power of the time-domain OFDM signalsto the saturation level of the HPAs [15ndash17]) is implemented torealize OFDM transmissions with no nonlinear distortions
In this paper per-subcarrier antenna selection MIMO-OFDM systems with linear scaling are investigated froman energy perspective for the first time The importantcontributions of this work include (a) the analysis of powerefficiency ofHPAs and energy efficiency and (b) the proposedstrategy to improve these useful performance metrics Themain results are summarized as follows
(1) A two-step data allocation strategy is proposed todeliver a maximum overall power efficiency of HPAsThis strategy consists of an equal allocation of datasubcarriers among transmit antennas based on linearoptimization and a peak-power reduction algorithmvia cross-antenna permutations
(2) Analytical expressions characterizing the achievedpower efficiency of HPAs including the CCDFs(complementary cumulative distribution function)and the average power efficiency are derived It isproved that from the power-efficiency viewpoint theproposed allocation scheme outperforms the conven-tional scheme
(3) The improvements in capacity and energy efficiencyresulting from the improved power efficiency ofHPAsare analyzed
Numerical results are provided to verify the analyses as wellas demonstrate the benefits in terms of the power efficiencyof HPAs and capacity as well as energy efficiency
The remainder of the paper is organized as follows InSection 2 a per-subcarrier antenna subset selection MIMO-OFDM system with linear scaling is described In Section 3a data allocation strategy that could allocate evenly data sub-carriers across antennas with a low peak power is proposedAnalysis of power efficiency is carried out in Section 4 Theachievable capacity and energy efficiency are considered inSection 5Numerical results are provided in Section 6 FinallySection 7 concludes the paper
Notation A bold letter denotes a vector or a matrix whereasan italic letter denotes a variable (sdot)119879 (sdot)119867 119864sdot and det(sdot)denote transpose Hermitian transpose expectation anddeterminant of a matrix respectively otimes denotes the Kro-necker product I
119899indicates the 119899times119899 identity matrix and 1
119870
is a119870times 1 vector of onesR indicates the set of real numbers
2 Antenna Selection for MIMO-OFDMSystems with Linear Scaling
21 SystemModel Weconsider aMIMO-OFDMsystemwith119870 subcarriers 119899
119879transmit antennas and 119899
119877receive antennas
as shown in Figure 1 At the transmitter the input data aredemultiplexed into 119899
119863independent data streams Each data
stream is then mapped onto 119872-QAM (119872-ary quadratureamplitudemodulation) constellations For the 119896th subcarrierwe denote 119906
119896
119897and 119909119896
119894 1 le 119897 le 119899
119863 1 le 119894 le 119899
119879
0 le 119896 le 119870 minus 1 to be the symbols that the subcarrierblock takes at its 119897th input and outputs at its 119894th outputrespectively The allocation block assigns the elements ofu119896
= [1199061198961 1199061198962 119906119896
119899119863]119879to 119899119863selected antennas at the 119896th
subcarrier based on feedback information As a result only119899119863elements in a vector x
119896= [1199091198961 1199091198962 119909119896
119899119879]119879 are assigned
values from u119896 whereas the others are zeros It is assumed
that 119864u119896u119867119896 = 1205902I
119899119863 The output sequences from the
subcarrier allocation block are then fed into 119870-point IFFT(inverse fast Fourier transform) blocks In this paper theNyquist sampling signal is considered Thus the discrete-time baseband OFDM signals can be expressed as
119904119894 (119899) =
1
radic119870
119870minus1
sum119896=0
119909119896
1198941198901198952120587119899119896119870
0 le 119899 le 119870 minus 1 1 le 119894 le 119899119879
(1)
International Journal of Antennas and Propagation 3
Inputdata
Symbolmapping
Subcarrierallocation
IFFTadd GI
Linearscaling
NonlinearHPA
1
nD nT
Dem
ultip
lexe
r
Symbolmapping
IFFTadd GI
NonlinearHPA
Antenna selection index from receiver
1 1
nD
Tx 1
Tx nT
(a)
middot middot middot
ChannelH
Remove GIFFT
Rece
iver
proc
essin
g Estimateddata
Channel estimation andantenna selection decision
Remove GIFFT
To transmitter
Rx 1
Rx nR
(b)
Figure 1 A simplified block diagram of a MIMO-OFDM system with per-subcarrier transmit antenna selection
For simplicity we consider ideal predistortion HPAs(ie soft envelope limiters) with a unity gain and class-Aoperation To deliver the maximum power efficiency withno nonlinear distortions in the system with nonlinear HPAsthe peak power across transmit antennas is linearly scaledto the saturation level 119875sat of the HPAs In addition asfeedback information (ie the selected antenna indiceswhichare calculated based on the channel state information) isdeployed by the transmitter all transmit branches are scaledwith the same scaling factor [16] Thus the signal after linearscaling can be expressed as
119904119894 (119899) = radic120572119904
119894 (119899) (2)
where the scaling factor 120572 = 119875sat119875 and the peak poweracross antennas 119875 = max119904
119894(119899)|119899 = 0 119870 minus 1 119894 =
1 119899119879 Each time-domain OFDM signal is then amplified
by the HPA before being transmitted via its correspondingtransmit antenna
At the receiver the received signal at each antenna is fedinto the FFT block after the GI (guard interval) is removedThe systemmodel in the frequency domain corresponding tothe 119896th subcarrier can be expressed as
y119896= radic120572H
119896x119896+ n119896
= radic120572H119896u119896+ n119896
(3)
where
x119896= [119909119896
1119909119896
2sdot sdot sdot 119909119896
119899119879]119879
H119896=
[[[[
[
ℎ119896
11ℎ11989612
sdot sdot sdot ℎ1198961119899119879
ℎ11989621
ℎ11989622
sdot sdot sdot ℎ1198962119899119879
sdot sdot sdot sdot sdot sdot sdot sdot sdot sdot sdot sdot
ℎ1198961198991198771
ℎ1198961198991198772
sdot sdot sdot ℎ119896119899119877119899119879
]]]]
]
y119896= [119910119896
11199101198962
sdot sdot sdot 119910119896119899119877]119879
n119896= [119899119896
11198991198962
sdot sdot sdot 119899119896119899119877]119879
(4)
In the above equations ℎ119896119895119894indicates the channel coefficient
between the 119894th transmit antenna and the 119895th receive antennaThe effective channel matrix H
119896is obtained by eliminating
the columns of H119896corresponding to the unselected transmit
Table 1 Antenna subsets (119899119879= 4 119899
119863= 2 and Γ = 6)
120574 Γ120574
1 1 2
2 1 3
3 1 4
4 2 3
5 2 4
6 3 4
antennas 119910119896119895and 119899119896119895denote the received signal and the noise
at the 119895th receive antenna respectively Here the noise ismodeled as a Gaussian random variable with zero mean and119864n119896n119867119896 = 1205902119899I119899119877 We assume that the receiver can perfectly
estimate the channel coefficients for example using a block-type pilot arrangement for channel estimation [18]
22 Per-Subcarrier Antenna Subset Selection In a MIMO-OFDM system with the conventional per-subcarrier antennasubset selection antenna subsets are selected independentlyfor each subcarrier [9] On each subcarrier only 119899
119863antennas
out of 119899119879available transmit antennas are active Denote
Γ120574 120574 = 1 2 Γ to be the 120574th subset consisting of 119899
119863
selected transmit antennas where Γ = (119899119863119899119879
) = 119899119879119899119863(119899119879minus
119899119863) is the number of all possible 119899
119863-element subsets Each
subset consists of 119899119863transmit antenna indices that are chosen
based on the feedback information from the receiver Forexample when 119899
119879= 4 and 119899
119863= 2 then Γ = 6 and all possible
subsets Γ120574 120574 = 1 2 6 are defined in Table 1 The choice
of the best antenna subset depends on a particular selectioncriterion
Several antenna selection criteria such as maximumcapacity or maximum SNR (signal-to-noise ratio) [19] canbe extended to this system In this paper we consider thecapacity criterion Accordingly the optimal subset at the119896th subcarrier is determined by maximizing the mutualinformation of the 119896th subchannel that is
Γ120574lowast (119896) = arg max
Γ120574 120574=1Γ
119868119896
120574 (5)
where
119868119896
120574= log2(det(I
119899119877+
120588
119899119863
H119896H119867119896)) (6)
4 International Journal of Antennas and Propagation
is the instantaneous mutual information associated with the119896th subchannel [5] Here 120588 = 119875
1199051205902119899
= 12057211989911986312059021205902119899 and
119875119905= 1205721198991198631205902 is the total transmit power per subchannel Also
we have assumed in (6) that the transmit power is allocateduniformly across antennas This is due to the fact that thefeedback information in our system is only the selectedantenna indices (ie not sufficient enough to perform powerallocation algorithms across subcarriers as well as antennas)The average mutual information across subcarriers can nowbe expressed as
119868 (120588H) =1
119870
119870minus1
sum119896=0
119868119896
120574lowast (7)
3 A Proposed Strategy forPeak-Power Reduction
In Section 2 we have described the MIMO-OFDM systemwith the conventional selection scheme It can be noted thatthe number of data subcarriers assigned to each transmitantenna might be significantly different depending on thechannel condition In the systemwith identical linear scalingto achieve the maximal overall power efficiency of HPAs thepeak power across antennas should be as small as possibleWe note that the peak power of the signal on each branchdepends on both the transmitted constellation symbols andthe number of data subcarriers allocated in each OFDMsymbol (cf (1)) Thus it is not sufficient to reduce the peakpower by solely implementing PAPR reduction techniquesMore specifically PAPR reduction techniques themselvescannot solve the problem of imbalance allocation of datasubcarriers across antennas To reduce the peak power acrossantennas we propose a two-step strategy consisting of thefollowing
Step 1 Allocate the same number of data subcarriers to alltransmit antennas (ie selecting antennas under a constraintthat all antennas have the same number of data subcarriersas illustrated in Figure 2(b)) Once this is achieved thetime-domain signals on all transmit branches have the sameaverage power Moreover as we will mathematically prove inSection 41 the peak power across antennas is reduced
Step 2 Reallocate data symbols across antennasThis processwill alter the statistical distribution of signals and thus furtherreduce the peak power
We note that this paper does not focus on developingoriginal techniques for either equal allocation of data subcar-riers or peak-power reduction Instead we are interested inanalyzing power efficiency of HPAs and energy efficiency inper-subcarrier antenna selection OFDM systems which hasnot been considered so far The two steps in our proposedstrategy described in Sections 31 and 32 are accomplishedby extending the suitable approaches available in the litera-ture to the context of the considered system
31 Optimal Equal Allocation of Data Subcarriers The opti-mal constrained antenna selection scheme based on linearoptimization was considered in [11 12] to improve error per-formance of OFDM systems suffering nonlinear distortionsdue to HPAs We now consider this method for the first stepof our strategy to achieve a better power delivery in a linearlyscaled MIMO-OFDM system Specifically we define a vari-able 119911
119896
120574 where 119911119896
120574= 1 if Γ
120574is chosen for the 119896th subcarrier
and 119911119896120574= 0 otherwise Also denote 119888119896
120574to be the cost associated
with the chosen subset Γ120574 Here 119888119896
120574= 119868119896120574as the maximum
capacity criterion is considered By denoting vectors z =
(11991101 1199110
Γ 11991111 1199111
Γ 119911119870minus1
1 119911119870minus1
Γ)119879
isin 0 1119870Γtimes1 and
c = (11988801 1198880
Γ 11988811 1198881
Γ 119888119870minus1
1 119888119870minus1
Γ)119879
isin R119870Γtimes1 anoptimal solution for an equal allocation of data subcarriersis obtained by solving the following linear optimizationproblem [11 12]
maxzisin01119870Γtimes1
c119879z
subject to Az = a(8)
where A1= I119870otimes 1119879Γisin 0 1
119870times119870Γ A2= 1119879119870otimes IΓisin 0 1
Γtimes119870ΓA = (A119879
1A1198792)119879
isin 0 1(119870+Γ)times119870Γ a = (1119879
119870120582119879)119879 and 120582 =
(1205821 1205822 120582
Γ)119879 where 120582
120574is the number of times that the
subset Γ120574is selected The constraint in (8) means that only
119899119863antennas are allowed to transmit data symbols on each
subcarrier and all transmit antennas have the same numberof allocated data subcarriers It is important to note that thisbinary linear optimization problem can be relaxed to linearprogramming with integral solutions [12] Hence (8) can besolved efficiently by the known linear programmingmethodssuch as the simplex methods or interior point methods [20]
32 Data Allocation with Peak-Power Reduction To furtherreduce the peak power of the whole system various availablePAPR reduction techniques (eg see [14] and the referencestherein) can be now adopted In this paper we are interestedin a selected mapping (SLM) technique [21] as SLM is adistortionless PAPR technique that could achieve a goodPAPR reduction [14 21] One of the most important steps inSLM is creating a set of candidates that represents the samedata information To exploit the available degrees of freedomin multiple-antenna systems for peak-power reduction wepropose to create a set of candidates using cross-antennapermutations In the literature a SLM-based scheme thatcould exploit the available degrees of freedom was firstdeveloped in [22] The scheme in [22] creates candidatesby performing cross-antenna rotation and inversion (CARI)based on a defined random matrix However that scheme isproposed for an Alamouti code basedMIMO-OFDM systemonly In a per-subcarrier antenna selection OFDM systemCARI cannot be implemented directly as only 119899
119863out of 119899
119879
antennas are active on each subcarrier To create candidates inour scheme we perform cross-antenna permutations insteadof CARI In addition we utilize an antenna allocation patternthat is already known by the transmitter and receiver insteadof storing a defined random matrix at both transmitter and
International Journal of Antennas and Propagation 5
Antennas
Subcarriers
Tx 1
Tx 2
Tx 3
Tx 4
Data
Not used
(a) Unbalanced-power selection
Data
Not used
Antennas
Subcarriers
Tx 1
Tx 2
Tx 3
Tx 4
(b) Balanced-power selection
Figure 2 Illustration of per-subcarrier antenna subset selection (119899119879= 4 119899
119863= 2 and 119870 = 12)
Ant
enna
s
Subcarriers
1st candidate(original)
x11 x
21
x12
x32
x33 x
43
x24 x
44
0 0
0
00
0 0
0
(a)
2nd candidate (permutedata on the 1st antenna)
Subcarriers
x12 x
24 0 0
00
00
0 0
x11 x
32
x33 x
43
x44
x21
(b)
3rd candidate (permutedata on the 2nd antenna)
Subcarriers
Ant
enna
s
x12
x21 0 0
00
00
0 0
x11 x
33
x32 x
43
x44
x24
(c)
4th candidate (permutedata on the 3rd antenna)
Subcarriers
0 0
00
00
0 0
x11 x
21
x12 x
33
x32 x
44
x43x
24
(d)
Figure 3 Illustration of cross-antenna permutations (119899119879= 4 119899
119863= 2 and 119870 = 4)
receiver as in [22] The proposed algorithm is described asfollows
(1) Create 119882 candidates by performing cross-antennaspermutations An illustration of this process in thesystem with 119899
119863= 2 119899
119879= 4 and 119870 = 4 is
shown in Figure 3 Accordingly the first candidateis the original data allocation The second candidateis obtained by permuting all symbols on the firstantennas with their associated symbols on the otherantennasThe third and fourth candidates are createdin a similar manner To obtain a larger number ofcandidates all symbols on the antenna that are goingbe permutated need first have their phase rotated (iebeing multiplied with an element of a phase set ega 4-phase set is 0 1205872 120587 31205872)
(2) Calculate the peak powers of all available candidates(3) Select the candidate with the minimum peak power
for transmission
To recover the transmitted data the transmitter needs toinform the receiver which candidates have been selectedThus the number of side information bits in this scheme islog2119882 which is similar to that in [22]
33 Complexity Considerations In this subsection the com-plexity of the proposed allocation scheme is compared tothat of the conventional (imbalance) allocation scheme Inthe first step of the proposed scheme to realize an equalallocation of data subcarriers the optimization problem in (8)
needs to be solved at the receiverWenote that this linear opti-mization problem can be solved in polynomial time Morespecifically the complexity to solve this problem using inte-rior point methods can be reduced to 119874([(119870Γ)
3 ln(119870Γ)]120585)
where119874(sdot) denotes an order of complexity and 120585 is the bit sizeof the optimization problem [23] In addition it is noted thatthis step is transparent to the transmitter (ie no additionalcomplexity is required at the transmitter) In the secondstep a major additional complexity lies in the required IFFToperations due to additional 119882 candidates As an 119870 point-IFFT requires 119870log
2119870 complex additions and (1198702)log
2119870
complex multiplications the numbers of complex additionsand complex multiplications in the conventional scheme are119899119879119870log2119870 and 119899
119879(1198702)log
2119870 respectivelyMeanwhile in the
proposed scheme with 119882 candidates 119882119899119879119870log2119870 complex
additions and 119882119899119879(1198702)log
2119870 complex multiplications are
required However as we will show analytically in Section 4and numerically in Section 6 an improvement in the peak-power reduction reduces when 119882 becomes large Thus asmall value of 119882 is generally chosen which does not incurmuch additional complexity Finally the amount of feedbackinformation in the proposed scheme is similar to that in theconventional scheme
4 Analysis of Power Efficiency
41 Statistical Distribution of Peak Power Before proceedingto analyze the power efficiency of HPAs we need to investi-gate the distribution of the peak power of the MIMO-OFDMsignals (ie the peak power across transmit antennas) We
6 International Journal of Antennas and Propagation
consider the complementary cumulative distribution func-tion (CCDF) of the peak power defined as the probability thatthe peak power 119875 exceeds a given threshold 119875
0 that is
CCDF119875 (1198750) = Pr (119875 gt 119875
0) (9)
Note that although a procedure for calculating CCDF ofPAPR in OFDM systems is known to the best of ourknowledge all the CCDF expressions with respect toMIMO-OFDM signals available in the literature assume that all datasubcarriers are active which can be considered as a specialcase in the considered system when all the transmit antennashave the same number of allocated data symbols In thefollowing we calculate the CCDF of the peak power in oursystem
Let us begin with the discrete-time OFDM signal 119904119894(119899)
119899 = 0 1 119870minus1 corresponding to the 119894th transmit antennaThe peak power of this signal is defined as
119875119894= max0le119899le119870minus1
|119904119894 (119899) |2 (10)
For analytical tractability we assume that both the real partand imaginary part of the signal 119904
119894(119899) are asymptotically
independent and identically distributed Gaussian randomvariables Note that this assumption which is based on thecentral limit theorem [24] only holds when the number ofassigned data subcarriers on the 119894th antenna denoted as119870119894 is large enough As a result |119904
119894(119899)| follows the Rayleigh
distribution and |119904119894(119899)|2 has a chi-square distribution with
two degrees of freedom The probability density function ofthe signal |119904
119894(119899)|2 can be expressed as [24]
119901|119904|2 (
100381610038161003816100381611990411989410038161003816100381610038162) =
1
1205902119870119894
119890minus|119904119894|21205902
119870119894 (11)
where 1205902119870119894
= 1205902119870119894119870 is the variance of the signal |119904
119894(119899)| Note
that sum119899119879
119894=1119870119894
= 119899119863119870 thus we have sum
119899119879
119894=11205902119870119894
= 1198991198631205902 The
CDF (cumulative distribution function) of the signal |119904119894(119899)|2
is given as
Pr (100381610038161003816100381611990411989410038161003816100381610038162le 120579) = 1 minus 119890
minus1205791205902
119870119894 120579 ge 0 (12)
Suppose that 119870 samples of |119904119894(119899)| 119899 = 0 1 119870 minus 1 are
independent the CDF of the peak power 119875119894can be expressed
as
CDF119875119894 = Pr (119875119894le 1198750)
= Pr (1003816100381610038161003816119904119894 (0)10038161003816100381610038162le 1198750)Pr (1003816100381610038161003816119904119894 (1)
10038161003816100381610038162le 1198750) sdot sdot sdot
Pr (1003816100381610038161003816119904119894 (119870 minus 1)10038161003816100381610038162le 1198750)
= (1 minus 119890minus1198750120590
2
119870119894 )119870
(13)
In MIMO-OFDM systems with linear scaling the peakpower across transmit antennas 119875 can be defined as
119875 = max1le119894le119899119879
119875119894 (14)
Given the statistical independence of data among transmitantennas which is the case in the considered spatial mul-tiplexed OFDM system the CDF of the peak power 119875 iscalculated as
CDF119875 = Pr (119875 le 1198750)
= Pr (1198751le 1198750)Pr (119875
2le 1198750) sdot sdot sdotPr (119875
119899119879le 1198750)
=
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
(15)
Therefore the CCDF of the peak power of the antennaselection MIMO-OFDM signals can be expressed as
CCDF119875imbalance (1198750) = 1 minus CDF119875
= 1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
(16)
In the MIMO-OFDM system with a power balancingconstraint the number of allocated data subcarriers pertransmit antenna is equal to one another (ie 119870
119894=
119899119863119870119899119879
= 119870 forall119894 = 1 2 119899119879) Thus the variances of the
signals are 1205902119870119894
= 1198991198631205902119899119879= 1205902119870 forall119894 = 1 2 119899
119879 As a result
the CCDF expression could be simplified to as
CCDF119875balance (1198750) = 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(17)
A comparison of the CCDF of the peak powers in the twosystems is presented in the following theorem
Theorem 1 In MIMO-OFDM transmission schemes that con-sist of inactive data subcarriers (eg per-subcarrier antennaselection) the probability of occurrences of high peak power isthe smallest when the same number of data symbols is allocatedto all transmit antennas that is
CCDF119875balance (1198750) le CCDF119875imbalance (1198750) (18)
Proof The proof is given in Appendix AWhen the peak-power reduction algorithm proposed in
Section 32 is implemented in theMIMO-OFDMsystemwitha power-balancing constraint the CCDF of the peak powercan be expressed as
CCDF119875balance+reduced (1198750) = (CCDF119875balance (1198750))119882
= (1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870)119882
(19)
where 119882 is the number of candidates that are assumed tobe independent Recall that by definition the CCDF value isalways smaller than one (cf (9)) Therefore the CCDF valuein (19) is smaller than that in (17) that is
CCDF119875balance+reduced (1198750) le CCDF119875balance (1198750) (20)
International Journal of Antennas and Propagation 7
42 Power Efficiency of HPAs We now analyze the powerefficiency (PE) of high-power amplifiers (HPAs) The drainefficiency of HPAs which is defined as a ratio between thepower drawn from the DC source 119875dc and the average outputpower 119875out is considered in this paper Denote 119875119894in and 119875119894out tobe the average input and output powers of the HPA for the119894th antenna respectively Recall that all HPAs are assumedto have a unity gain that is 119875119894out = 119875119894in forall119894 = 1 2 119899
119879
Hence the instantaneous overall power efficiency of HPAs inthe MIMO-OFDM system can be expressed as [16]
120578PE
=sum119899119879
119894=1119875119894out
119899119879119875dc
=sum119899119879
119894=1119875119894in
119899119879119875dc
= 1205721198991198631205902
119899119879119875dc
=1198991198631205902119875sat
119899119879119875dc
1
119875=
1198991198631205902
2119899119879
1
119875
(21)
In the above manipulations we have used the fact thatsum119899119879
119894=1119875119894in = 120572119899
1198631205902 and119875dc = 2119875sat for class-AHPAs regardless
of the average powers of the input time-domain signalsDenoting CCDFPE (120578PE
0) = Pr(120578PE gt 120578PE
0) to be the CCDF
of the power efficiency we obtain the following result withrespect to 120578
PE
Theorem 2 In per-subcarrier antenna selection MIMO-OFDM systems with linear scaling the probability of achievinghigh instantaneous overall power efficiency of HPAs is thelargest when all transmit antennas have the same number ofallocated data symbols that is
CCDFPEbalance (120578PE0) ge CCDFPEimbalance (120578
PE0) (22)
where
CCDFPEbalance (120578PE0) = (1 minus 119890
minus12120578PE0 )119899119879119870
CCDFPEimbalance (120578PE0) =
119899119879
prod119894=1
(1 minus 119890minus1198991198631198702119899119879119870119894120578
PE0 )119870
(23)
Proof From (18) and (21) it is readily to obtain (22) and (23)With respect to the average value of the overall power
efficiency from (21) we can express
120578PE
= 119864 120578PE =
1198991198631205902
2119899119879
1198641
119875 =
1198991198631205902
2119899119879
int1
119909119901 (119909) 119889119909 (24)
where 119901(119909) is the pdf (probability distribution function) ofthe peak power In the system with a balance constraint (ieonly use Step 1) the pdf of the peak power can be calculatedas
119901balance (119909) =119889
119889119909CDF119875balance (119909) =
119889
119889119909(1 minus 119890
minus1199091205902
119870)119899119879119870
=119899119879119870
1205902119870
119890minus1199091205902
119870(1 minus 119890minus1199091205902
119870)119899119879119870minus1
(25)
Hence
120578PEbalance =
1198991198631205902
2119899119879
int1
119909119901balance (119909) 119889119909
=119899119879119870
2int1198701205902
119870
1205902
119870
1
119909119890minus1199091205902
119870(1 minus 119890minus1199091205902
119870)119899119879119870minus1
119889119909
=119899119879119870
2int119870
1
1
119909119890minus119909
(1 minus 119890minus119909
)119899119879119870minus1
119889119909
(26)
Similarly the power efficiency of HPAs in the conventionalsystem is
120578PEimbalance =
1198991198631205902
2119899119879
int1
119909119901imbalance (119909) 119889119909
=1198991198631198701205902
2119899119879
int119870max120590
2
max
1205902
max
1
119909
119899119879
sum119895=1
119890minus1199091205902
119870119895
(1 minus 119890minus1199091205902
119870119895 ) 1205902119870119895
times
119899119879
prod119894=1
(1 minus 119890minus1199091205902
119870119894 )119870
119889119909
(27)
where 1205902max = max12059021198701
1205902119870119899119879
and 119870max = max1198701
119870119899119879When the peak-power reduction algorithm is also imple-
mented (ie the system employs both Steps 1 and 2) it isreadily from (20) and (21) that
CCDFPEbalance+reduced (120578PE0
) ge CCDFPEbalance (120578PE0
) (28)
where
CCDFPEbalance+reduced (120578PE0
) = 1 minus (1 minus (1 minus 119890minus12120578
PE0 )119899119879119870
)119882
(29)
Also the average power efficiency can now be calculated as
120578PEbalance+reduced =
1198991198631205902
2119899119879
int1
119909119901balance+reduced (119909) 119889119909
=119899119879119870119882
2int119870
1
1
119909119890minus119909
(1 minus 119890minus119909
)119899119879119870minus1
times (1 minus (1 minus 119890minus119909
)119899119879119870
)119882minus1
119889119909
(30)
It can be seen from (30) that the smaller the peak poweris reduced (ie the larger the number of candidates 119882 isused) the higher the power efficiency could be achievedNote that although the integrals in (26) (27) and (30) haveno closed-form solutions they can be evaluated numericallyAlso the average power efficiencies in (26) (27) and (30) aretaken with respect to the input data In other words they areconsidered as instantaneous power efficiencieswith respect tothe channel distribution Consequently the power efficiencyin the systems is obtained by averaging these values over thefading channel distribution
8 International Journal of Antennas and Propagation
5 Analyses of Capacity and Energy Efficiency
It has been shown in (22) and (28) that the proposed systemcould achieve a better power efficiency of HPAs than itscounterpart Thus when the power 119875dc is fixed it is intuitivethat an increased average power efficiency results in anincreased average transmit power and in turn leads to anincrease in the achievable rate Moreover an increase in thedata rate under a constant consumption power will translateinto an improvement in energy efficiency The achievedcapacity and energy efficiency are now investigated in thissection
51 System Capacity We begin by rewriting the mutualinformation in (7) with respect to the average SNR valueof 120588 = 119875
1199051205902119899 where 119875
119905= 120572119899
1198631205902 = 120578
PE119899119879119875dc (cf (21))
The ergodic capacity is then calculated by averaging themutual information over the fading channel distributionthat is 119862(120588) = 119864H119868(120588H) From (6) and (7) the mutualinformation in the proposed and conventional systems canbe expressed respectively as
119868 (120588proposedH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
(31)
119868 (120588imbalanceH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(32)
where 120588proposed = 120578PEproposed119899119879119875dc120590
2
119899and 120588imbalance =
120578PEimbalance119899119879119875dc120590
2
119899 Here 120578
PEproposed = 120578
PEbalance+reduced if the
peak-power reduction algorithm is implemented otherwise120578PEproposed = 120578
PEbalance Also H119896 in (31) denotes the effective
channel matrix on the 119896th subcarrier in the proposed systemwhich is obtainedwhen solving the problem in (8)This chan-nel matrix is generally different from the effective channelmatrix H
119896in the conventional system because the selected
antenna subset may be differentThe difference in the mutualinformation between the two systems can be now calculatedas
Δ119868 = 119868 (120588proposedH) minus 119868 (120588imbalanceH) =1
119870
119870minus1
sum119896=0
Δ119868119896 (33)
where
Δ119868119896= log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
minus log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(34)
For analytical simplicity we focus on the high-SNRregime At the high SNR the mutual information at the 119896thsubcarrier can be approximated as [25]
119868119896= log2(det(
120588
119899119863
Ω119896)) (35)
where
Ω119896= Ω (H
119896) =
H119896H119867119896 119899119877le 119899119863
H119867119896H119896 119899119877gt 119899119863
(36)
Thus the difference in the mutual information can berewritten as
Δ119868 =1
119870
119870minus1
sum119896=0
(log2(det(
120588proposed
119899119863
Ω119896))
minuslog2(det(
120588imbalance119899119863
Ω119896)))
= 119901log2
120578PEproposed
120578PEimbalance
minus1
119870
119870minus1
sum119896=0
Δ119896= 1198791+ 1198792
(37)
where 119901 = min(119899119863 119899119877)Ω119896= Ω(H
119896) and
Δ119896= log2(det (Ω
119896)) minus log
2(det (Ω
119896)) (38)
is the loss in the mutual information associated with the 119896thsubcarrier due to the constrained allocation Note that if bothsystems have the same selected antenna subset at the 119896thsubcarrier then Δ
119896= 0 otherwise Δ
119896gt 0Thus the total loss
in the mutual information Δ = (1119870)sum119870minus1
119896=0Δ119896gt 0
We have some important observations with respect to thevalue of Δ119868 in (37)
(i)The change in mutual information Δ119868 comes fromtwo sources The first source 119879
1is a benefit in mutual
information due to the improvement in the powerefficiency of HPAs The second source 119879
2is a penalty
that incurs because the chosen effective channelmatrices in the proposed system are different from theones in the conventional system(ii) For each channel realization thematrixH
119896is fixed
and the first term 1198791in (37) is a constant Thus the
value of Δ119868 depends on how the effective channelmatrix H
119896is selected in the constrained selection
scheme From this observation it is clear that tomake the value Δ119868 become as positive as possiblethe constrained selection method should result inthe cost penalty Δ as small as possible We note thatthe formulated optimization in (8) could achieve theminimum possible value of the total cost Hence it isexpected that the constrained selection scheme basedon linear optimization will guarantee the maximumachievable value of Δ119868 In addition to have an insightinto the cost penalty we derive the upper bound ofthe expected value of the cost penalty in Appendix BBased on the obtained bound it is observed that forfixed values of 119899
119879and 119899
119863 the cost penalty becomes
smaller with an increasing value of 119902 = max(119899119863 119899119877)
International Journal of Antennas and Propagation 9
(iii) As Δ gt 0 the upper bound of the capacityimprovement can be given as
Δ119862 = 119864H Δ119868 le 119901log2119864H
120578PEproposed
120578PEimbalance
(39)
In (39) we have used Jensenrsquos inequality of119864log(119909) le log(119864119909) as log(119909) is a concavefunction Based on this bound we could estimatethe maximum improvement in capacity that couldbe realized in the proposed system compared to itscounterpart
It is now necessary to evaluate the change in capacitythat is Δ119862 We note that although the distribution of themutual information at high SNRs can be well approximatedby a Gaussian distribution [25] it is still challenging toperform a mathematical evaluation of Δ119862 from a statisticalviewpoint This is mainly due to the fact that the two termsin (37) are complicated dependent random variables Thuswe perform a numerical evaluation of Δ119862 instead Figure 4plots the empirical CCDF of 119879
1 CDF of 119879
2 and CCDF
of Δ119868 In the figure ldquo119882 = 1rdquo stands for the case in whichonly Step 1 in Section 31 is implemented The results areobtained in the systems with 119899
119879= 4 119899
119863= 2 119899
119877= 2 119870= 128
and are averaged over 103 channel realizations Details aboutother simulation parameters are described in Section 6 Thenumerical results confirm that 119879
1gt 0 and 119879
2lt 0 Moreover
as shown in Figure 4(c) Δ119868 is always positive when the peak-power reduction algorithm is implemented (ie 119882= 4 and119882 = 8) For the case of 119882 = 1 the probability of ΔI beingpositive is significant Therefore the proposed system attainsa better ergodic capacity than that in the conventional systemThe achieved capacities in the considered systems will beprovided in Section 6
52 Energy Efficiency In this subsection we further exam-ine the efficacy of the proposed system from an energy-efficiency (EE) perspective Normalized energy efficiency(bitsHzJoule) in MIMO-OFDM systems can be defined as[3 26]
120578EE
=119862 (120588)
119875total (40)
where 119862(120588) is the achievable rate and the total powerconsumption per-subchannel is 119875total = 119899
119879119875dc + 119899
119879119875RF + 119875sp
where 119875RF is the RF power consumption in each transmitbranch excluding the associatedHPA and119875sp is the basebandprocessing power consumption It can be seen from (40)that given a fixed value of 119875total a comparison of energyefficiency achieved in the two systems is based on the capacitycomparison that has been analyzed in Section 51We are nowinterested in evaluating a useful metric of energy efficiency-spectral efficiency performance Recall that the average SNR120588 is given as 120588 = 119875
1199051205902119899= 120578
PE119899119879119875dc1205902
119899 Thus we can rewrite
the energy efficiency in (40) as a function of 119875dc as
120578EE
(119875dc) =119862 (120578
PE119899119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
(41)
Table 2 Simulation parameters
Parameter ValueBandwidth 528MHzFFT size 128Number of samples in zero-padded suffix 37Modulation scheme 4-QAMIEEE 802153a channel model CM1
The energy efficiency of the proposed and conventionalsystems can now be respectively expressed as
120578EEproposed (119875dc) =
119862proposed (120578PEproposed 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEproposed 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(42)
120578EEimbalance (119875dc) =
119862imbalance (120578PEimbalance 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEimbalance 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(43)
Similarly to the case of capacity we compare the energyefficiency achieved in the two systems by means of numericalresults in the next section Note that the calculation of energyefficiency in the proposed system (ie (42)) has assumed thata reduction in spectral efficiency due to the side informationas well as additional processing power required for the peak-power reduction algorithm is negligible In fact a reductionin spectral efficiency is very small For example in a systemwith 16-QAM FFT size of 128 119899
119863= 2 and 119882= 4 (ie 2 bits
are needed for side information) a spectral efficiency lossis 2 bits(128 times 4 times 2 + 2) bits = 019 Also it was shownin [27] that the additional power cost when implementingSLM schemes is minuscule Thus the proposed peak-powerreduction algorithm in Section 32 which is a SLM-basedscheme requires a small additional power cost
6 Numerical Results
In this section we provide numerical results to validatethe analyses mentioned in the previous sections as wellas demonstrate the effectiveness of the proposed allocationscheme over its counterpart A MIMO-OFDM system with119899119879= 4 119899
119863= 2 and 119899
119877= 2 is considered in our simulations
The system parameters are listed in Table 2These parametersare chosen based on the legacy WiMedia MB-OFDM UWB(Multiband-OFDM UWB) standard [28] Also the channelCM1 defined in the IEEE 802153a channel model [29] isbased on ameasurement of a line-of-sight scenario where thedistance between the transmitter and the receiver is up to 4mMoreover the multipath gains are modeled as independentlog normally distributed random variables We assume thatperfect channel state information is available at the receiverAlso the feedback link has no delay and is error-free
10 International Journal of Antennas and Propagation
Empirical CCDF of T110
0
10minus1
10minus2
minus2 0 2
W = 1
W = 4
W = 8
(a)
100
10minus1
10minus2
minus04 minus02 0
Empirical CDF of T2
(b)
Empirical CCDF of (T1 + T2)10
0
10minus1
10minus2
minus1 minus05 0 05 1 15 2
W = 1
W = 4
W = 8
(c)
Figure 4 Statistical distributions (note 1198792is independent of119882)
61 Evaluations of Peak-Power Distribution In Figure 5 weplot the CCDFs of the peak power of time-domain signalsThe analytical curves are based on (16) (17) and (19) Mean-while the simulation curves are empirical CCDF values Thesimulation result confirms that a system with the proposedallocation scheme offers a better CCDF performance than itscounterpart As expected the occurrence of high peak poweris significantly reduced when the peak-power reductionalgorithm is implemented Also it can be seen that theimprovement associated with this algorithm is reduced withincreasing 119882 In other words a very large value of 119882 whilerequiring higher complexity in terms on the number of IFFToperations results in a marginal improvement Thus it isreasonable to choose a relatively small value for 119882 (eg119882 = 4) It is also worth noting that the analytical curvesare relatively close to the simulation curves The small gapsexist due to the fact that the assumption of independentsamples |119904
119894(119899)| to obtain (13) does not strictly hold as we have
sum119870minus1
119899=0|119904119894(119899)|2 = 1205902119870
119894by Parsevalrsquos relation [24]
62 Evaluations of Power Efficiency of HPAs Figure 6 com-pares the CCDFs of the power efficiency achieved in theproposed and conventional systems It can be seen that theprobability of power efficiency being large highly likely occursin the proposed system compared to its counterpart Also
the simulation results agree well with the analytical resultsderived in (23) and (29) In Table 3 we compare the averagepower efficiencies Here the analytical values are obtainedaccording to (26) (27) and (30) Meanwhile the simulationvalues are empirical values based on the original definitionof the drain efficiency in (21) Also these values are averagedover the fading channel realizations It can be seen that thederived expressions approximate well the achieved powerefficiencies Table 3 also provides relative improvements ofthe power efficiencies achieved in the proposed system overthe conventional system Here only 120578
PE (Simulation) valuesare used for calculating these improvements It is clear thatthe proposed system could achieve a significant improvementin terms of average power efficiency
63 Evaluations of Capacity and Energy Efficiency Figure 7shows the system capacity inMbps (ie the normalized valuein (6) is scaled upwith the system bandwidth) versus the SNRvalue of 12059021205902
119899 It is clear that a systemwith the proposed allo-
cation scheme achieves a higher capacity than its counterpartThis agrees with the analysis in Section 51 that the changein capacity Δ119862 is positive In Figure 8 we plot the energyefficiency (MbitsJoule) versus spectral efficiency (MbpsHz)This figure is obtained based on (42) and (43) when varying119875dc Other parameters are 119875RF = 100mW 119875sp = 10mW and
International Journal of Antennas and Propagation 11
Table 3 A comparison of average power efficiencies
Imbalance Proposed (119882 = 1) Proposed (119882 = 4) Proposed (119882 = 8)120578PE (Simulation) 00697 00768 00894 00942
120578PE (Analysis) 00691 00757 00892 00943
Improvement120578PEproposed minus 120578
PEimbalance
120578PEimbalance
mdash 1019 2826 3515
1 2 3 4 5 6 7 8 9
100
10minus1
10minus2
10minus3
Peak power P0
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Pr (P
gtP0)
Figure 5 Comparison of CCDFs of the peak powers
002 004 006 008 01 012 014Power efficiency
CCD
F
100
10minus1
10minus2
10minus3
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Figure 6 Comparison of CCDFs of the power efficiencies
4500
4000
3500
3000
2500
2000
1500
1000
Ergo
dic c
apac
ity (M
bps)
2 4 6 8 10 12 14
SNR (dB)
3300
3200
3100
3000
2900
2800
97 98 99 10 101
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 7 Comparison of the ergodic capacities
12059021205902119899= 15 dB As expected the improvement in the power
efficiency of HPAs results in an improved energy efficiencyIn addition it can be observed that there exists an energyefficiency-spectral efficiency tradeoff in the systems Thistradeoff clearly needs to be taken into consideration whendesigning energy-efficient per-subcarrier antenna selectionbased OFDM wireless systems
7 Conclusions
In this paper a per-subcarrier antenna subset selectionMIMO-OFDM system with linear scaling has been investi-gated from an energy-efficiency perspective We have shownthat an imbalance allocation of data subcarriers associatedwith the conventional selection scheme affects the power effi-ciency of HPAs as well as the energy-efficiency of the wholesystem To deliver the maximum overall power efficiencywe have proposed the two-step strategy consisting of equalallocation data subcarriers across antennas and peak-powerreduction It has been proved from the power-efficiency view-point that the proposed allocation scheme outperforms theconventional scheme We have also derived the expressionsfor measuring the average power efficiency Moreover theimprovements in terms of capacity and energy efficiency
12 International Journal of Antennas and Propagation
0 2 4 6 8 10400
600
800
1000
1200
1400
1600
Spectral efficiency (MbpsHz)
Ener
gy effi
cien
cy (M
bits
J)
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 8 Energy efficiency versus spectral efficiency
resulting from the improved power efficiency have beenanalyzed The analytical results are validated by simulationresults The simulation result also shows that the systemwith the proposed allocation scheme could achieve a betterefficiency efficiency-spectral energy tradeoff compared to itscounterpart
Appendices
A Proof of Theorem 1
Let us consider a function 119891(120592) = 1 minus 119890minus1198750120592 0 lt 120592 le 1205902maxwhere 1205902max = max1205902
1198701 12059021198702
1205902119870119899119879
The second derivativeof this function is
11989110158401015840(120592) =
21198750120592 minus 11987520
1205924119890minus1198750120592 (A1)
From a HPAsrsquo viewpoint it is of interest to consider thesituation when the peak power across antennas 119875
0is large
Thus we consider the scenarios of 1198750
gt 21205902max where 1205902maxis the maximum average power across antennas Under thesesituations it is clear that 11989110158401015840(120592) lt 0 forall120592 isin (0 1205902max] Hencethe function 119891(120592) is concave By applying Jensenrsquos inequalitywe obtain the following inequality
1
119899119879
119899119879
sum119894=1
119891 (1205902
119870119894) le 119891(
1
119899119879
119899119879
sum119894=1
1205902
119870119894)
= 119891(1
119899119879
119899119879
sum119894=1
1205902
119870) = 119891 (120590
2
119870)
(A2)
where the equality comes from the fact that sum119899119879
119894=11205902119870119894
=
sum119899119879
119894=11205902119870
= 1198991198631205902 Expression (A2) can be rewritten as119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le 119899119879(1 minus 119890
minus11987501205902
119870) (A3)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879
On the other hand by applying the arithmetic-geometricmean inequality and note that (1 minus 119890
minus119909) gt 0 forall119909 gt 0 we have
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1
119899119879
119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ))
119899119879
(A4)
Note that the equality in (A4) holds if and only if 1205902119870119894
= 1205902119870
forall119894 = 1 119899119879
Combining (A3) and (A4) results in
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1 minus 119890minus1198750120590
2
119870)119899119879
(A5)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879 Thus we
get the following desired inequality
1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
ge 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(A6)
or
CCDF119875imbalance (1198750) ge CCDF119875balance (1198750) (A7)
This completes the proof
B Upper Bound of an ExpectedValue of Cost Penalty
In this appendix we derive an upper bound of the expectedvalue of Δ
119896 It can be seen from (5) that among all pos-
sible matrices H119896 the matrix H
119896with the highest value of
log2(det(Ω
119896))Ω119896
= Ω(H119896) will be selected as the effective
channel matrix for the 119896th subcarrier in the conventionalscheme Meanwhile in the proposed scheme due to thebalance constraint the effective channel matrix associatedwith the kth subcarrier is not necessarily the one with thehighest log
2(det(Ω
119896)) that is log
2(det(Ω
119896)) le log
2(det(Ω
119896))
Thus the expected value of Δ119896can be computed by using
order statistics In particular an upper bound on the expecteddifference of two-order statistics the Γth and 120574th 1 le 120574 lt Γis given by [30]
119864 Δ119896 = 119864 log
2(det (Ω
119896)) minus 119864 log
2(det (Ω
119896))
le 120590119862radic
Γ (120574 + 1)
120574
(B1)
where 1205902119862is the variance of log
2(det(Ω
119896)) that is assumed to
be the same for all possible matricesH119896
On the other hand suppose that the entries of the 119899119877times119899119879
matrixH119896are iid complex Gaussian random variables with
zero mean and unit variance then for any effective channelmatrix H
119896 Ω119896is a complex Wishart matrix It follows from
[25] that the variance of log2(det(Ω
119896)) can be expressed as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1205951015840(119902 minus 119898 + 1) (B2)
International Journal of Antennas and Propagation 13
where 119901 = min(119899119863 119899119877) 119902 = max(119899
119863 119899119877) and 1205951015840(119909) =
suminfin
120593=11(120593 + 119909 minus 1)
2 is the first derivative of the digammafunction By approximating 1205951015840(119909) asymp 1119909 [25] the simplerexpression for 1205902
119862in (B2) is given as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1
119902 minus 119898 + 1 (B3)
Substitute (B3) into (B1) we finally arrive at
119864 Δ119896 le log
2(119890)radic(
119901
sum119898=1
1
119902 minus 119898 + 1) times
Γ (120574 + 1)
120574 (B4)
Conflict of Interests
The authors declare that there is no conflict of interestsregarding the publication of this paper
References
[1] L M Correia D Zeller O Blume et al ldquoChallenges andenabling technologies for energy aware mobile radio networksrdquoIEEECommunicationsMagazine vol 48 no 11 pp 66ndash72 2010
[2] Z Hasan H Boostanimehr and V K Bhargava ldquoGreen cellularnetworks a survey some research issues and challengesrdquo IEEECommunications Surveys and Tutorials vol 13 no 4 pp 524ndash540 2011
[3] J Joung C K Ho and S Sun ldquoGreenwireless communicationsa power amplifier perspectiverdquo in Proceedings of the 4th Asia-Pacific Signal and Information Processing Association AnnualSummit and Conference (APSIPA ASC rsquo12) pp 1ndash8 December2012
[4] G L Stuber J R Barry S W Mclaughlin Y E Li M AIngram and T G Pratt ldquoBroadband MIMO-OFDM wirelesscommunicationsrdquoProceedings of the IEEE vol 92 no 2 pp 271ndash294 2004
[5] H Bolcskei D Gesbert and A J Paulraj ldquoOn the capacity ofOFDM-based spatial multiplexing systemsrdquo IEEE Transactionson Communications vol 50 no 2 pp 225ndash234 2002
[6] V Tarokh N Seshadri and A R Calderbank ldquoSpace-timecodes for high data rate wireless communication performancecriterion and code constructionrdquo IEEE Transactions on Infor-mation Theory vol 44 no 2 pp 744ndash765 1998
[7] C M Vithanage M Sandell J P Coon and Y Wang ldquoPrecod-ing in OFDM-based multi-antenna ultra-wideband systemsrdquoIEEE Communications Magazine vol 47 no 1 pp 41ndash47 2009
[8] Z Tang H Suzuki and I B Collings ldquoPerformance of antennaselection forMIMO-OFDMsystems based onmeasured indoorcorrelated frequency selective channelsrdquo in Proceedings of theAustralian Telecommunication Networks and Applications Con-ference pp 435ndash439 December 2006
[9] H Zhang and R U Nabar ldquoTransmit antenna selection inMIMO-OFDM systems bulk versus per-tone selectionrdquo inProceedings of the IEEE International Conference on Communi-cations (ICC rsquo08) pp 4371ndash4375 May 2008
[10] H Shi M Katayama T Yamazato H Okada and A OgawaldquoAn adaptive antenna selection scheme for transmit diversityin OFDM systemsrdquo in Proceedings of the IEEE 54th VehicularTechnology Conference (VTC rsquo01) pp 2168ndash2172 October 2001
[11] M Sandell and J P Coon ldquoPer-subcarrier antenna selectionwith power constraints in OFDM systemsrdquo IEEE Transactionson Wireless Communications vol 8 no 2 pp 673ndash677 2009
[12] N P Le F Safaei and L C Tran ldquoTransmit antenna subsetselection for high-rate MIMO-OFDM systems in the presenceof nonlinear power amplifiersrdquo EURASIP Journal on WirelessCommunications and Networking vol 2014 article 27 2014
[13] R PrasadOFDM for Wireless Communications Systems ArtechHouse 1st edition 2004
[14] T Jiang and Y Wu ldquoAn overview peak-to-average power ratioreduction techniques for OFDM signalsrdquo IEEE Transactions onBroadcasting vol 54 no 2 pp 257ndash268 2008
[15] H Ochiai ldquoPerformance analysis of peak power and band-limited OFDM system with linear scalingrdquo IEEE Transactionson Wireless Communications vol 2 no 5 pp 1055ndash1065 2003
[16] C Zhao R J Baxley and G T Zhou ldquoPeak-to-average powerratio and power efficiency considerations in MIMO-OFDMsystemsrdquo IEEE Communications Letters vol 12 no 4 pp 268ndash270 2008
[17] D Wulich and I Gutman ldquoImpact of linear power amplifier onpower loading in OFDM part I principlesrdquo in Proceedings ofthe IEEE 26th Convention of Electrical and Electronics Engineersin Israel (IEEEI rsquo10) pp 360ndash364 November 2010
[18] S Coleri M Ergen A Puri and A Bahai ldquoChannel estimationtechniques based on pilot arrangement in OFDM systemsrdquoIEEE Transactions on Broadcasting vol 48 no 3 pp 223ndash2292002
[19] R W Heath S Sandhu and A Paulraj ldquoAntenna selectionfor spatial multiplexing systems with linear receiversrdquo IEEECommunications Letters vol 5 no 4 pp 142ndash144 2001
[20] R Fletcher Practical Methods of Optimization John Willey ampSons 2nd edition 1987
[21] R W Bauml R F H Fischer and J B Huber ldquoReducingthe peak-to-average power ratio of multicarrier modulation byselected mappingrdquo Electronics Letters vol 32 no 22 pp 2056ndash2057 1996
[22] M Tan Z Latinovic and Y Bar-Ness ldquoSTBC MIMO-OFDMpeak-to-average power ratio reduction by cross-antenna rota-tion and inversionrdquo IEEE Communications Letters vol 9 no 7pp 592ndash594 2005
[23] K M Anstreicher ldquoLinear programming in O(n3lnnL) opera-tionsrdquo SIAM Journal on Optimization vol 9 no 4 pp 803ndash8121999
[24] J G Proakis Digital Communications McGraw Hill 4th edi-tion 2001
[25] O Oyman R U Nabar H Bolcskei and A J Paulraj ldquoChar-acterizing the statistical properties of mutual information inMIMO channelsrdquo IEEE Transactions on Signal Processing vol51 no 11 pp 2784ndash2795 2003
[26] S Cui A J Goldsmith and A Bahai ldquoEnergy-constrainedmodulation optimizationrdquo IEEE Transactions onWireless Com-munications vol 4 no 5 pp 2349ndash2360 2005
[27] R J Baxley and G T Zhou ldquoPower savings analysis of peak-to-average power ratio reduction in OFDMrdquo IEEE Transactions onConsumer Electronics vol 50 no 3 pp 792ndash797 2004
[28] A Batra et al Multiband OFDM Physical Layer SpecificationRelease 1 5 WiMedia Alliance 2009
[29] J Foerster et al ldquoChannel modeling sub-committee reportfinalrdquo IEEE P802 15-02490r1-SG3a 2003
[30] B C Arnold and R A Groeneveld ldquoBounds on expectationsof linear systematic statistics based on dependent samplesrdquoTheAnnals of Statistics vol 7 no 1 pp 220ndash223 1979
International Journal of
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VLSI Design
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Shock and Vibration
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Civil EngineeringAdvances in
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Electrical and Computer Engineering
Journal of
Advances inOptoElectronics
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Volume 2014
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Modelling amp Simulation in EngineeringHindawi Publishing Corporation httpwwwhindawicom Volume 2014
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Chemical EngineeringInternational Journal of Antennas and
Propagation
International Journal of
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Navigation and Observation
International Journal of
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DistributedSensor Networks
International Journal of
2 International Journal of Antennas and Propagation
small The fluctuation of the powers clearly affects the powerefficiency of HPAs or distorts signals which in turn reducesthe potential benefits of the antenna selectionOFDM systems[13]
One possible approach to deal with the problem ofimbalance allocation of data subcarriers is selecting antennasunder a constraint that the number of data subcarriersallocated to each antenna is equal Some research workshave studied such a constrained selection approach in theliterature for example see [10ndash12] In [10] an ad hoc algo-rithm was developed to realize the constrained selectionscheme Meanwhile the authors in [11] considered linearoptimization to devise the constrained selection scheme Itwas shown that the selection scheme based on optimizationcould offer a better performance than the suboptimal solutionin [10] In [12] we generalized the approach in [11] to thesystem with an arbitrary number of multiplexed data streamsand analyzed the performance directly in nonlinear fadingchannels However all of these works only study the efficacyof the constrained selection scheme from error-performanceperspective Moreover even though the same number of datasubcarriers is allocated to each transmit antenna (ie allantennas have an equal average power) an occurrence of highpeak-to-average power ratio (PAPR) still affects the systemDespite an increasing concern about energy consumption inwireless networks to the best of our knowledge a research onenergy efficiency in the context of antenna selection MIMO-OFDM systems is still missing
It is also essential to emphasize the need of research onimproving energy efficiency in antenna selection MIMO-OFDM systems First per-subcarrier antenna selectionMIMO configurations need multiple active RF (radio fre-quency) chains which immediately raises a concern aboutenergy consumption compared to single RF-chain OFDMsystems Second OFDM inherently suffers from a high PAPRproblem which leads to a poor power efficiency of HPAs[13 14] In per-subcarrier antenna selection OFDM systemsthis effect is intuitively more serious due to a combinationof the high PAPR and power fluctuation resulting from animbalance allocation of data subcarriers This problem alsobecomes crucial in the OFDM systems where linear scaling(ie scale the peak power of the time-domain OFDM signalsto the saturation level of the HPAs [15ndash17]) is implemented torealize OFDM transmissions with no nonlinear distortions
In this paper per-subcarrier antenna selection MIMO-OFDM systems with linear scaling are investigated froman energy perspective for the first time The importantcontributions of this work include (a) the analysis of powerefficiency ofHPAs and energy efficiency and (b) the proposedstrategy to improve these useful performance metrics Themain results are summarized as follows
(1) A two-step data allocation strategy is proposed todeliver a maximum overall power efficiency of HPAsThis strategy consists of an equal allocation of datasubcarriers among transmit antennas based on linearoptimization and a peak-power reduction algorithmvia cross-antenna permutations
(2) Analytical expressions characterizing the achievedpower efficiency of HPAs including the CCDFs(complementary cumulative distribution function)and the average power efficiency are derived It isproved that from the power-efficiency viewpoint theproposed allocation scheme outperforms the conven-tional scheme
(3) The improvements in capacity and energy efficiencyresulting from the improved power efficiency ofHPAsare analyzed
Numerical results are provided to verify the analyses as wellas demonstrate the benefits in terms of the power efficiencyof HPAs and capacity as well as energy efficiency
The remainder of the paper is organized as follows InSection 2 a per-subcarrier antenna subset selection MIMO-OFDM system with linear scaling is described In Section 3a data allocation strategy that could allocate evenly data sub-carriers across antennas with a low peak power is proposedAnalysis of power efficiency is carried out in Section 4 Theachievable capacity and energy efficiency are considered inSection 5Numerical results are provided in Section 6 FinallySection 7 concludes the paper
Notation A bold letter denotes a vector or a matrix whereasan italic letter denotes a variable (sdot)119879 (sdot)119867 119864sdot and det(sdot)denote transpose Hermitian transpose expectation anddeterminant of a matrix respectively otimes denotes the Kro-necker product I
119899indicates the 119899times119899 identity matrix and 1
119870
is a119870times 1 vector of onesR indicates the set of real numbers
2 Antenna Selection for MIMO-OFDMSystems with Linear Scaling
21 SystemModel Weconsider aMIMO-OFDMsystemwith119870 subcarriers 119899
119879transmit antennas and 119899
119877receive antennas
as shown in Figure 1 At the transmitter the input data aredemultiplexed into 119899
119863independent data streams Each data
stream is then mapped onto 119872-QAM (119872-ary quadratureamplitudemodulation) constellations For the 119896th subcarrierwe denote 119906
119896
119897and 119909119896
119894 1 le 119897 le 119899
119863 1 le 119894 le 119899
119879
0 le 119896 le 119870 minus 1 to be the symbols that the subcarrierblock takes at its 119897th input and outputs at its 119894th outputrespectively The allocation block assigns the elements ofu119896
= [1199061198961 1199061198962 119906119896
119899119863]119879to 119899119863selected antennas at the 119896th
subcarrier based on feedback information As a result only119899119863elements in a vector x
119896= [1199091198961 1199091198962 119909119896
119899119879]119879 are assigned
values from u119896 whereas the others are zeros It is assumed
that 119864u119896u119867119896 = 1205902I
119899119863 The output sequences from the
subcarrier allocation block are then fed into 119870-point IFFT(inverse fast Fourier transform) blocks In this paper theNyquist sampling signal is considered Thus the discrete-time baseband OFDM signals can be expressed as
119904119894 (119899) =
1
radic119870
119870minus1
sum119896=0
119909119896
1198941198901198952120587119899119896119870
0 le 119899 le 119870 minus 1 1 le 119894 le 119899119879
(1)
International Journal of Antennas and Propagation 3
Inputdata
Symbolmapping
Subcarrierallocation
IFFTadd GI
Linearscaling
NonlinearHPA
1
nD nT
Dem
ultip
lexe
r
Symbolmapping
IFFTadd GI
NonlinearHPA
Antenna selection index from receiver
1 1
nD
Tx 1
Tx nT
(a)
middot middot middot
ChannelH
Remove GIFFT
Rece
iver
proc
essin
g Estimateddata
Channel estimation andantenna selection decision
Remove GIFFT
To transmitter
Rx 1
Rx nR
(b)
Figure 1 A simplified block diagram of a MIMO-OFDM system with per-subcarrier transmit antenna selection
For simplicity we consider ideal predistortion HPAs(ie soft envelope limiters) with a unity gain and class-Aoperation To deliver the maximum power efficiency withno nonlinear distortions in the system with nonlinear HPAsthe peak power across transmit antennas is linearly scaledto the saturation level 119875sat of the HPAs In addition asfeedback information (ie the selected antenna indiceswhichare calculated based on the channel state information) isdeployed by the transmitter all transmit branches are scaledwith the same scaling factor [16] Thus the signal after linearscaling can be expressed as
119904119894 (119899) = radic120572119904
119894 (119899) (2)
where the scaling factor 120572 = 119875sat119875 and the peak poweracross antennas 119875 = max119904
119894(119899)|119899 = 0 119870 minus 1 119894 =
1 119899119879 Each time-domain OFDM signal is then amplified
by the HPA before being transmitted via its correspondingtransmit antenna
At the receiver the received signal at each antenna is fedinto the FFT block after the GI (guard interval) is removedThe systemmodel in the frequency domain corresponding tothe 119896th subcarrier can be expressed as
y119896= radic120572H
119896x119896+ n119896
= radic120572H119896u119896+ n119896
(3)
where
x119896= [119909119896
1119909119896
2sdot sdot sdot 119909119896
119899119879]119879
H119896=
[[[[
[
ℎ119896
11ℎ11989612
sdot sdot sdot ℎ1198961119899119879
ℎ11989621
ℎ11989622
sdot sdot sdot ℎ1198962119899119879
sdot sdot sdot sdot sdot sdot sdot sdot sdot sdot sdot sdot
ℎ1198961198991198771
ℎ1198961198991198772
sdot sdot sdot ℎ119896119899119877119899119879
]]]]
]
y119896= [119910119896
11199101198962
sdot sdot sdot 119910119896119899119877]119879
n119896= [119899119896
11198991198962
sdot sdot sdot 119899119896119899119877]119879
(4)
In the above equations ℎ119896119895119894indicates the channel coefficient
between the 119894th transmit antenna and the 119895th receive antennaThe effective channel matrix H
119896is obtained by eliminating
the columns of H119896corresponding to the unselected transmit
Table 1 Antenna subsets (119899119879= 4 119899
119863= 2 and Γ = 6)
120574 Γ120574
1 1 2
2 1 3
3 1 4
4 2 3
5 2 4
6 3 4
antennas 119910119896119895and 119899119896119895denote the received signal and the noise
at the 119895th receive antenna respectively Here the noise ismodeled as a Gaussian random variable with zero mean and119864n119896n119867119896 = 1205902119899I119899119877 We assume that the receiver can perfectly
estimate the channel coefficients for example using a block-type pilot arrangement for channel estimation [18]
22 Per-Subcarrier Antenna Subset Selection In a MIMO-OFDM system with the conventional per-subcarrier antennasubset selection antenna subsets are selected independentlyfor each subcarrier [9] On each subcarrier only 119899
119863antennas
out of 119899119879available transmit antennas are active Denote
Γ120574 120574 = 1 2 Γ to be the 120574th subset consisting of 119899
119863
selected transmit antennas where Γ = (119899119863119899119879
) = 119899119879119899119863(119899119879minus
119899119863) is the number of all possible 119899
119863-element subsets Each
subset consists of 119899119863transmit antenna indices that are chosen
based on the feedback information from the receiver Forexample when 119899
119879= 4 and 119899
119863= 2 then Γ = 6 and all possible
subsets Γ120574 120574 = 1 2 6 are defined in Table 1 The choice
of the best antenna subset depends on a particular selectioncriterion
Several antenna selection criteria such as maximumcapacity or maximum SNR (signal-to-noise ratio) [19] canbe extended to this system In this paper we consider thecapacity criterion Accordingly the optimal subset at the119896th subcarrier is determined by maximizing the mutualinformation of the 119896th subchannel that is
Γ120574lowast (119896) = arg max
Γ120574 120574=1Γ
119868119896
120574 (5)
where
119868119896
120574= log2(det(I
119899119877+
120588
119899119863
H119896H119867119896)) (6)
4 International Journal of Antennas and Propagation
is the instantaneous mutual information associated with the119896th subchannel [5] Here 120588 = 119875
1199051205902119899
= 12057211989911986312059021205902119899 and
119875119905= 1205721198991198631205902 is the total transmit power per subchannel Also
we have assumed in (6) that the transmit power is allocateduniformly across antennas This is due to the fact that thefeedback information in our system is only the selectedantenna indices (ie not sufficient enough to perform powerallocation algorithms across subcarriers as well as antennas)The average mutual information across subcarriers can nowbe expressed as
119868 (120588H) =1
119870
119870minus1
sum119896=0
119868119896
120574lowast (7)
3 A Proposed Strategy forPeak-Power Reduction
In Section 2 we have described the MIMO-OFDM systemwith the conventional selection scheme It can be noted thatthe number of data subcarriers assigned to each transmitantenna might be significantly different depending on thechannel condition In the systemwith identical linear scalingto achieve the maximal overall power efficiency of HPAs thepeak power across antennas should be as small as possibleWe note that the peak power of the signal on each branchdepends on both the transmitted constellation symbols andthe number of data subcarriers allocated in each OFDMsymbol (cf (1)) Thus it is not sufficient to reduce the peakpower by solely implementing PAPR reduction techniquesMore specifically PAPR reduction techniques themselvescannot solve the problem of imbalance allocation of datasubcarriers across antennas To reduce the peak power acrossantennas we propose a two-step strategy consisting of thefollowing
Step 1 Allocate the same number of data subcarriers to alltransmit antennas (ie selecting antennas under a constraintthat all antennas have the same number of data subcarriersas illustrated in Figure 2(b)) Once this is achieved thetime-domain signals on all transmit branches have the sameaverage power Moreover as we will mathematically prove inSection 41 the peak power across antennas is reduced
Step 2 Reallocate data symbols across antennasThis processwill alter the statistical distribution of signals and thus furtherreduce the peak power
We note that this paper does not focus on developingoriginal techniques for either equal allocation of data subcar-riers or peak-power reduction Instead we are interested inanalyzing power efficiency of HPAs and energy efficiency inper-subcarrier antenna selection OFDM systems which hasnot been considered so far The two steps in our proposedstrategy described in Sections 31 and 32 are accomplishedby extending the suitable approaches available in the litera-ture to the context of the considered system
31 Optimal Equal Allocation of Data Subcarriers The opti-mal constrained antenna selection scheme based on linearoptimization was considered in [11 12] to improve error per-formance of OFDM systems suffering nonlinear distortionsdue to HPAs We now consider this method for the first stepof our strategy to achieve a better power delivery in a linearlyscaled MIMO-OFDM system Specifically we define a vari-able 119911
119896
120574 where 119911119896
120574= 1 if Γ
120574is chosen for the 119896th subcarrier
and 119911119896120574= 0 otherwise Also denote 119888119896
120574to be the cost associated
with the chosen subset Γ120574 Here 119888119896
120574= 119868119896120574as the maximum
capacity criterion is considered By denoting vectors z =
(11991101 1199110
Γ 11991111 1199111
Γ 119911119870minus1
1 119911119870minus1
Γ)119879
isin 0 1119870Γtimes1 and
c = (11988801 1198880
Γ 11988811 1198881
Γ 119888119870minus1
1 119888119870minus1
Γ)119879
isin R119870Γtimes1 anoptimal solution for an equal allocation of data subcarriersis obtained by solving the following linear optimizationproblem [11 12]
maxzisin01119870Γtimes1
c119879z
subject to Az = a(8)
where A1= I119870otimes 1119879Γisin 0 1
119870times119870Γ A2= 1119879119870otimes IΓisin 0 1
Γtimes119870ΓA = (A119879
1A1198792)119879
isin 0 1(119870+Γ)times119870Γ a = (1119879
119870120582119879)119879 and 120582 =
(1205821 1205822 120582
Γ)119879 where 120582
120574is the number of times that the
subset Γ120574is selected The constraint in (8) means that only
119899119863antennas are allowed to transmit data symbols on each
subcarrier and all transmit antennas have the same numberof allocated data subcarriers It is important to note that thisbinary linear optimization problem can be relaxed to linearprogramming with integral solutions [12] Hence (8) can besolved efficiently by the known linear programmingmethodssuch as the simplex methods or interior point methods [20]
32 Data Allocation with Peak-Power Reduction To furtherreduce the peak power of the whole system various availablePAPR reduction techniques (eg see [14] and the referencestherein) can be now adopted In this paper we are interestedin a selected mapping (SLM) technique [21] as SLM is adistortionless PAPR technique that could achieve a goodPAPR reduction [14 21] One of the most important steps inSLM is creating a set of candidates that represents the samedata information To exploit the available degrees of freedomin multiple-antenna systems for peak-power reduction wepropose to create a set of candidates using cross-antennapermutations In the literature a SLM-based scheme thatcould exploit the available degrees of freedom was firstdeveloped in [22] The scheme in [22] creates candidatesby performing cross-antenna rotation and inversion (CARI)based on a defined random matrix However that scheme isproposed for an Alamouti code basedMIMO-OFDM systemonly In a per-subcarrier antenna selection OFDM systemCARI cannot be implemented directly as only 119899
119863out of 119899
119879
antennas are active on each subcarrier To create candidates inour scheme we perform cross-antenna permutations insteadof CARI In addition we utilize an antenna allocation patternthat is already known by the transmitter and receiver insteadof storing a defined random matrix at both transmitter and
International Journal of Antennas and Propagation 5
Antennas
Subcarriers
Tx 1
Tx 2
Tx 3
Tx 4
Data
Not used
(a) Unbalanced-power selection
Data
Not used
Antennas
Subcarriers
Tx 1
Tx 2
Tx 3
Tx 4
(b) Balanced-power selection
Figure 2 Illustration of per-subcarrier antenna subset selection (119899119879= 4 119899
119863= 2 and 119870 = 12)
Ant
enna
s
Subcarriers
1st candidate(original)
x11 x
21
x12
x32
x33 x
43
x24 x
44
0 0
0
00
0 0
0
(a)
2nd candidate (permutedata on the 1st antenna)
Subcarriers
x12 x
24 0 0
00
00
0 0
x11 x
32
x33 x
43
x44
x21
(b)
3rd candidate (permutedata on the 2nd antenna)
Subcarriers
Ant
enna
s
x12
x21 0 0
00
00
0 0
x11 x
33
x32 x
43
x44
x24
(c)
4th candidate (permutedata on the 3rd antenna)
Subcarriers
0 0
00
00
0 0
x11 x
21
x12 x
33
x32 x
44
x43x
24
(d)
Figure 3 Illustration of cross-antenna permutations (119899119879= 4 119899
119863= 2 and 119870 = 4)
receiver as in [22] The proposed algorithm is described asfollows
(1) Create 119882 candidates by performing cross-antennaspermutations An illustration of this process in thesystem with 119899
119863= 2 119899
119879= 4 and 119870 = 4 is
shown in Figure 3 Accordingly the first candidateis the original data allocation The second candidateis obtained by permuting all symbols on the firstantennas with their associated symbols on the otherantennasThe third and fourth candidates are createdin a similar manner To obtain a larger number ofcandidates all symbols on the antenna that are goingbe permutated need first have their phase rotated (iebeing multiplied with an element of a phase set ega 4-phase set is 0 1205872 120587 31205872)
(2) Calculate the peak powers of all available candidates(3) Select the candidate with the minimum peak power
for transmission
To recover the transmitted data the transmitter needs toinform the receiver which candidates have been selectedThus the number of side information bits in this scheme islog2119882 which is similar to that in [22]
33 Complexity Considerations In this subsection the com-plexity of the proposed allocation scheme is compared tothat of the conventional (imbalance) allocation scheme Inthe first step of the proposed scheme to realize an equalallocation of data subcarriers the optimization problem in (8)
needs to be solved at the receiverWenote that this linear opti-mization problem can be solved in polynomial time Morespecifically the complexity to solve this problem using inte-rior point methods can be reduced to 119874([(119870Γ)
3 ln(119870Γ)]120585)
where119874(sdot) denotes an order of complexity and 120585 is the bit sizeof the optimization problem [23] In addition it is noted thatthis step is transparent to the transmitter (ie no additionalcomplexity is required at the transmitter) In the secondstep a major additional complexity lies in the required IFFToperations due to additional 119882 candidates As an 119870 point-IFFT requires 119870log
2119870 complex additions and (1198702)log
2119870
complex multiplications the numbers of complex additionsand complex multiplications in the conventional scheme are119899119879119870log2119870 and 119899
119879(1198702)log
2119870 respectivelyMeanwhile in the
proposed scheme with 119882 candidates 119882119899119879119870log2119870 complex
additions and 119882119899119879(1198702)log
2119870 complex multiplications are
required However as we will show analytically in Section 4and numerically in Section 6 an improvement in the peak-power reduction reduces when 119882 becomes large Thus asmall value of 119882 is generally chosen which does not incurmuch additional complexity Finally the amount of feedbackinformation in the proposed scheme is similar to that in theconventional scheme
4 Analysis of Power Efficiency
41 Statistical Distribution of Peak Power Before proceedingto analyze the power efficiency of HPAs we need to investi-gate the distribution of the peak power of the MIMO-OFDMsignals (ie the peak power across transmit antennas) We
6 International Journal of Antennas and Propagation
consider the complementary cumulative distribution func-tion (CCDF) of the peak power defined as the probability thatthe peak power 119875 exceeds a given threshold 119875
0 that is
CCDF119875 (1198750) = Pr (119875 gt 119875
0) (9)
Note that although a procedure for calculating CCDF ofPAPR in OFDM systems is known to the best of ourknowledge all the CCDF expressions with respect toMIMO-OFDM signals available in the literature assume that all datasubcarriers are active which can be considered as a specialcase in the considered system when all the transmit antennashave the same number of allocated data symbols In thefollowing we calculate the CCDF of the peak power in oursystem
Let us begin with the discrete-time OFDM signal 119904119894(119899)
119899 = 0 1 119870minus1 corresponding to the 119894th transmit antennaThe peak power of this signal is defined as
119875119894= max0le119899le119870minus1
|119904119894 (119899) |2 (10)
For analytical tractability we assume that both the real partand imaginary part of the signal 119904
119894(119899) are asymptotically
independent and identically distributed Gaussian randomvariables Note that this assumption which is based on thecentral limit theorem [24] only holds when the number ofassigned data subcarriers on the 119894th antenna denoted as119870119894 is large enough As a result |119904
119894(119899)| follows the Rayleigh
distribution and |119904119894(119899)|2 has a chi-square distribution with
two degrees of freedom The probability density function ofthe signal |119904
119894(119899)|2 can be expressed as [24]
119901|119904|2 (
100381610038161003816100381611990411989410038161003816100381610038162) =
1
1205902119870119894
119890minus|119904119894|21205902
119870119894 (11)
where 1205902119870119894
= 1205902119870119894119870 is the variance of the signal |119904
119894(119899)| Note
that sum119899119879
119894=1119870119894
= 119899119863119870 thus we have sum
119899119879
119894=11205902119870119894
= 1198991198631205902 The
CDF (cumulative distribution function) of the signal |119904119894(119899)|2
is given as
Pr (100381610038161003816100381611990411989410038161003816100381610038162le 120579) = 1 minus 119890
minus1205791205902
119870119894 120579 ge 0 (12)
Suppose that 119870 samples of |119904119894(119899)| 119899 = 0 1 119870 minus 1 are
independent the CDF of the peak power 119875119894can be expressed
as
CDF119875119894 = Pr (119875119894le 1198750)
= Pr (1003816100381610038161003816119904119894 (0)10038161003816100381610038162le 1198750)Pr (1003816100381610038161003816119904119894 (1)
10038161003816100381610038162le 1198750) sdot sdot sdot
Pr (1003816100381610038161003816119904119894 (119870 minus 1)10038161003816100381610038162le 1198750)
= (1 minus 119890minus1198750120590
2
119870119894 )119870
(13)
In MIMO-OFDM systems with linear scaling the peakpower across transmit antennas 119875 can be defined as
119875 = max1le119894le119899119879
119875119894 (14)
Given the statistical independence of data among transmitantennas which is the case in the considered spatial mul-tiplexed OFDM system the CDF of the peak power 119875 iscalculated as
CDF119875 = Pr (119875 le 1198750)
= Pr (1198751le 1198750)Pr (119875
2le 1198750) sdot sdot sdotPr (119875
119899119879le 1198750)
=
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
(15)
Therefore the CCDF of the peak power of the antennaselection MIMO-OFDM signals can be expressed as
CCDF119875imbalance (1198750) = 1 minus CDF119875
= 1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
(16)
In the MIMO-OFDM system with a power balancingconstraint the number of allocated data subcarriers pertransmit antenna is equal to one another (ie 119870
119894=
119899119863119870119899119879
= 119870 forall119894 = 1 2 119899119879) Thus the variances of the
signals are 1205902119870119894
= 1198991198631205902119899119879= 1205902119870 forall119894 = 1 2 119899
119879 As a result
the CCDF expression could be simplified to as
CCDF119875balance (1198750) = 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(17)
A comparison of the CCDF of the peak powers in the twosystems is presented in the following theorem
Theorem 1 In MIMO-OFDM transmission schemes that con-sist of inactive data subcarriers (eg per-subcarrier antennaselection) the probability of occurrences of high peak power isthe smallest when the same number of data symbols is allocatedto all transmit antennas that is
CCDF119875balance (1198750) le CCDF119875imbalance (1198750) (18)
Proof The proof is given in Appendix AWhen the peak-power reduction algorithm proposed in
Section 32 is implemented in theMIMO-OFDMsystemwitha power-balancing constraint the CCDF of the peak powercan be expressed as
CCDF119875balance+reduced (1198750) = (CCDF119875balance (1198750))119882
= (1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870)119882
(19)
where 119882 is the number of candidates that are assumed tobe independent Recall that by definition the CCDF value isalways smaller than one (cf (9)) Therefore the CCDF valuein (19) is smaller than that in (17) that is
CCDF119875balance+reduced (1198750) le CCDF119875balance (1198750) (20)
International Journal of Antennas and Propagation 7
42 Power Efficiency of HPAs We now analyze the powerefficiency (PE) of high-power amplifiers (HPAs) The drainefficiency of HPAs which is defined as a ratio between thepower drawn from the DC source 119875dc and the average outputpower 119875out is considered in this paper Denote 119875119894in and 119875119894out tobe the average input and output powers of the HPA for the119894th antenna respectively Recall that all HPAs are assumedto have a unity gain that is 119875119894out = 119875119894in forall119894 = 1 2 119899
119879
Hence the instantaneous overall power efficiency of HPAs inthe MIMO-OFDM system can be expressed as [16]
120578PE
=sum119899119879
119894=1119875119894out
119899119879119875dc
=sum119899119879
119894=1119875119894in
119899119879119875dc
= 1205721198991198631205902
119899119879119875dc
=1198991198631205902119875sat
119899119879119875dc
1
119875=
1198991198631205902
2119899119879
1
119875
(21)
In the above manipulations we have used the fact thatsum119899119879
119894=1119875119894in = 120572119899
1198631205902 and119875dc = 2119875sat for class-AHPAs regardless
of the average powers of the input time-domain signalsDenoting CCDFPE (120578PE
0) = Pr(120578PE gt 120578PE
0) to be the CCDF
of the power efficiency we obtain the following result withrespect to 120578
PE
Theorem 2 In per-subcarrier antenna selection MIMO-OFDM systems with linear scaling the probability of achievinghigh instantaneous overall power efficiency of HPAs is thelargest when all transmit antennas have the same number ofallocated data symbols that is
CCDFPEbalance (120578PE0) ge CCDFPEimbalance (120578
PE0) (22)
where
CCDFPEbalance (120578PE0) = (1 minus 119890
minus12120578PE0 )119899119879119870
CCDFPEimbalance (120578PE0) =
119899119879
prod119894=1
(1 minus 119890minus1198991198631198702119899119879119870119894120578
PE0 )119870
(23)
Proof From (18) and (21) it is readily to obtain (22) and (23)With respect to the average value of the overall power
efficiency from (21) we can express
120578PE
= 119864 120578PE =
1198991198631205902
2119899119879
1198641
119875 =
1198991198631205902
2119899119879
int1
119909119901 (119909) 119889119909 (24)
where 119901(119909) is the pdf (probability distribution function) ofthe peak power In the system with a balance constraint (ieonly use Step 1) the pdf of the peak power can be calculatedas
119901balance (119909) =119889
119889119909CDF119875balance (119909) =
119889
119889119909(1 minus 119890
minus1199091205902
119870)119899119879119870
=119899119879119870
1205902119870
119890minus1199091205902
119870(1 minus 119890minus1199091205902
119870)119899119879119870minus1
(25)
Hence
120578PEbalance =
1198991198631205902
2119899119879
int1
119909119901balance (119909) 119889119909
=119899119879119870
2int1198701205902
119870
1205902
119870
1
119909119890minus1199091205902
119870(1 minus 119890minus1199091205902
119870)119899119879119870minus1
119889119909
=119899119879119870
2int119870
1
1
119909119890minus119909
(1 minus 119890minus119909
)119899119879119870minus1
119889119909
(26)
Similarly the power efficiency of HPAs in the conventionalsystem is
120578PEimbalance =
1198991198631205902
2119899119879
int1
119909119901imbalance (119909) 119889119909
=1198991198631198701205902
2119899119879
int119870max120590
2
max
1205902
max
1
119909
119899119879
sum119895=1
119890minus1199091205902
119870119895
(1 minus 119890minus1199091205902
119870119895 ) 1205902119870119895
times
119899119879
prod119894=1
(1 minus 119890minus1199091205902
119870119894 )119870
119889119909
(27)
where 1205902max = max12059021198701
1205902119870119899119879
and 119870max = max1198701
119870119899119879When the peak-power reduction algorithm is also imple-
mented (ie the system employs both Steps 1 and 2) it isreadily from (20) and (21) that
CCDFPEbalance+reduced (120578PE0
) ge CCDFPEbalance (120578PE0
) (28)
where
CCDFPEbalance+reduced (120578PE0
) = 1 minus (1 minus (1 minus 119890minus12120578
PE0 )119899119879119870
)119882
(29)
Also the average power efficiency can now be calculated as
120578PEbalance+reduced =
1198991198631205902
2119899119879
int1
119909119901balance+reduced (119909) 119889119909
=119899119879119870119882
2int119870
1
1
119909119890minus119909
(1 minus 119890minus119909
)119899119879119870minus1
times (1 minus (1 minus 119890minus119909
)119899119879119870
)119882minus1
119889119909
(30)
It can be seen from (30) that the smaller the peak poweris reduced (ie the larger the number of candidates 119882 isused) the higher the power efficiency could be achievedNote that although the integrals in (26) (27) and (30) haveno closed-form solutions they can be evaluated numericallyAlso the average power efficiencies in (26) (27) and (30) aretaken with respect to the input data In other words they areconsidered as instantaneous power efficiencieswith respect tothe channel distribution Consequently the power efficiencyin the systems is obtained by averaging these values over thefading channel distribution
8 International Journal of Antennas and Propagation
5 Analyses of Capacity and Energy Efficiency
It has been shown in (22) and (28) that the proposed systemcould achieve a better power efficiency of HPAs than itscounterpart Thus when the power 119875dc is fixed it is intuitivethat an increased average power efficiency results in anincreased average transmit power and in turn leads to anincrease in the achievable rate Moreover an increase in thedata rate under a constant consumption power will translateinto an improvement in energy efficiency The achievedcapacity and energy efficiency are now investigated in thissection
51 System Capacity We begin by rewriting the mutualinformation in (7) with respect to the average SNR valueof 120588 = 119875
1199051205902119899 where 119875
119905= 120572119899
1198631205902 = 120578
PE119899119879119875dc (cf (21))
The ergodic capacity is then calculated by averaging themutual information over the fading channel distributionthat is 119862(120588) = 119864H119868(120588H) From (6) and (7) the mutualinformation in the proposed and conventional systems canbe expressed respectively as
119868 (120588proposedH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
(31)
119868 (120588imbalanceH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(32)
where 120588proposed = 120578PEproposed119899119879119875dc120590
2
119899and 120588imbalance =
120578PEimbalance119899119879119875dc120590
2
119899 Here 120578
PEproposed = 120578
PEbalance+reduced if the
peak-power reduction algorithm is implemented otherwise120578PEproposed = 120578
PEbalance Also H119896 in (31) denotes the effective
channel matrix on the 119896th subcarrier in the proposed systemwhich is obtainedwhen solving the problem in (8)This chan-nel matrix is generally different from the effective channelmatrix H
119896in the conventional system because the selected
antenna subset may be differentThe difference in the mutualinformation between the two systems can be now calculatedas
Δ119868 = 119868 (120588proposedH) minus 119868 (120588imbalanceH) =1
119870
119870minus1
sum119896=0
Δ119868119896 (33)
where
Δ119868119896= log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
minus log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(34)
For analytical simplicity we focus on the high-SNRregime At the high SNR the mutual information at the 119896thsubcarrier can be approximated as [25]
119868119896= log2(det(
120588
119899119863
Ω119896)) (35)
where
Ω119896= Ω (H
119896) =
H119896H119867119896 119899119877le 119899119863
H119867119896H119896 119899119877gt 119899119863
(36)
Thus the difference in the mutual information can berewritten as
Δ119868 =1
119870
119870minus1
sum119896=0
(log2(det(
120588proposed
119899119863
Ω119896))
minuslog2(det(
120588imbalance119899119863
Ω119896)))
= 119901log2
120578PEproposed
120578PEimbalance
minus1
119870
119870minus1
sum119896=0
Δ119896= 1198791+ 1198792
(37)
where 119901 = min(119899119863 119899119877)Ω119896= Ω(H
119896) and
Δ119896= log2(det (Ω
119896)) minus log
2(det (Ω
119896)) (38)
is the loss in the mutual information associated with the 119896thsubcarrier due to the constrained allocation Note that if bothsystems have the same selected antenna subset at the 119896thsubcarrier then Δ
119896= 0 otherwise Δ
119896gt 0Thus the total loss
in the mutual information Δ = (1119870)sum119870minus1
119896=0Δ119896gt 0
We have some important observations with respect to thevalue of Δ119868 in (37)
(i)The change in mutual information Δ119868 comes fromtwo sources The first source 119879
1is a benefit in mutual
information due to the improvement in the powerefficiency of HPAs The second source 119879
2is a penalty
that incurs because the chosen effective channelmatrices in the proposed system are different from theones in the conventional system(ii) For each channel realization thematrixH
119896is fixed
and the first term 1198791in (37) is a constant Thus the
value of Δ119868 depends on how the effective channelmatrix H
119896is selected in the constrained selection
scheme From this observation it is clear that tomake the value Δ119868 become as positive as possiblethe constrained selection method should result inthe cost penalty Δ as small as possible We note thatthe formulated optimization in (8) could achieve theminimum possible value of the total cost Hence it isexpected that the constrained selection scheme basedon linear optimization will guarantee the maximumachievable value of Δ119868 In addition to have an insightinto the cost penalty we derive the upper bound ofthe expected value of the cost penalty in Appendix BBased on the obtained bound it is observed that forfixed values of 119899
119879and 119899
119863 the cost penalty becomes
smaller with an increasing value of 119902 = max(119899119863 119899119877)
International Journal of Antennas and Propagation 9
(iii) As Δ gt 0 the upper bound of the capacityimprovement can be given as
Δ119862 = 119864H Δ119868 le 119901log2119864H
120578PEproposed
120578PEimbalance
(39)
In (39) we have used Jensenrsquos inequality of119864log(119909) le log(119864119909) as log(119909) is a concavefunction Based on this bound we could estimatethe maximum improvement in capacity that couldbe realized in the proposed system compared to itscounterpart
It is now necessary to evaluate the change in capacitythat is Δ119862 We note that although the distribution of themutual information at high SNRs can be well approximatedby a Gaussian distribution [25] it is still challenging toperform a mathematical evaluation of Δ119862 from a statisticalviewpoint This is mainly due to the fact that the two termsin (37) are complicated dependent random variables Thuswe perform a numerical evaluation of Δ119862 instead Figure 4plots the empirical CCDF of 119879
1 CDF of 119879
2 and CCDF
of Δ119868 In the figure ldquo119882 = 1rdquo stands for the case in whichonly Step 1 in Section 31 is implemented The results areobtained in the systems with 119899
119879= 4 119899
119863= 2 119899
119877= 2 119870= 128
and are averaged over 103 channel realizations Details aboutother simulation parameters are described in Section 6 Thenumerical results confirm that 119879
1gt 0 and 119879
2lt 0 Moreover
as shown in Figure 4(c) Δ119868 is always positive when the peak-power reduction algorithm is implemented (ie 119882= 4 and119882 = 8) For the case of 119882 = 1 the probability of ΔI beingpositive is significant Therefore the proposed system attainsa better ergodic capacity than that in the conventional systemThe achieved capacities in the considered systems will beprovided in Section 6
52 Energy Efficiency In this subsection we further exam-ine the efficacy of the proposed system from an energy-efficiency (EE) perspective Normalized energy efficiency(bitsHzJoule) in MIMO-OFDM systems can be defined as[3 26]
120578EE
=119862 (120588)
119875total (40)
where 119862(120588) is the achievable rate and the total powerconsumption per-subchannel is 119875total = 119899
119879119875dc + 119899
119879119875RF + 119875sp
where 119875RF is the RF power consumption in each transmitbranch excluding the associatedHPA and119875sp is the basebandprocessing power consumption It can be seen from (40)that given a fixed value of 119875total a comparison of energyefficiency achieved in the two systems is based on the capacitycomparison that has been analyzed in Section 51We are nowinterested in evaluating a useful metric of energy efficiency-spectral efficiency performance Recall that the average SNR120588 is given as 120588 = 119875
1199051205902119899= 120578
PE119899119879119875dc1205902
119899 Thus we can rewrite
the energy efficiency in (40) as a function of 119875dc as
120578EE
(119875dc) =119862 (120578
PE119899119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
(41)
Table 2 Simulation parameters
Parameter ValueBandwidth 528MHzFFT size 128Number of samples in zero-padded suffix 37Modulation scheme 4-QAMIEEE 802153a channel model CM1
The energy efficiency of the proposed and conventionalsystems can now be respectively expressed as
120578EEproposed (119875dc) =
119862proposed (120578PEproposed 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEproposed 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(42)
120578EEimbalance (119875dc) =
119862imbalance (120578PEimbalance 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEimbalance 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(43)
Similarly to the case of capacity we compare the energyefficiency achieved in the two systems by means of numericalresults in the next section Note that the calculation of energyefficiency in the proposed system (ie (42)) has assumed thata reduction in spectral efficiency due to the side informationas well as additional processing power required for the peak-power reduction algorithm is negligible In fact a reductionin spectral efficiency is very small For example in a systemwith 16-QAM FFT size of 128 119899
119863= 2 and 119882= 4 (ie 2 bits
are needed for side information) a spectral efficiency lossis 2 bits(128 times 4 times 2 + 2) bits = 019 Also it was shownin [27] that the additional power cost when implementingSLM schemes is minuscule Thus the proposed peak-powerreduction algorithm in Section 32 which is a SLM-basedscheme requires a small additional power cost
6 Numerical Results
In this section we provide numerical results to validatethe analyses mentioned in the previous sections as wellas demonstrate the effectiveness of the proposed allocationscheme over its counterpart A MIMO-OFDM system with119899119879= 4 119899
119863= 2 and 119899
119877= 2 is considered in our simulations
The system parameters are listed in Table 2These parametersare chosen based on the legacy WiMedia MB-OFDM UWB(Multiband-OFDM UWB) standard [28] Also the channelCM1 defined in the IEEE 802153a channel model [29] isbased on ameasurement of a line-of-sight scenario where thedistance between the transmitter and the receiver is up to 4mMoreover the multipath gains are modeled as independentlog normally distributed random variables We assume thatperfect channel state information is available at the receiverAlso the feedback link has no delay and is error-free
10 International Journal of Antennas and Propagation
Empirical CCDF of T110
0
10minus1
10minus2
minus2 0 2
W = 1
W = 4
W = 8
(a)
100
10minus1
10minus2
minus04 minus02 0
Empirical CDF of T2
(b)
Empirical CCDF of (T1 + T2)10
0
10minus1
10minus2
minus1 minus05 0 05 1 15 2
W = 1
W = 4
W = 8
(c)
Figure 4 Statistical distributions (note 1198792is independent of119882)
61 Evaluations of Peak-Power Distribution In Figure 5 weplot the CCDFs of the peak power of time-domain signalsThe analytical curves are based on (16) (17) and (19) Mean-while the simulation curves are empirical CCDF values Thesimulation result confirms that a system with the proposedallocation scheme offers a better CCDF performance than itscounterpart As expected the occurrence of high peak poweris significantly reduced when the peak-power reductionalgorithm is implemented Also it can be seen that theimprovement associated with this algorithm is reduced withincreasing 119882 In other words a very large value of 119882 whilerequiring higher complexity in terms on the number of IFFToperations results in a marginal improvement Thus it isreasonable to choose a relatively small value for 119882 (eg119882 = 4) It is also worth noting that the analytical curvesare relatively close to the simulation curves The small gapsexist due to the fact that the assumption of independentsamples |119904
119894(119899)| to obtain (13) does not strictly hold as we have
sum119870minus1
119899=0|119904119894(119899)|2 = 1205902119870
119894by Parsevalrsquos relation [24]
62 Evaluations of Power Efficiency of HPAs Figure 6 com-pares the CCDFs of the power efficiency achieved in theproposed and conventional systems It can be seen that theprobability of power efficiency being large highly likely occursin the proposed system compared to its counterpart Also
the simulation results agree well with the analytical resultsderived in (23) and (29) In Table 3 we compare the averagepower efficiencies Here the analytical values are obtainedaccording to (26) (27) and (30) Meanwhile the simulationvalues are empirical values based on the original definitionof the drain efficiency in (21) Also these values are averagedover the fading channel realizations It can be seen that thederived expressions approximate well the achieved powerefficiencies Table 3 also provides relative improvements ofthe power efficiencies achieved in the proposed system overthe conventional system Here only 120578
PE (Simulation) valuesare used for calculating these improvements It is clear thatthe proposed system could achieve a significant improvementin terms of average power efficiency
63 Evaluations of Capacity and Energy Efficiency Figure 7shows the system capacity inMbps (ie the normalized valuein (6) is scaled upwith the system bandwidth) versus the SNRvalue of 12059021205902
119899 It is clear that a systemwith the proposed allo-
cation scheme achieves a higher capacity than its counterpartThis agrees with the analysis in Section 51 that the changein capacity Δ119862 is positive In Figure 8 we plot the energyefficiency (MbitsJoule) versus spectral efficiency (MbpsHz)This figure is obtained based on (42) and (43) when varying119875dc Other parameters are 119875RF = 100mW 119875sp = 10mW and
International Journal of Antennas and Propagation 11
Table 3 A comparison of average power efficiencies
Imbalance Proposed (119882 = 1) Proposed (119882 = 4) Proposed (119882 = 8)120578PE (Simulation) 00697 00768 00894 00942
120578PE (Analysis) 00691 00757 00892 00943
Improvement120578PEproposed minus 120578
PEimbalance
120578PEimbalance
mdash 1019 2826 3515
1 2 3 4 5 6 7 8 9
100
10minus1
10minus2
10minus3
Peak power P0
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Pr (P
gtP0)
Figure 5 Comparison of CCDFs of the peak powers
002 004 006 008 01 012 014Power efficiency
CCD
F
100
10minus1
10minus2
10minus3
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Figure 6 Comparison of CCDFs of the power efficiencies
4500
4000
3500
3000
2500
2000
1500
1000
Ergo
dic c
apac
ity (M
bps)
2 4 6 8 10 12 14
SNR (dB)
3300
3200
3100
3000
2900
2800
97 98 99 10 101
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 7 Comparison of the ergodic capacities
12059021205902119899= 15 dB As expected the improvement in the power
efficiency of HPAs results in an improved energy efficiencyIn addition it can be observed that there exists an energyefficiency-spectral efficiency tradeoff in the systems Thistradeoff clearly needs to be taken into consideration whendesigning energy-efficient per-subcarrier antenna selectionbased OFDM wireless systems
7 Conclusions
In this paper a per-subcarrier antenna subset selectionMIMO-OFDM system with linear scaling has been investi-gated from an energy-efficiency perspective We have shownthat an imbalance allocation of data subcarriers associatedwith the conventional selection scheme affects the power effi-ciency of HPAs as well as the energy-efficiency of the wholesystem To deliver the maximum overall power efficiencywe have proposed the two-step strategy consisting of equalallocation data subcarriers across antennas and peak-powerreduction It has been proved from the power-efficiency view-point that the proposed allocation scheme outperforms theconventional scheme We have also derived the expressionsfor measuring the average power efficiency Moreover theimprovements in terms of capacity and energy efficiency
12 International Journal of Antennas and Propagation
0 2 4 6 8 10400
600
800
1000
1200
1400
1600
Spectral efficiency (MbpsHz)
Ener
gy effi
cien
cy (M
bits
J)
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 8 Energy efficiency versus spectral efficiency
resulting from the improved power efficiency have beenanalyzed The analytical results are validated by simulationresults The simulation result also shows that the systemwith the proposed allocation scheme could achieve a betterefficiency efficiency-spectral energy tradeoff compared to itscounterpart
Appendices
A Proof of Theorem 1
Let us consider a function 119891(120592) = 1 minus 119890minus1198750120592 0 lt 120592 le 1205902maxwhere 1205902max = max1205902
1198701 12059021198702
1205902119870119899119879
The second derivativeof this function is
11989110158401015840(120592) =
21198750120592 minus 11987520
1205924119890minus1198750120592 (A1)
From a HPAsrsquo viewpoint it is of interest to consider thesituation when the peak power across antennas 119875
0is large
Thus we consider the scenarios of 1198750
gt 21205902max where 1205902maxis the maximum average power across antennas Under thesesituations it is clear that 11989110158401015840(120592) lt 0 forall120592 isin (0 1205902max] Hencethe function 119891(120592) is concave By applying Jensenrsquos inequalitywe obtain the following inequality
1
119899119879
119899119879
sum119894=1
119891 (1205902
119870119894) le 119891(
1
119899119879
119899119879
sum119894=1
1205902
119870119894)
= 119891(1
119899119879
119899119879
sum119894=1
1205902
119870) = 119891 (120590
2
119870)
(A2)
where the equality comes from the fact that sum119899119879
119894=11205902119870119894
=
sum119899119879
119894=11205902119870
= 1198991198631205902 Expression (A2) can be rewritten as119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le 119899119879(1 minus 119890
minus11987501205902
119870) (A3)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879
On the other hand by applying the arithmetic-geometricmean inequality and note that (1 minus 119890
minus119909) gt 0 forall119909 gt 0 we have
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1
119899119879
119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ))
119899119879
(A4)
Note that the equality in (A4) holds if and only if 1205902119870119894
= 1205902119870
forall119894 = 1 119899119879
Combining (A3) and (A4) results in
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1 minus 119890minus1198750120590
2
119870)119899119879
(A5)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879 Thus we
get the following desired inequality
1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
ge 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(A6)
or
CCDF119875imbalance (1198750) ge CCDF119875balance (1198750) (A7)
This completes the proof
B Upper Bound of an ExpectedValue of Cost Penalty
In this appendix we derive an upper bound of the expectedvalue of Δ
119896 It can be seen from (5) that among all pos-
sible matrices H119896 the matrix H
119896with the highest value of
log2(det(Ω
119896))Ω119896
= Ω(H119896) will be selected as the effective
channel matrix for the 119896th subcarrier in the conventionalscheme Meanwhile in the proposed scheme due to thebalance constraint the effective channel matrix associatedwith the kth subcarrier is not necessarily the one with thehighest log
2(det(Ω
119896)) that is log
2(det(Ω
119896)) le log
2(det(Ω
119896))
Thus the expected value of Δ119896can be computed by using
order statistics In particular an upper bound on the expecteddifference of two-order statistics the Γth and 120574th 1 le 120574 lt Γis given by [30]
119864 Δ119896 = 119864 log
2(det (Ω
119896)) minus 119864 log
2(det (Ω
119896))
le 120590119862radic
Γ (120574 + 1)
120574
(B1)
where 1205902119862is the variance of log
2(det(Ω
119896)) that is assumed to
be the same for all possible matricesH119896
On the other hand suppose that the entries of the 119899119877times119899119879
matrixH119896are iid complex Gaussian random variables with
zero mean and unit variance then for any effective channelmatrix H
119896 Ω119896is a complex Wishart matrix It follows from
[25] that the variance of log2(det(Ω
119896)) can be expressed as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1205951015840(119902 minus 119898 + 1) (B2)
International Journal of Antennas and Propagation 13
where 119901 = min(119899119863 119899119877) 119902 = max(119899
119863 119899119877) and 1205951015840(119909) =
suminfin
120593=11(120593 + 119909 minus 1)
2 is the first derivative of the digammafunction By approximating 1205951015840(119909) asymp 1119909 [25] the simplerexpression for 1205902
119862in (B2) is given as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1
119902 minus 119898 + 1 (B3)
Substitute (B3) into (B1) we finally arrive at
119864 Δ119896 le log
2(119890)radic(
119901
sum119898=1
1
119902 minus 119898 + 1) times
Γ (120574 + 1)
120574 (B4)
Conflict of Interests
The authors declare that there is no conflict of interestsregarding the publication of this paper
References
[1] L M Correia D Zeller O Blume et al ldquoChallenges andenabling technologies for energy aware mobile radio networksrdquoIEEECommunicationsMagazine vol 48 no 11 pp 66ndash72 2010
[2] Z Hasan H Boostanimehr and V K Bhargava ldquoGreen cellularnetworks a survey some research issues and challengesrdquo IEEECommunications Surveys and Tutorials vol 13 no 4 pp 524ndash540 2011
[3] J Joung C K Ho and S Sun ldquoGreenwireless communicationsa power amplifier perspectiverdquo in Proceedings of the 4th Asia-Pacific Signal and Information Processing Association AnnualSummit and Conference (APSIPA ASC rsquo12) pp 1ndash8 December2012
[4] G L Stuber J R Barry S W Mclaughlin Y E Li M AIngram and T G Pratt ldquoBroadband MIMO-OFDM wirelesscommunicationsrdquoProceedings of the IEEE vol 92 no 2 pp 271ndash294 2004
[5] H Bolcskei D Gesbert and A J Paulraj ldquoOn the capacity ofOFDM-based spatial multiplexing systemsrdquo IEEE Transactionson Communications vol 50 no 2 pp 225ndash234 2002
[6] V Tarokh N Seshadri and A R Calderbank ldquoSpace-timecodes for high data rate wireless communication performancecriterion and code constructionrdquo IEEE Transactions on Infor-mation Theory vol 44 no 2 pp 744ndash765 1998
[7] C M Vithanage M Sandell J P Coon and Y Wang ldquoPrecod-ing in OFDM-based multi-antenna ultra-wideband systemsrdquoIEEE Communications Magazine vol 47 no 1 pp 41ndash47 2009
[8] Z Tang H Suzuki and I B Collings ldquoPerformance of antennaselection forMIMO-OFDMsystems based onmeasured indoorcorrelated frequency selective channelsrdquo in Proceedings of theAustralian Telecommunication Networks and Applications Con-ference pp 435ndash439 December 2006
[9] H Zhang and R U Nabar ldquoTransmit antenna selection inMIMO-OFDM systems bulk versus per-tone selectionrdquo inProceedings of the IEEE International Conference on Communi-cations (ICC rsquo08) pp 4371ndash4375 May 2008
[10] H Shi M Katayama T Yamazato H Okada and A OgawaldquoAn adaptive antenna selection scheme for transmit diversityin OFDM systemsrdquo in Proceedings of the IEEE 54th VehicularTechnology Conference (VTC rsquo01) pp 2168ndash2172 October 2001
[11] M Sandell and J P Coon ldquoPer-subcarrier antenna selectionwith power constraints in OFDM systemsrdquo IEEE Transactionson Wireless Communications vol 8 no 2 pp 673ndash677 2009
[12] N P Le F Safaei and L C Tran ldquoTransmit antenna subsetselection for high-rate MIMO-OFDM systems in the presenceof nonlinear power amplifiersrdquo EURASIP Journal on WirelessCommunications and Networking vol 2014 article 27 2014
[13] R PrasadOFDM for Wireless Communications Systems ArtechHouse 1st edition 2004
[14] T Jiang and Y Wu ldquoAn overview peak-to-average power ratioreduction techniques for OFDM signalsrdquo IEEE Transactions onBroadcasting vol 54 no 2 pp 257ndash268 2008
[15] H Ochiai ldquoPerformance analysis of peak power and band-limited OFDM system with linear scalingrdquo IEEE Transactionson Wireless Communications vol 2 no 5 pp 1055ndash1065 2003
[16] C Zhao R J Baxley and G T Zhou ldquoPeak-to-average powerratio and power efficiency considerations in MIMO-OFDMsystemsrdquo IEEE Communications Letters vol 12 no 4 pp 268ndash270 2008
[17] D Wulich and I Gutman ldquoImpact of linear power amplifier onpower loading in OFDM part I principlesrdquo in Proceedings ofthe IEEE 26th Convention of Electrical and Electronics Engineersin Israel (IEEEI rsquo10) pp 360ndash364 November 2010
[18] S Coleri M Ergen A Puri and A Bahai ldquoChannel estimationtechniques based on pilot arrangement in OFDM systemsrdquoIEEE Transactions on Broadcasting vol 48 no 3 pp 223ndash2292002
[19] R W Heath S Sandhu and A Paulraj ldquoAntenna selectionfor spatial multiplexing systems with linear receiversrdquo IEEECommunications Letters vol 5 no 4 pp 142ndash144 2001
[20] R Fletcher Practical Methods of Optimization John Willey ampSons 2nd edition 1987
[21] R W Bauml R F H Fischer and J B Huber ldquoReducingthe peak-to-average power ratio of multicarrier modulation byselected mappingrdquo Electronics Letters vol 32 no 22 pp 2056ndash2057 1996
[22] M Tan Z Latinovic and Y Bar-Ness ldquoSTBC MIMO-OFDMpeak-to-average power ratio reduction by cross-antenna rota-tion and inversionrdquo IEEE Communications Letters vol 9 no 7pp 592ndash594 2005
[23] K M Anstreicher ldquoLinear programming in O(n3lnnL) opera-tionsrdquo SIAM Journal on Optimization vol 9 no 4 pp 803ndash8121999
[24] J G Proakis Digital Communications McGraw Hill 4th edi-tion 2001
[25] O Oyman R U Nabar H Bolcskei and A J Paulraj ldquoChar-acterizing the statistical properties of mutual information inMIMO channelsrdquo IEEE Transactions on Signal Processing vol51 no 11 pp 2784ndash2795 2003
[26] S Cui A J Goldsmith and A Bahai ldquoEnergy-constrainedmodulation optimizationrdquo IEEE Transactions onWireless Com-munications vol 4 no 5 pp 2349ndash2360 2005
[27] R J Baxley and G T Zhou ldquoPower savings analysis of peak-to-average power ratio reduction in OFDMrdquo IEEE Transactions onConsumer Electronics vol 50 no 3 pp 792ndash797 2004
[28] A Batra et al Multiband OFDM Physical Layer SpecificationRelease 1 5 WiMedia Alliance 2009
[29] J Foerster et al ldquoChannel modeling sub-committee reportfinalrdquo IEEE P802 15-02490r1-SG3a 2003
[30] B C Arnold and R A Groeneveld ldquoBounds on expectationsof linear systematic statistics based on dependent samplesrdquoTheAnnals of Statistics vol 7 no 1 pp 220ndash223 1979
International Journal of
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Active and Passive Electronic Components
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RotatingMachinery
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
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Journal ofEngineeringVolume 2014
Submit your manuscripts athttpwwwhindawicom
VLSI Design
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Shock and Vibration
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Civil EngineeringAdvances in
Acoustics and VibrationAdvances in
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Electrical and Computer Engineering
Journal of
Advances inOptoElectronics
Hindawi Publishing Corporation httpwwwhindawicom
Volume 2014
The Scientific World JournalHindawi Publishing Corporation httpwwwhindawicom Volume 2014
SensorsJournal of
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Modelling amp Simulation in EngineeringHindawi Publishing Corporation httpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Chemical EngineeringInternational Journal of Antennas and
Propagation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Navigation and Observation
International Journal of
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DistributedSensor Networks
International Journal of
International Journal of Antennas and Propagation 3
Inputdata
Symbolmapping
Subcarrierallocation
IFFTadd GI
Linearscaling
NonlinearHPA
1
nD nT
Dem
ultip
lexe
r
Symbolmapping
IFFTadd GI
NonlinearHPA
Antenna selection index from receiver
1 1
nD
Tx 1
Tx nT
(a)
middot middot middot
ChannelH
Remove GIFFT
Rece
iver
proc
essin
g Estimateddata
Channel estimation andantenna selection decision
Remove GIFFT
To transmitter
Rx 1
Rx nR
(b)
Figure 1 A simplified block diagram of a MIMO-OFDM system with per-subcarrier transmit antenna selection
For simplicity we consider ideal predistortion HPAs(ie soft envelope limiters) with a unity gain and class-Aoperation To deliver the maximum power efficiency withno nonlinear distortions in the system with nonlinear HPAsthe peak power across transmit antennas is linearly scaledto the saturation level 119875sat of the HPAs In addition asfeedback information (ie the selected antenna indiceswhichare calculated based on the channel state information) isdeployed by the transmitter all transmit branches are scaledwith the same scaling factor [16] Thus the signal after linearscaling can be expressed as
119904119894 (119899) = radic120572119904
119894 (119899) (2)
where the scaling factor 120572 = 119875sat119875 and the peak poweracross antennas 119875 = max119904
119894(119899)|119899 = 0 119870 minus 1 119894 =
1 119899119879 Each time-domain OFDM signal is then amplified
by the HPA before being transmitted via its correspondingtransmit antenna
At the receiver the received signal at each antenna is fedinto the FFT block after the GI (guard interval) is removedThe systemmodel in the frequency domain corresponding tothe 119896th subcarrier can be expressed as
y119896= radic120572H
119896x119896+ n119896
= radic120572H119896u119896+ n119896
(3)
where
x119896= [119909119896
1119909119896
2sdot sdot sdot 119909119896
119899119879]119879
H119896=
[[[[
[
ℎ119896
11ℎ11989612
sdot sdot sdot ℎ1198961119899119879
ℎ11989621
ℎ11989622
sdot sdot sdot ℎ1198962119899119879
sdot sdot sdot sdot sdot sdot sdot sdot sdot sdot sdot sdot
ℎ1198961198991198771
ℎ1198961198991198772
sdot sdot sdot ℎ119896119899119877119899119879
]]]]
]
y119896= [119910119896
11199101198962
sdot sdot sdot 119910119896119899119877]119879
n119896= [119899119896
11198991198962
sdot sdot sdot 119899119896119899119877]119879
(4)
In the above equations ℎ119896119895119894indicates the channel coefficient
between the 119894th transmit antenna and the 119895th receive antennaThe effective channel matrix H
119896is obtained by eliminating
the columns of H119896corresponding to the unselected transmit
Table 1 Antenna subsets (119899119879= 4 119899
119863= 2 and Γ = 6)
120574 Γ120574
1 1 2
2 1 3
3 1 4
4 2 3
5 2 4
6 3 4
antennas 119910119896119895and 119899119896119895denote the received signal and the noise
at the 119895th receive antenna respectively Here the noise ismodeled as a Gaussian random variable with zero mean and119864n119896n119867119896 = 1205902119899I119899119877 We assume that the receiver can perfectly
estimate the channel coefficients for example using a block-type pilot arrangement for channel estimation [18]
22 Per-Subcarrier Antenna Subset Selection In a MIMO-OFDM system with the conventional per-subcarrier antennasubset selection antenna subsets are selected independentlyfor each subcarrier [9] On each subcarrier only 119899
119863antennas
out of 119899119879available transmit antennas are active Denote
Γ120574 120574 = 1 2 Γ to be the 120574th subset consisting of 119899
119863
selected transmit antennas where Γ = (119899119863119899119879
) = 119899119879119899119863(119899119879minus
119899119863) is the number of all possible 119899
119863-element subsets Each
subset consists of 119899119863transmit antenna indices that are chosen
based on the feedback information from the receiver Forexample when 119899
119879= 4 and 119899
119863= 2 then Γ = 6 and all possible
subsets Γ120574 120574 = 1 2 6 are defined in Table 1 The choice
of the best antenna subset depends on a particular selectioncriterion
Several antenna selection criteria such as maximumcapacity or maximum SNR (signal-to-noise ratio) [19] canbe extended to this system In this paper we consider thecapacity criterion Accordingly the optimal subset at the119896th subcarrier is determined by maximizing the mutualinformation of the 119896th subchannel that is
Γ120574lowast (119896) = arg max
Γ120574 120574=1Γ
119868119896
120574 (5)
where
119868119896
120574= log2(det(I
119899119877+
120588
119899119863
H119896H119867119896)) (6)
4 International Journal of Antennas and Propagation
is the instantaneous mutual information associated with the119896th subchannel [5] Here 120588 = 119875
1199051205902119899
= 12057211989911986312059021205902119899 and
119875119905= 1205721198991198631205902 is the total transmit power per subchannel Also
we have assumed in (6) that the transmit power is allocateduniformly across antennas This is due to the fact that thefeedback information in our system is only the selectedantenna indices (ie not sufficient enough to perform powerallocation algorithms across subcarriers as well as antennas)The average mutual information across subcarriers can nowbe expressed as
119868 (120588H) =1
119870
119870minus1
sum119896=0
119868119896
120574lowast (7)
3 A Proposed Strategy forPeak-Power Reduction
In Section 2 we have described the MIMO-OFDM systemwith the conventional selection scheme It can be noted thatthe number of data subcarriers assigned to each transmitantenna might be significantly different depending on thechannel condition In the systemwith identical linear scalingto achieve the maximal overall power efficiency of HPAs thepeak power across antennas should be as small as possibleWe note that the peak power of the signal on each branchdepends on both the transmitted constellation symbols andthe number of data subcarriers allocated in each OFDMsymbol (cf (1)) Thus it is not sufficient to reduce the peakpower by solely implementing PAPR reduction techniquesMore specifically PAPR reduction techniques themselvescannot solve the problem of imbalance allocation of datasubcarriers across antennas To reduce the peak power acrossantennas we propose a two-step strategy consisting of thefollowing
Step 1 Allocate the same number of data subcarriers to alltransmit antennas (ie selecting antennas under a constraintthat all antennas have the same number of data subcarriersas illustrated in Figure 2(b)) Once this is achieved thetime-domain signals on all transmit branches have the sameaverage power Moreover as we will mathematically prove inSection 41 the peak power across antennas is reduced
Step 2 Reallocate data symbols across antennasThis processwill alter the statistical distribution of signals and thus furtherreduce the peak power
We note that this paper does not focus on developingoriginal techniques for either equal allocation of data subcar-riers or peak-power reduction Instead we are interested inanalyzing power efficiency of HPAs and energy efficiency inper-subcarrier antenna selection OFDM systems which hasnot been considered so far The two steps in our proposedstrategy described in Sections 31 and 32 are accomplishedby extending the suitable approaches available in the litera-ture to the context of the considered system
31 Optimal Equal Allocation of Data Subcarriers The opti-mal constrained antenna selection scheme based on linearoptimization was considered in [11 12] to improve error per-formance of OFDM systems suffering nonlinear distortionsdue to HPAs We now consider this method for the first stepof our strategy to achieve a better power delivery in a linearlyscaled MIMO-OFDM system Specifically we define a vari-able 119911
119896
120574 where 119911119896
120574= 1 if Γ
120574is chosen for the 119896th subcarrier
and 119911119896120574= 0 otherwise Also denote 119888119896
120574to be the cost associated
with the chosen subset Γ120574 Here 119888119896
120574= 119868119896120574as the maximum
capacity criterion is considered By denoting vectors z =
(11991101 1199110
Γ 11991111 1199111
Γ 119911119870minus1
1 119911119870minus1
Γ)119879
isin 0 1119870Γtimes1 and
c = (11988801 1198880
Γ 11988811 1198881
Γ 119888119870minus1
1 119888119870minus1
Γ)119879
isin R119870Γtimes1 anoptimal solution for an equal allocation of data subcarriersis obtained by solving the following linear optimizationproblem [11 12]
maxzisin01119870Γtimes1
c119879z
subject to Az = a(8)
where A1= I119870otimes 1119879Γisin 0 1
119870times119870Γ A2= 1119879119870otimes IΓisin 0 1
Γtimes119870ΓA = (A119879
1A1198792)119879
isin 0 1(119870+Γ)times119870Γ a = (1119879
119870120582119879)119879 and 120582 =
(1205821 1205822 120582
Γ)119879 where 120582
120574is the number of times that the
subset Γ120574is selected The constraint in (8) means that only
119899119863antennas are allowed to transmit data symbols on each
subcarrier and all transmit antennas have the same numberof allocated data subcarriers It is important to note that thisbinary linear optimization problem can be relaxed to linearprogramming with integral solutions [12] Hence (8) can besolved efficiently by the known linear programmingmethodssuch as the simplex methods or interior point methods [20]
32 Data Allocation with Peak-Power Reduction To furtherreduce the peak power of the whole system various availablePAPR reduction techniques (eg see [14] and the referencestherein) can be now adopted In this paper we are interestedin a selected mapping (SLM) technique [21] as SLM is adistortionless PAPR technique that could achieve a goodPAPR reduction [14 21] One of the most important steps inSLM is creating a set of candidates that represents the samedata information To exploit the available degrees of freedomin multiple-antenna systems for peak-power reduction wepropose to create a set of candidates using cross-antennapermutations In the literature a SLM-based scheme thatcould exploit the available degrees of freedom was firstdeveloped in [22] The scheme in [22] creates candidatesby performing cross-antenna rotation and inversion (CARI)based on a defined random matrix However that scheme isproposed for an Alamouti code basedMIMO-OFDM systemonly In a per-subcarrier antenna selection OFDM systemCARI cannot be implemented directly as only 119899
119863out of 119899
119879
antennas are active on each subcarrier To create candidates inour scheme we perform cross-antenna permutations insteadof CARI In addition we utilize an antenna allocation patternthat is already known by the transmitter and receiver insteadof storing a defined random matrix at both transmitter and
International Journal of Antennas and Propagation 5
Antennas
Subcarriers
Tx 1
Tx 2
Tx 3
Tx 4
Data
Not used
(a) Unbalanced-power selection
Data
Not used
Antennas
Subcarriers
Tx 1
Tx 2
Tx 3
Tx 4
(b) Balanced-power selection
Figure 2 Illustration of per-subcarrier antenna subset selection (119899119879= 4 119899
119863= 2 and 119870 = 12)
Ant
enna
s
Subcarriers
1st candidate(original)
x11 x
21
x12
x32
x33 x
43
x24 x
44
0 0
0
00
0 0
0
(a)
2nd candidate (permutedata on the 1st antenna)
Subcarriers
x12 x
24 0 0
00
00
0 0
x11 x
32
x33 x
43
x44
x21
(b)
3rd candidate (permutedata on the 2nd antenna)
Subcarriers
Ant
enna
s
x12
x21 0 0
00
00
0 0
x11 x
33
x32 x
43
x44
x24
(c)
4th candidate (permutedata on the 3rd antenna)
Subcarriers
0 0
00
00
0 0
x11 x
21
x12 x
33
x32 x
44
x43x
24
(d)
Figure 3 Illustration of cross-antenna permutations (119899119879= 4 119899
119863= 2 and 119870 = 4)
receiver as in [22] The proposed algorithm is described asfollows
(1) Create 119882 candidates by performing cross-antennaspermutations An illustration of this process in thesystem with 119899
119863= 2 119899
119879= 4 and 119870 = 4 is
shown in Figure 3 Accordingly the first candidateis the original data allocation The second candidateis obtained by permuting all symbols on the firstantennas with their associated symbols on the otherantennasThe third and fourth candidates are createdin a similar manner To obtain a larger number ofcandidates all symbols on the antenna that are goingbe permutated need first have their phase rotated (iebeing multiplied with an element of a phase set ega 4-phase set is 0 1205872 120587 31205872)
(2) Calculate the peak powers of all available candidates(3) Select the candidate with the minimum peak power
for transmission
To recover the transmitted data the transmitter needs toinform the receiver which candidates have been selectedThus the number of side information bits in this scheme islog2119882 which is similar to that in [22]
33 Complexity Considerations In this subsection the com-plexity of the proposed allocation scheme is compared tothat of the conventional (imbalance) allocation scheme Inthe first step of the proposed scheme to realize an equalallocation of data subcarriers the optimization problem in (8)
needs to be solved at the receiverWenote that this linear opti-mization problem can be solved in polynomial time Morespecifically the complexity to solve this problem using inte-rior point methods can be reduced to 119874([(119870Γ)
3 ln(119870Γ)]120585)
where119874(sdot) denotes an order of complexity and 120585 is the bit sizeof the optimization problem [23] In addition it is noted thatthis step is transparent to the transmitter (ie no additionalcomplexity is required at the transmitter) In the secondstep a major additional complexity lies in the required IFFToperations due to additional 119882 candidates As an 119870 point-IFFT requires 119870log
2119870 complex additions and (1198702)log
2119870
complex multiplications the numbers of complex additionsand complex multiplications in the conventional scheme are119899119879119870log2119870 and 119899
119879(1198702)log
2119870 respectivelyMeanwhile in the
proposed scheme with 119882 candidates 119882119899119879119870log2119870 complex
additions and 119882119899119879(1198702)log
2119870 complex multiplications are
required However as we will show analytically in Section 4and numerically in Section 6 an improvement in the peak-power reduction reduces when 119882 becomes large Thus asmall value of 119882 is generally chosen which does not incurmuch additional complexity Finally the amount of feedbackinformation in the proposed scheme is similar to that in theconventional scheme
4 Analysis of Power Efficiency
41 Statistical Distribution of Peak Power Before proceedingto analyze the power efficiency of HPAs we need to investi-gate the distribution of the peak power of the MIMO-OFDMsignals (ie the peak power across transmit antennas) We
6 International Journal of Antennas and Propagation
consider the complementary cumulative distribution func-tion (CCDF) of the peak power defined as the probability thatthe peak power 119875 exceeds a given threshold 119875
0 that is
CCDF119875 (1198750) = Pr (119875 gt 119875
0) (9)
Note that although a procedure for calculating CCDF ofPAPR in OFDM systems is known to the best of ourknowledge all the CCDF expressions with respect toMIMO-OFDM signals available in the literature assume that all datasubcarriers are active which can be considered as a specialcase in the considered system when all the transmit antennashave the same number of allocated data symbols In thefollowing we calculate the CCDF of the peak power in oursystem
Let us begin with the discrete-time OFDM signal 119904119894(119899)
119899 = 0 1 119870minus1 corresponding to the 119894th transmit antennaThe peak power of this signal is defined as
119875119894= max0le119899le119870minus1
|119904119894 (119899) |2 (10)
For analytical tractability we assume that both the real partand imaginary part of the signal 119904
119894(119899) are asymptotically
independent and identically distributed Gaussian randomvariables Note that this assumption which is based on thecentral limit theorem [24] only holds when the number ofassigned data subcarriers on the 119894th antenna denoted as119870119894 is large enough As a result |119904
119894(119899)| follows the Rayleigh
distribution and |119904119894(119899)|2 has a chi-square distribution with
two degrees of freedom The probability density function ofthe signal |119904
119894(119899)|2 can be expressed as [24]
119901|119904|2 (
100381610038161003816100381611990411989410038161003816100381610038162) =
1
1205902119870119894
119890minus|119904119894|21205902
119870119894 (11)
where 1205902119870119894
= 1205902119870119894119870 is the variance of the signal |119904
119894(119899)| Note
that sum119899119879
119894=1119870119894
= 119899119863119870 thus we have sum
119899119879
119894=11205902119870119894
= 1198991198631205902 The
CDF (cumulative distribution function) of the signal |119904119894(119899)|2
is given as
Pr (100381610038161003816100381611990411989410038161003816100381610038162le 120579) = 1 minus 119890
minus1205791205902
119870119894 120579 ge 0 (12)
Suppose that 119870 samples of |119904119894(119899)| 119899 = 0 1 119870 minus 1 are
independent the CDF of the peak power 119875119894can be expressed
as
CDF119875119894 = Pr (119875119894le 1198750)
= Pr (1003816100381610038161003816119904119894 (0)10038161003816100381610038162le 1198750)Pr (1003816100381610038161003816119904119894 (1)
10038161003816100381610038162le 1198750) sdot sdot sdot
Pr (1003816100381610038161003816119904119894 (119870 minus 1)10038161003816100381610038162le 1198750)
= (1 minus 119890minus1198750120590
2
119870119894 )119870
(13)
In MIMO-OFDM systems with linear scaling the peakpower across transmit antennas 119875 can be defined as
119875 = max1le119894le119899119879
119875119894 (14)
Given the statistical independence of data among transmitantennas which is the case in the considered spatial mul-tiplexed OFDM system the CDF of the peak power 119875 iscalculated as
CDF119875 = Pr (119875 le 1198750)
= Pr (1198751le 1198750)Pr (119875
2le 1198750) sdot sdot sdotPr (119875
119899119879le 1198750)
=
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
(15)
Therefore the CCDF of the peak power of the antennaselection MIMO-OFDM signals can be expressed as
CCDF119875imbalance (1198750) = 1 minus CDF119875
= 1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
(16)
In the MIMO-OFDM system with a power balancingconstraint the number of allocated data subcarriers pertransmit antenna is equal to one another (ie 119870
119894=
119899119863119870119899119879
= 119870 forall119894 = 1 2 119899119879) Thus the variances of the
signals are 1205902119870119894
= 1198991198631205902119899119879= 1205902119870 forall119894 = 1 2 119899
119879 As a result
the CCDF expression could be simplified to as
CCDF119875balance (1198750) = 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(17)
A comparison of the CCDF of the peak powers in the twosystems is presented in the following theorem
Theorem 1 In MIMO-OFDM transmission schemes that con-sist of inactive data subcarriers (eg per-subcarrier antennaselection) the probability of occurrences of high peak power isthe smallest when the same number of data symbols is allocatedto all transmit antennas that is
CCDF119875balance (1198750) le CCDF119875imbalance (1198750) (18)
Proof The proof is given in Appendix AWhen the peak-power reduction algorithm proposed in
Section 32 is implemented in theMIMO-OFDMsystemwitha power-balancing constraint the CCDF of the peak powercan be expressed as
CCDF119875balance+reduced (1198750) = (CCDF119875balance (1198750))119882
= (1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870)119882
(19)
where 119882 is the number of candidates that are assumed tobe independent Recall that by definition the CCDF value isalways smaller than one (cf (9)) Therefore the CCDF valuein (19) is smaller than that in (17) that is
CCDF119875balance+reduced (1198750) le CCDF119875balance (1198750) (20)
International Journal of Antennas and Propagation 7
42 Power Efficiency of HPAs We now analyze the powerefficiency (PE) of high-power amplifiers (HPAs) The drainefficiency of HPAs which is defined as a ratio between thepower drawn from the DC source 119875dc and the average outputpower 119875out is considered in this paper Denote 119875119894in and 119875119894out tobe the average input and output powers of the HPA for the119894th antenna respectively Recall that all HPAs are assumedto have a unity gain that is 119875119894out = 119875119894in forall119894 = 1 2 119899
119879
Hence the instantaneous overall power efficiency of HPAs inthe MIMO-OFDM system can be expressed as [16]
120578PE
=sum119899119879
119894=1119875119894out
119899119879119875dc
=sum119899119879
119894=1119875119894in
119899119879119875dc
= 1205721198991198631205902
119899119879119875dc
=1198991198631205902119875sat
119899119879119875dc
1
119875=
1198991198631205902
2119899119879
1
119875
(21)
In the above manipulations we have used the fact thatsum119899119879
119894=1119875119894in = 120572119899
1198631205902 and119875dc = 2119875sat for class-AHPAs regardless
of the average powers of the input time-domain signalsDenoting CCDFPE (120578PE
0) = Pr(120578PE gt 120578PE
0) to be the CCDF
of the power efficiency we obtain the following result withrespect to 120578
PE
Theorem 2 In per-subcarrier antenna selection MIMO-OFDM systems with linear scaling the probability of achievinghigh instantaneous overall power efficiency of HPAs is thelargest when all transmit antennas have the same number ofallocated data symbols that is
CCDFPEbalance (120578PE0) ge CCDFPEimbalance (120578
PE0) (22)
where
CCDFPEbalance (120578PE0) = (1 minus 119890
minus12120578PE0 )119899119879119870
CCDFPEimbalance (120578PE0) =
119899119879
prod119894=1
(1 minus 119890minus1198991198631198702119899119879119870119894120578
PE0 )119870
(23)
Proof From (18) and (21) it is readily to obtain (22) and (23)With respect to the average value of the overall power
efficiency from (21) we can express
120578PE
= 119864 120578PE =
1198991198631205902
2119899119879
1198641
119875 =
1198991198631205902
2119899119879
int1
119909119901 (119909) 119889119909 (24)
where 119901(119909) is the pdf (probability distribution function) ofthe peak power In the system with a balance constraint (ieonly use Step 1) the pdf of the peak power can be calculatedas
119901balance (119909) =119889
119889119909CDF119875balance (119909) =
119889
119889119909(1 minus 119890
minus1199091205902
119870)119899119879119870
=119899119879119870
1205902119870
119890minus1199091205902
119870(1 minus 119890minus1199091205902
119870)119899119879119870minus1
(25)
Hence
120578PEbalance =
1198991198631205902
2119899119879
int1
119909119901balance (119909) 119889119909
=119899119879119870
2int1198701205902
119870
1205902
119870
1
119909119890minus1199091205902
119870(1 minus 119890minus1199091205902
119870)119899119879119870minus1
119889119909
=119899119879119870
2int119870
1
1
119909119890minus119909
(1 minus 119890minus119909
)119899119879119870minus1
119889119909
(26)
Similarly the power efficiency of HPAs in the conventionalsystem is
120578PEimbalance =
1198991198631205902
2119899119879
int1
119909119901imbalance (119909) 119889119909
=1198991198631198701205902
2119899119879
int119870max120590
2
max
1205902
max
1
119909
119899119879
sum119895=1
119890minus1199091205902
119870119895
(1 minus 119890minus1199091205902
119870119895 ) 1205902119870119895
times
119899119879
prod119894=1
(1 minus 119890minus1199091205902
119870119894 )119870
119889119909
(27)
where 1205902max = max12059021198701
1205902119870119899119879
and 119870max = max1198701
119870119899119879When the peak-power reduction algorithm is also imple-
mented (ie the system employs both Steps 1 and 2) it isreadily from (20) and (21) that
CCDFPEbalance+reduced (120578PE0
) ge CCDFPEbalance (120578PE0
) (28)
where
CCDFPEbalance+reduced (120578PE0
) = 1 minus (1 minus (1 minus 119890minus12120578
PE0 )119899119879119870
)119882
(29)
Also the average power efficiency can now be calculated as
120578PEbalance+reduced =
1198991198631205902
2119899119879
int1
119909119901balance+reduced (119909) 119889119909
=119899119879119870119882
2int119870
1
1
119909119890minus119909
(1 minus 119890minus119909
)119899119879119870minus1
times (1 minus (1 minus 119890minus119909
)119899119879119870
)119882minus1
119889119909
(30)
It can be seen from (30) that the smaller the peak poweris reduced (ie the larger the number of candidates 119882 isused) the higher the power efficiency could be achievedNote that although the integrals in (26) (27) and (30) haveno closed-form solutions they can be evaluated numericallyAlso the average power efficiencies in (26) (27) and (30) aretaken with respect to the input data In other words they areconsidered as instantaneous power efficiencieswith respect tothe channel distribution Consequently the power efficiencyin the systems is obtained by averaging these values over thefading channel distribution
8 International Journal of Antennas and Propagation
5 Analyses of Capacity and Energy Efficiency
It has been shown in (22) and (28) that the proposed systemcould achieve a better power efficiency of HPAs than itscounterpart Thus when the power 119875dc is fixed it is intuitivethat an increased average power efficiency results in anincreased average transmit power and in turn leads to anincrease in the achievable rate Moreover an increase in thedata rate under a constant consumption power will translateinto an improvement in energy efficiency The achievedcapacity and energy efficiency are now investigated in thissection
51 System Capacity We begin by rewriting the mutualinformation in (7) with respect to the average SNR valueof 120588 = 119875
1199051205902119899 where 119875
119905= 120572119899
1198631205902 = 120578
PE119899119879119875dc (cf (21))
The ergodic capacity is then calculated by averaging themutual information over the fading channel distributionthat is 119862(120588) = 119864H119868(120588H) From (6) and (7) the mutualinformation in the proposed and conventional systems canbe expressed respectively as
119868 (120588proposedH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
(31)
119868 (120588imbalanceH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(32)
where 120588proposed = 120578PEproposed119899119879119875dc120590
2
119899and 120588imbalance =
120578PEimbalance119899119879119875dc120590
2
119899 Here 120578
PEproposed = 120578
PEbalance+reduced if the
peak-power reduction algorithm is implemented otherwise120578PEproposed = 120578
PEbalance Also H119896 in (31) denotes the effective
channel matrix on the 119896th subcarrier in the proposed systemwhich is obtainedwhen solving the problem in (8)This chan-nel matrix is generally different from the effective channelmatrix H
119896in the conventional system because the selected
antenna subset may be differentThe difference in the mutualinformation between the two systems can be now calculatedas
Δ119868 = 119868 (120588proposedH) minus 119868 (120588imbalanceH) =1
119870
119870minus1
sum119896=0
Δ119868119896 (33)
where
Δ119868119896= log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
minus log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(34)
For analytical simplicity we focus on the high-SNRregime At the high SNR the mutual information at the 119896thsubcarrier can be approximated as [25]
119868119896= log2(det(
120588
119899119863
Ω119896)) (35)
where
Ω119896= Ω (H
119896) =
H119896H119867119896 119899119877le 119899119863
H119867119896H119896 119899119877gt 119899119863
(36)
Thus the difference in the mutual information can berewritten as
Δ119868 =1
119870
119870minus1
sum119896=0
(log2(det(
120588proposed
119899119863
Ω119896))
minuslog2(det(
120588imbalance119899119863
Ω119896)))
= 119901log2
120578PEproposed
120578PEimbalance
minus1
119870
119870minus1
sum119896=0
Δ119896= 1198791+ 1198792
(37)
where 119901 = min(119899119863 119899119877)Ω119896= Ω(H
119896) and
Δ119896= log2(det (Ω
119896)) minus log
2(det (Ω
119896)) (38)
is the loss in the mutual information associated with the 119896thsubcarrier due to the constrained allocation Note that if bothsystems have the same selected antenna subset at the 119896thsubcarrier then Δ
119896= 0 otherwise Δ
119896gt 0Thus the total loss
in the mutual information Δ = (1119870)sum119870minus1
119896=0Δ119896gt 0
We have some important observations with respect to thevalue of Δ119868 in (37)
(i)The change in mutual information Δ119868 comes fromtwo sources The first source 119879
1is a benefit in mutual
information due to the improvement in the powerefficiency of HPAs The second source 119879
2is a penalty
that incurs because the chosen effective channelmatrices in the proposed system are different from theones in the conventional system(ii) For each channel realization thematrixH
119896is fixed
and the first term 1198791in (37) is a constant Thus the
value of Δ119868 depends on how the effective channelmatrix H
119896is selected in the constrained selection
scheme From this observation it is clear that tomake the value Δ119868 become as positive as possiblethe constrained selection method should result inthe cost penalty Δ as small as possible We note thatthe formulated optimization in (8) could achieve theminimum possible value of the total cost Hence it isexpected that the constrained selection scheme basedon linear optimization will guarantee the maximumachievable value of Δ119868 In addition to have an insightinto the cost penalty we derive the upper bound ofthe expected value of the cost penalty in Appendix BBased on the obtained bound it is observed that forfixed values of 119899
119879and 119899
119863 the cost penalty becomes
smaller with an increasing value of 119902 = max(119899119863 119899119877)
International Journal of Antennas and Propagation 9
(iii) As Δ gt 0 the upper bound of the capacityimprovement can be given as
Δ119862 = 119864H Δ119868 le 119901log2119864H
120578PEproposed
120578PEimbalance
(39)
In (39) we have used Jensenrsquos inequality of119864log(119909) le log(119864119909) as log(119909) is a concavefunction Based on this bound we could estimatethe maximum improvement in capacity that couldbe realized in the proposed system compared to itscounterpart
It is now necessary to evaluate the change in capacitythat is Δ119862 We note that although the distribution of themutual information at high SNRs can be well approximatedby a Gaussian distribution [25] it is still challenging toperform a mathematical evaluation of Δ119862 from a statisticalviewpoint This is mainly due to the fact that the two termsin (37) are complicated dependent random variables Thuswe perform a numerical evaluation of Δ119862 instead Figure 4plots the empirical CCDF of 119879
1 CDF of 119879
2 and CCDF
of Δ119868 In the figure ldquo119882 = 1rdquo stands for the case in whichonly Step 1 in Section 31 is implemented The results areobtained in the systems with 119899
119879= 4 119899
119863= 2 119899
119877= 2 119870= 128
and are averaged over 103 channel realizations Details aboutother simulation parameters are described in Section 6 Thenumerical results confirm that 119879
1gt 0 and 119879
2lt 0 Moreover
as shown in Figure 4(c) Δ119868 is always positive when the peak-power reduction algorithm is implemented (ie 119882= 4 and119882 = 8) For the case of 119882 = 1 the probability of ΔI beingpositive is significant Therefore the proposed system attainsa better ergodic capacity than that in the conventional systemThe achieved capacities in the considered systems will beprovided in Section 6
52 Energy Efficiency In this subsection we further exam-ine the efficacy of the proposed system from an energy-efficiency (EE) perspective Normalized energy efficiency(bitsHzJoule) in MIMO-OFDM systems can be defined as[3 26]
120578EE
=119862 (120588)
119875total (40)
where 119862(120588) is the achievable rate and the total powerconsumption per-subchannel is 119875total = 119899
119879119875dc + 119899
119879119875RF + 119875sp
where 119875RF is the RF power consumption in each transmitbranch excluding the associatedHPA and119875sp is the basebandprocessing power consumption It can be seen from (40)that given a fixed value of 119875total a comparison of energyefficiency achieved in the two systems is based on the capacitycomparison that has been analyzed in Section 51We are nowinterested in evaluating a useful metric of energy efficiency-spectral efficiency performance Recall that the average SNR120588 is given as 120588 = 119875
1199051205902119899= 120578
PE119899119879119875dc1205902
119899 Thus we can rewrite
the energy efficiency in (40) as a function of 119875dc as
120578EE
(119875dc) =119862 (120578
PE119899119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
(41)
Table 2 Simulation parameters
Parameter ValueBandwidth 528MHzFFT size 128Number of samples in zero-padded suffix 37Modulation scheme 4-QAMIEEE 802153a channel model CM1
The energy efficiency of the proposed and conventionalsystems can now be respectively expressed as
120578EEproposed (119875dc) =
119862proposed (120578PEproposed 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEproposed 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(42)
120578EEimbalance (119875dc) =
119862imbalance (120578PEimbalance 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEimbalance 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(43)
Similarly to the case of capacity we compare the energyefficiency achieved in the two systems by means of numericalresults in the next section Note that the calculation of energyefficiency in the proposed system (ie (42)) has assumed thata reduction in spectral efficiency due to the side informationas well as additional processing power required for the peak-power reduction algorithm is negligible In fact a reductionin spectral efficiency is very small For example in a systemwith 16-QAM FFT size of 128 119899
119863= 2 and 119882= 4 (ie 2 bits
are needed for side information) a spectral efficiency lossis 2 bits(128 times 4 times 2 + 2) bits = 019 Also it was shownin [27] that the additional power cost when implementingSLM schemes is minuscule Thus the proposed peak-powerreduction algorithm in Section 32 which is a SLM-basedscheme requires a small additional power cost
6 Numerical Results
In this section we provide numerical results to validatethe analyses mentioned in the previous sections as wellas demonstrate the effectiveness of the proposed allocationscheme over its counterpart A MIMO-OFDM system with119899119879= 4 119899
119863= 2 and 119899
119877= 2 is considered in our simulations
The system parameters are listed in Table 2These parametersare chosen based on the legacy WiMedia MB-OFDM UWB(Multiband-OFDM UWB) standard [28] Also the channelCM1 defined in the IEEE 802153a channel model [29] isbased on ameasurement of a line-of-sight scenario where thedistance between the transmitter and the receiver is up to 4mMoreover the multipath gains are modeled as independentlog normally distributed random variables We assume thatperfect channel state information is available at the receiverAlso the feedback link has no delay and is error-free
10 International Journal of Antennas and Propagation
Empirical CCDF of T110
0
10minus1
10minus2
minus2 0 2
W = 1
W = 4
W = 8
(a)
100
10minus1
10minus2
minus04 minus02 0
Empirical CDF of T2
(b)
Empirical CCDF of (T1 + T2)10
0
10minus1
10minus2
minus1 minus05 0 05 1 15 2
W = 1
W = 4
W = 8
(c)
Figure 4 Statistical distributions (note 1198792is independent of119882)
61 Evaluations of Peak-Power Distribution In Figure 5 weplot the CCDFs of the peak power of time-domain signalsThe analytical curves are based on (16) (17) and (19) Mean-while the simulation curves are empirical CCDF values Thesimulation result confirms that a system with the proposedallocation scheme offers a better CCDF performance than itscounterpart As expected the occurrence of high peak poweris significantly reduced when the peak-power reductionalgorithm is implemented Also it can be seen that theimprovement associated with this algorithm is reduced withincreasing 119882 In other words a very large value of 119882 whilerequiring higher complexity in terms on the number of IFFToperations results in a marginal improvement Thus it isreasonable to choose a relatively small value for 119882 (eg119882 = 4) It is also worth noting that the analytical curvesare relatively close to the simulation curves The small gapsexist due to the fact that the assumption of independentsamples |119904
119894(119899)| to obtain (13) does not strictly hold as we have
sum119870minus1
119899=0|119904119894(119899)|2 = 1205902119870
119894by Parsevalrsquos relation [24]
62 Evaluations of Power Efficiency of HPAs Figure 6 com-pares the CCDFs of the power efficiency achieved in theproposed and conventional systems It can be seen that theprobability of power efficiency being large highly likely occursin the proposed system compared to its counterpart Also
the simulation results agree well with the analytical resultsderived in (23) and (29) In Table 3 we compare the averagepower efficiencies Here the analytical values are obtainedaccording to (26) (27) and (30) Meanwhile the simulationvalues are empirical values based on the original definitionof the drain efficiency in (21) Also these values are averagedover the fading channel realizations It can be seen that thederived expressions approximate well the achieved powerefficiencies Table 3 also provides relative improvements ofthe power efficiencies achieved in the proposed system overthe conventional system Here only 120578
PE (Simulation) valuesare used for calculating these improvements It is clear thatthe proposed system could achieve a significant improvementin terms of average power efficiency
63 Evaluations of Capacity and Energy Efficiency Figure 7shows the system capacity inMbps (ie the normalized valuein (6) is scaled upwith the system bandwidth) versus the SNRvalue of 12059021205902
119899 It is clear that a systemwith the proposed allo-
cation scheme achieves a higher capacity than its counterpartThis agrees with the analysis in Section 51 that the changein capacity Δ119862 is positive In Figure 8 we plot the energyefficiency (MbitsJoule) versus spectral efficiency (MbpsHz)This figure is obtained based on (42) and (43) when varying119875dc Other parameters are 119875RF = 100mW 119875sp = 10mW and
International Journal of Antennas and Propagation 11
Table 3 A comparison of average power efficiencies
Imbalance Proposed (119882 = 1) Proposed (119882 = 4) Proposed (119882 = 8)120578PE (Simulation) 00697 00768 00894 00942
120578PE (Analysis) 00691 00757 00892 00943
Improvement120578PEproposed minus 120578
PEimbalance
120578PEimbalance
mdash 1019 2826 3515
1 2 3 4 5 6 7 8 9
100
10minus1
10minus2
10minus3
Peak power P0
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Pr (P
gtP0)
Figure 5 Comparison of CCDFs of the peak powers
002 004 006 008 01 012 014Power efficiency
CCD
F
100
10minus1
10minus2
10minus3
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Figure 6 Comparison of CCDFs of the power efficiencies
4500
4000
3500
3000
2500
2000
1500
1000
Ergo
dic c
apac
ity (M
bps)
2 4 6 8 10 12 14
SNR (dB)
3300
3200
3100
3000
2900
2800
97 98 99 10 101
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 7 Comparison of the ergodic capacities
12059021205902119899= 15 dB As expected the improvement in the power
efficiency of HPAs results in an improved energy efficiencyIn addition it can be observed that there exists an energyefficiency-spectral efficiency tradeoff in the systems Thistradeoff clearly needs to be taken into consideration whendesigning energy-efficient per-subcarrier antenna selectionbased OFDM wireless systems
7 Conclusions
In this paper a per-subcarrier antenna subset selectionMIMO-OFDM system with linear scaling has been investi-gated from an energy-efficiency perspective We have shownthat an imbalance allocation of data subcarriers associatedwith the conventional selection scheme affects the power effi-ciency of HPAs as well as the energy-efficiency of the wholesystem To deliver the maximum overall power efficiencywe have proposed the two-step strategy consisting of equalallocation data subcarriers across antennas and peak-powerreduction It has been proved from the power-efficiency view-point that the proposed allocation scheme outperforms theconventional scheme We have also derived the expressionsfor measuring the average power efficiency Moreover theimprovements in terms of capacity and energy efficiency
12 International Journal of Antennas and Propagation
0 2 4 6 8 10400
600
800
1000
1200
1400
1600
Spectral efficiency (MbpsHz)
Ener
gy effi
cien
cy (M
bits
J)
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 8 Energy efficiency versus spectral efficiency
resulting from the improved power efficiency have beenanalyzed The analytical results are validated by simulationresults The simulation result also shows that the systemwith the proposed allocation scheme could achieve a betterefficiency efficiency-spectral energy tradeoff compared to itscounterpart
Appendices
A Proof of Theorem 1
Let us consider a function 119891(120592) = 1 minus 119890minus1198750120592 0 lt 120592 le 1205902maxwhere 1205902max = max1205902
1198701 12059021198702
1205902119870119899119879
The second derivativeof this function is
11989110158401015840(120592) =
21198750120592 minus 11987520
1205924119890minus1198750120592 (A1)
From a HPAsrsquo viewpoint it is of interest to consider thesituation when the peak power across antennas 119875
0is large
Thus we consider the scenarios of 1198750
gt 21205902max where 1205902maxis the maximum average power across antennas Under thesesituations it is clear that 11989110158401015840(120592) lt 0 forall120592 isin (0 1205902max] Hencethe function 119891(120592) is concave By applying Jensenrsquos inequalitywe obtain the following inequality
1
119899119879
119899119879
sum119894=1
119891 (1205902
119870119894) le 119891(
1
119899119879
119899119879
sum119894=1
1205902
119870119894)
= 119891(1
119899119879
119899119879
sum119894=1
1205902
119870) = 119891 (120590
2
119870)
(A2)
where the equality comes from the fact that sum119899119879
119894=11205902119870119894
=
sum119899119879
119894=11205902119870
= 1198991198631205902 Expression (A2) can be rewritten as119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le 119899119879(1 minus 119890
minus11987501205902
119870) (A3)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879
On the other hand by applying the arithmetic-geometricmean inequality and note that (1 minus 119890
minus119909) gt 0 forall119909 gt 0 we have
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1
119899119879
119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ))
119899119879
(A4)
Note that the equality in (A4) holds if and only if 1205902119870119894
= 1205902119870
forall119894 = 1 119899119879
Combining (A3) and (A4) results in
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1 minus 119890minus1198750120590
2
119870)119899119879
(A5)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879 Thus we
get the following desired inequality
1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
ge 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(A6)
or
CCDF119875imbalance (1198750) ge CCDF119875balance (1198750) (A7)
This completes the proof
B Upper Bound of an ExpectedValue of Cost Penalty
In this appendix we derive an upper bound of the expectedvalue of Δ
119896 It can be seen from (5) that among all pos-
sible matrices H119896 the matrix H
119896with the highest value of
log2(det(Ω
119896))Ω119896
= Ω(H119896) will be selected as the effective
channel matrix for the 119896th subcarrier in the conventionalscheme Meanwhile in the proposed scheme due to thebalance constraint the effective channel matrix associatedwith the kth subcarrier is not necessarily the one with thehighest log
2(det(Ω
119896)) that is log
2(det(Ω
119896)) le log
2(det(Ω
119896))
Thus the expected value of Δ119896can be computed by using
order statistics In particular an upper bound on the expecteddifference of two-order statistics the Γth and 120574th 1 le 120574 lt Γis given by [30]
119864 Δ119896 = 119864 log
2(det (Ω
119896)) minus 119864 log
2(det (Ω
119896))
le 120590119862radic
Γ (120574 + 1)
120574
(B1)
where 1205902119862is the variance of log
2(det(Ω
119896)) that is assumed to
be the same for all possible matricesH119896
On the other hand suppose that the entries of the 119899119877times119899119879
matrixH119896are iid complex Gaussian random variables with
zero mean and unit variance then for any effective channelmatrix H
119896 Ω119896is a complex Wishart matrix It follows from
[25] that the variance of log2(det(Ω
119896)) can be expressed as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1205951015840(119902 minus 119898 + 1) (B2)
International Journal of Antennas and Propagation 13
where 119901 = min(119899119863 119899119877) 119902 = max(119899
119863 119899119877) and 1205951015840(119909) =
suminfin
120593=11(120593 + 119909 minus 1)
2 is the first derivative of the digammafunction By approximating 1205951015840(119909) asymp 1119909 [25] the simplerexpression for 1205902
119862in (B2) is given as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1
119902 minus 119898 + 1 (B3)
Substitute (B3) into (B1) we finally arrive at
119864 Δ119896 le log
2(119890)radic(
119901
sum119898=1
1
119902 minus 119898 + 1) times
Γ (120574 + 1)
120574 (B4)
Conflict of Interests
The authors declare that there is no conflict of interestsregarding the publication of this paper
References
[1] L M Correia D Zeller O Blume et al ldquoChallenges andenabling technologies for energy aware mobile radio networksrdquoIEEECommunicationsMagazine vol 48 no 11 pp 66ndash72 2010
[2] Z Hasan H Boostanimehr and V K Bhargava ldquoGreen cellularnetworks a survey some research issues and challengesrdquo IEEECommunications Surveys and Tutorials vol 13 no 4 pp 524ndash540 2011
[3] J Joung C K Ho and S Sun ldquoGreenwireless communicationsa power amplifier perspectiverdquo in Proceedings of the 4th Asia-Pacific Signal and Information Processing Association AnnualSummit and Conference (APSIPA ASC rsquo12) pp 1ndash8 December2012
[4] G L Stuber J R Barry S W Mclaughlin Y E Li M AIngram and T G Pratt ldquoBroadband MIMO-OFDM wirelesscommunicationsrdquoProceedings of the IEEE vol 92 no 2 pp 271ndash294 2004
[5] H Bolcskei D Gesbert and A J Paulraj ldquoOn the capacity ofOFDM-based spatial multiplexing systemsrdquo IEEE Transactionson Communications vol 50 no 2 pp 225ndash234 2002
[6] V Tarokh N Seshadri and A R Calderbank ldquoSpace-timecodes for high data rate wireless communication performancecriterion and code constructionrdquo IEEE Transactions on Infor-mation Theory vol 44 no 2 pp 744ndash765 1998
[7] C M Vithanage M Sandell J P Coon and Y Wang ldquoPrecod-ing in OFDM-based multi-antenna ultra-wideband systemsrdquoIEEE Communications Magazine vol 47 no 1 pp 41ndash47 2009
[8] Z Tang H Suzuki and I B Collings ldquoPerformance of antennaselection forMIMO-OFDMsystems based onmeasured indoorcorrelated frequency selective channelsrdquo in Proceedings of theAustralian Telecommunication Networks and Applications Con-ference pp 435ndash439 December 2006
[9] H Zhang and R U Nabar ldquoTransmit antenna selection inMIMO-OFDM systems bulk versus per-tone selectionrdquo inProceedings of the IEEE International Conference on Communi-cations (ICC rsquo08) pp 4371ndash4375 May 2008
[10] H Shi M Katayama T Yamazato H Okada and A OgawaldquoAn adaptive antenna selection scheme for transmit diversityin OFDM systemsrdquo in Proceedings of the IEEE 54th VehicularTechnology Conference (VTC rsquo01) pp 2168ndash2172 October 2001
[11] M Sandell and J P Coon ldquoPer-subcarrier antenna selectionwith power constraints in OFDM systemsrdquo IEEE Transactionson Wireless Communications vol 8 no 2 pp 673ndash677 2009
[12] N P Le F Safaei and L C Tran ldquoTransmit antenna subsetselection for high-rate MIMO-OFDM systems in the presenceof nonlinear power amplifiersrdquo EURASIP Journal on WirelessCommunications and Networking vol 2014 article 27 2014
[13] R PrasadOFDM for Wireless Communications Systems ArtechHouse 1st edition 2004
[14] T Jiang and Y Wu ldquoAn overview peak-to-average power ratioreduction techniques for OFDM signalsrdquo IEEE Transactions onBroadcasting vol 54 no 2 pp 257ndash268 2008
[15] H Ochiai ldquoPerformance analysis of peak power and band-limited OFDM system with linear scalingrdquo IEEE Transactionson Wireless Communications vol 2 no 5 pp 1055ndash1065 2003
[16] C Zhao R J Baxley and G T Zhou ldquoPeak-to-average powerratio and power efficiency considerations in MIMO-OFDMsystemsrdquo IEEE Communications Letters vol 12 no 4 pp 268ndash270 2008
[17] D Wulich and I Gutman ldquoImpact of linear power amplifier onpower loading in OFDM part I principlesrdquo in Proceedings ofthe IEEE 26th Convention of Electrical and Electronics Engineersin Israel (IEEEI rsquo10) pp 360ndash364 November 2010
[18] S Coleri M Ergen A Puri and A Bahai ldquoChannel estimationtechniques based on pilot arrangement in OFDM systemsrdquoIEEE Transactions on Broadcasting vol 48 no 3 pp 223ndash2292002
[19] R W Heath S Sandhu and A Paulraj ldquoAntenna selectionfor spatial multiplexing systems with linear receiversrdquo IEEECommunications Letters vol 5 no 4 pp 142ndash144 2001
[20] R Fletcher Practical Methods of Optimization John Willey ampSons 2nd edition 1987
[21] R W Bauml R F H Fischer and J B Huber ldquoReducingthe peak-to-average power ratio of multicarrier modulation byselected mappingrdquo Electronics Letters vol 32 no 22 pp 2056ndash2057 1996
[22] M Tan Z Latinovic and Y Bar-Ness ldquoSTBC MIMO-OFDMpeak-to-average power ratio reduction by cross-antenna rota-tion and inversionrdquo IEEE Communications Letters vol 9 no 7pp 592ndash594 2005
[23] K M Anstreicher ldquoLinear programming in O(n3lnnL) opera-tionsrdquo SIAM Journal on Optimization vol 9 no 4 pp 803ndash8121999
[24] J G Proakis Digital Communications McGraw Hill 4th edi-tion 2001
[25] O Oyman R U Nabar H Bolcskei and A J Paulraj ldquoChar-acterizing the statistical properties of mutual information inMIMO channelsrdquo IEEE Transactions on Signal Processing vol51 no 11 pp 2784ndash2795 2003
[26] S Cui A J Goldsmith and A Bahai ldquoEnergy-constrainedmodulation optimizationrdquo IEEE Transactions onWireless Com-munications vol 4 no 5 pp 2349ndash2360 2005
[27] R J Baxley and G T Zhou ldquoPower savings analysis of peak-to-average power ratio reduction in OFDMrdquo IEEE Transactions onConsumer Electronics vol 50 no 3 pp 792ndash797 2004
[28] A Batra et al Multiband OFDM Physical Layer SpecificationRelease 1 5 WiMedia Alliance 2009
[29] J Foerster et al ldquoChannel modeling sub-committee reportfinalrdquo IEEE P802 15-02490r1-SG3a 2003
[30] B C Arnold and R A Groeneveld ldquoBounds on expectationsof linear systematic statistics based on dependent samplesrdquoTheAnnals of Statistics vol 7 no 1 pp 220ndash223 1979
International Journal of
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RotatingMachinery
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporation httpwwwhindawicom
Journal ofEngineeringVolume 2014
Submit your manuscripts athttpwwwhindawicom
VLSI Design
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
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Shock and Vibration
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Civil EngineeringAdvances in
Acoustics and VibrationAdvances in
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Electrical and Computer Engineering
Journal of
Advances inOptoElectronics
Hindawi Publishing Corporation httpwwwhindawicom
Volume 2014
The Scientific World JournalHindawi Publishing Corporation httpwwwhindawicom Volume 2014
SensorsJournal of
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Modelling amp Simulation in EngineeringHindawi Publishing Corporation httpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Chemical EngineeringInternational Journal of Antennas and
Propagation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
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Navigation and Observation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
DistributedSensor Networks
International Journal of
4 International Journal of Antennas and Propagation
is the instantaneous mutual information associated with the119896th subchannel [5] Here 120588 = 119875
1199051205902119899
= 12057211989911986312059021205902119899 and
119875119905= 1205721198991198631205902 is the total transmit power per subchannel Also
we have assumed in (6) that the transmit power is allocateduniformly across antennas This is due to the fact that thefeedback information in our system is only the selectedantenna indices (ie not sufficient enough to perform powerallocation algorithms across subcarriers as well as antennas)The average mutual information across subcarriers can nowbe expressed as
119868 (120588H) =1
119870
119870minus1
sum119896=0
119868119896
120574lowast (7)
3 A Proposed Strategy forPeak-Power Reduction
In Section 2 we have described the MIMO-OFDM systemwith the conventional selection scheme It can be noted thatthe number of data subcarriers assigned to each transmitantenna might be significantly different depending on thechannel condition In the systemwith identical linear scalingto achieve the maximal overall power efficiency of HPAs thepeak power across antennas should be as small as possibleWe note that the peak power of the signal on each branchdepends on both the transmitted constellation symbols andthe number of data subcarriers allocated in each OFDMsymbol (cf (1)) Thus it is not sufficient to reduce the peakpower by solely implementing PAPR reduction techniquesMore specifically PAPR reduction techniques themselvescannot solve the problem of imbalance allocation of datasubcarriers across antennas To reduce the peak power acrossantennas we propose a two-step strategy consisting of thefollowing
Step 1 Allocate the same number of data subcarriers to alltransmit antennas (ie selecting antennas under a constraintthat all antennas have the same number of data subcarriersas illustrated in Figure 2(b)) Once this is achieved thetime-domain signals on all transmit branches have the sameaverage power Moreover as we will mathematically prove inSection 41 the peak power across antennas is reduced
Step 2 Reallocate data symbols across antennasThis processwill alter the statistical distribution of signals and thus furtherreduce the peak power
We note that this paper does not focus on developingoriginal techniques for either equal allocation of data subcar-riers or peak-power reduction Instead we are interested inanalyzing power efficiency of HPAs and energy efficiency inper-subcarrier antenna selection OFDM systems which hasnot been considered so far The two steps in our proposedstrategy described in Sections 31 and 32 are accomplishedby extending the suitable approaches available in the litera-ture to the context of the considered system
31 Optimal Equal Allocation of Data Subcarriers The opti-mal constrained antenna selection scheme based on linearoptimization was considered in [11 12] to improve error per-formance of OFDM systems suffering nonlinear distortionsdue to HPAs We now consider this method for the first stepof our strategy to achieve a better power delivery in a linearlyscaled MIMO-OFDM system Specifically we define a vari-able 119911
119896
120574 where 119911119896
120574= 1 if Γ
120574is chosen for the 119896th subcarrier
and 119911119896120574= 0 otherwise Also denote 119888119896
120574to be the cost associated
with the chosen subset Γ120574 Here 119888119896
120574= 119868119896120574as the maximum
capacity criterion is considered By denoting vectors z =
(11991101 1199110
Γ 11991111 1199111
Γ 119911119870minus1
1 119911119870minus1
Γ)119879
isin 0 1119870Γtimes1 and
c = (11988801 1198880
Γ 11988811 1198881
Γ 119888119870minus1
1 119888119870minus1
Γ)119879
isin R119870Γtimes1 anoptimal solution for an equal allocation of data subcarriersis obtained by solving the following linear optimizationproblem [11 12]
maxzisin01119870Γtimes1
c119879z
subject to Az = a(8)
where A1= I119870otimes 1119879Γisin 0 1
119870times119870Γ A2= 1119879119870otimes IΓisin 0 1
Γtimes119870ΓA = (A119879
1A1198792)119879
isin 0 1(119870+Γ)times119870Γ a = (1119879
119870120582119879)119879 and 120582 =
(1205821 1205822 120582
Γ)119879 where 120582
120574is the number of times that the
subset Γ120574is selected The constraint in (8) means that only
119899119863antennas are allowed to transmit data symbols on each
subcarrier and all transmit antennas have the same numberof allocated data subcarriers It is important to note that thisbinary linear optimization problem can be relaxed to linearprogramming with integral solutions [12] Hence (8) can besolved efficiently by the known linear programmingmethodssuch as the simplex methods or interior point methods [20]
32 Data Allocation with Peak-Power Reduction To furtherreduce the peak power of the whole system various availablePAPR reduction techniques (eg see [14] and the referencestherein) can be now adopted In this paper we are interestedin a selected mapping (SLM) technique [21] as SLM is adistortionless PAPR technique that could achieve a goodPAPR reduction [14 21] One of the most important steps inSLM is creating a set of candidates that represents the samedata information To exploit the available degrees of freedomin multiple-antenna systems for peak-power reduction wepropose to create a set of candidates using cross-antennapermutations In the literature a SLM-based scheme thatcould exploit the available degrees of freedom was firstdeveloped in [22] The scheme in [22] creates candidatesby performing cross-antenna rotation and inversion (CARI)based on a defined random matrix However that scheme isproposed for an Alamouti code basedMIMO-OFDM systemonly In a per-subcarrier antenna selection OFDM systemCARI cannot be implemented directly as only 119899
119863out of 119899
119879
antennas are active on each subcarrier To create candidates inour scheme we perform cross-antenna permutations insteadof CARI In addition we utilize an antenna allocation patternthat is already known by the transmitter and receiver insteadof storing a defined random matrix at both transmitter and
International Journal of Antennas and Propagation 5
Antennas
Subcarriers
Tx 1
Tx 2
Tx 3
Tx 4
Data
Not used
(a) Unbalanced-power selection
Data
Not used
Antennas
Subcarriers
Tx 1
Tx 2
Tx 3
Tx 4
(b) Balanced-power selection
Figure 2 Illustration of per-subcarrier antenna subset selection (119899119879= 4 119899
119863= 2 and 119870 = 12)
Ant
enna
s
Subcarriers
1st candidate(original)
x11 x
21
x12
x32
x33 x
43
x24 x
44
0 0
0
00
0 0
0
(a)
2nd candidate (permutedata on the 1st antenna)
Subcarriers
x12 x
24 0 0
00
00
0 0
x11 x
32
x33 x
43
x44
x21
(b)
3rd candidate (permutedata on the 2nd antenna)
Subcarriers
Ant
enna
s
x12
x21 0 0
00
00
0 0
x11 x
33
x32 x
43
x44
x24
(c)
4th candidate (permutedata on the 3rd antenna)
Subcarriers
0 0
00
00
0 0
x11 x
21
x12 x
33
x32 x
44
x43x
24
(d)
Figure 3 Illustration of cross-antenna permutations (119899119879= 4 119899
119863= 2 and 119870 = 4)
receiver as in [22] The proposed algorithm is described asfollows
(1) Create 119882 candidates by performing cross-antennaspermutations An illustration of this process in thesystem with 119899
119863= 2 119899
119879= 4 and 119870 = 4 is
shown in Figure 3 Accordingly the first candidateis the original data allocation The second candidateis obtained by permuting all symbols on the firstantennas with their associated symbols on the otherantennasThe third and fourth candidates are createdin a similar manner To obtain a larger number ofcandidates all symbols on the antenna that are goingbe permutated need first have their phase rotated (iebeing multiplied with an element of a phase set ega 4-phase set is 0 1205872 120587 31205872)
(2) Calculate the peak powers of all available candidates(3) Select the candidate with the minimum peak power
for transmission
To recover the transmitted data the transmitter needs toinform the receiver which candidates have been selectedThus the number of side information bits in this scheme islog2119882 which is similar to that in [22]
33 Complexity Considerations In this subsection the com-plexity of the proposed allocation scheme is compared tothat of the conventional (imbalance) allocation scheme Inthe first step of the proposed scheme to realize an equalallocation of data subcarriers the optimization problem in (8)
needs to be solved at the receiverWenote that this linear opti-mization problem can be solved in polynomial time Morespecifically the complexity to solve this problem using inte-rior point methods can be reduced to 119874([(119870Γ)
3 ln(119870Γ)]120585)
where119874(sdot) denotes an order of complexity and 120585 is the bit sizeof the optimization problem [23] In addition it is noted thatthis step is transparent to the transmitter (ie no additionalcomplexity is required at the transmitter) In the secondstep a major additional complexity lies in the required IFFToperations due to additional 119882 candidates As an 119870 point-IFFT requires 119870log
2119870 complex additions and (1198702)log
2119870
complex multiplications the numbers of complex additionsand complex multiplications in the conventional scheme are119899119879119870log2119870 and 119899
119879(1198702)log
2119870 respectivelyMeanwhile in the
proposed scheme with 119882 candidates 119882119899119879119870log2119870 complex
additions and 119882119899119879(1198702)log
2119870 complex multiplications are
required However as we will show analytically in Section 4and numerically in Section 6 an improvement in the peak-power reduction reduces when 119882 becomes large Thus asmall value of 119882 is generally chosen which does not incurmuch additional complexity Finally the amount of feedbackinformation in the proposed scheme is similar to that in theconventional scheme
4 Analysis of Power Efficiency
41 Statistical Distribution of Peak Power Before proceedingto analyze the power efficiency of HPAs we need to investi-gate the distribution of the peak power of the MIMO-OFDMsignals (ie the peak power across transmit antennas) We
6 International Journal of Antennas and Propagation
consider the complementary cumulative distribution func-tion (CCDF) of the peak power defined as the probability thatthe peak power 119875 exceeds a given threshold 119875
0 that is
CCDF119875 (1198750) = Pr (119875 gt 119875
0) (9)
Note that although a procedure for calculating CCDF ofPAPR in OFDM systems is known to the best of ourknowledge all the CCDF expressions with respect toMIMO-OFDM signals available in the literature assume that all datasubcarriers are active which can be considered as a specialcase in the considered system when all the transmit antennashave the same number of allocated data symbols In thefollowing we calculate the CCDF of the peak power in oursystem
Let us begin with the discrete-time OFDM signal 119904119894(119899)
119899 = 0 1 119870minus1 corresponding to the 119894th transmit antennaThe peak power of this signal is defined as
119875119894= max0le119899le119870minus1
|119904119894 (119899) |2 (10)
For analytical tractability we assume that both the real partand imaginary part of the signal 119904
119894(119899) are asymptotically
independent and identically distributed Gaussian randomvariables Note that this assumption which is based on thecentral limit theorem [24] only holds when the number ofassigned data subcarriers on the 119894th antenna denoted as119870119894 is large enough As a result |119904
119894(119899)| follows the Rayleigh
distribution and |119904119894(119899)|2 has a chi-square distribution with
two degrees of freedom The probability density function ofthe signal |119904
119894(119899)|2 can be expressed as [24]
119901|119904|2 (
100381610038161003816100381611990411989410038161003816100381610038162) =
1
1205902119870119894
119890minus|119904119894|21205902
119870119894 (11)
where 1205902119870119894
= 1205902119870119894119870 is the variance of the signal |119904
119894(119899)| Note
that sum119899119879
119894=1119870119894
= 119899119863119870 thus we have sum
119899119879
119894=11205902119870119894
= 1198991198631205902 The
CDF (cumulative distribution function) of the signal |119904119894(119899)|2
is given as
Pr (100381610038161003816100381611990411989410038161003816100381610038162le 120579) = 1 minus 119890
minus1205791205902
119870119894 120579 ge 0 (12)
Suppose that 119870 samples of |119904119894(119899)| 119899 = 0 1 119870 minus 1 are
independent the CDF of the peak power 119875119894can be expressed
as
CDF119875119894 = Pr (119875119894le 1198750)
= Pr (1003816100381610038161003816119904119894 (0)10038161003816100381610038162le 1198750)Pr (1003816100381610038161003816119904119894 (1)
10038161003816100381610038162le 1198750) sdot sdot sdot
Pr (1003816100381610038161003816119904119894 (119870 minus 1)10038161003816100381610038162le 1198750)
= (1 minus 119890minus1198750120590
2
119870119894 )119870
(13)
In MIMO-OFDM systems with linear scaling the peakpower across transmit antennas 119875 can be defined as
119875 = max1le119894le119899119879
119875119894 (14)
Given the statistical independence of data among transmitantennas which is the case in the considered spatial mul-tiplexed OFDM system the CDF of the peak power 119875 iscalculated as
CDF119875 = Pr (119875 le 1198750)
= Pr (1198751le 1198750)Pr (119875
2le 1198750) sdot sdot sdotPr (119875
119899119879le 1198750)
=
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
(15)
Therefore the CCDF of the peak power of the antennaselection MIMO-OFDM signals can be expressed as
CCDF119875imbalance (1198750) = 1 minus CDF119875
= 1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
(16)
In the MIMO-OFDM system with a power balancingconstraint the number of allocated data subcarriers pertransmit antenna is equal to one another (ie 119870
119894=
119899119863119870119899119879
= 119870 forall119894 = 1 2 119899119879) Thus the variances of the
signals are 1205902119870119894
= 1198991198631205902119899119879= 1205902119870 forall119894 = 1 2 119899
119879 As a result
the CCDF expression could be simplified to as
CCDF119875balance (1198750) = 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(17)
A comparison of the CCDF of the peak powers in the twosystems is presented in the following theorem
Theorem 1 In MIMO-OFDM transmission schemes that con-sist of inactive data subcarriers (eg per-subcarrier antennaselection) the probability of occurrences of high peak power isthe smallest when the same number of data symbols is allocatedto all transmit antennas that is
CCDF119875balance (1198750) le CCDF119875imbalance (1198750) (18)
Proof The proof is given in Appendix AWhen the peak-power reduction algorithm proposed in
Section 32 is implemented in theMIMO-OFDMsystemwitha power-balancing constraint the CCDF of the peak powercan be expressed as
CCDF119875balance+reduced (1198750) = (CCDF119875balance (1198750))119882
= (1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870)119882
(19)
where 119882 is the number of candidates that are assumed tobe independent Recall that by definition the CCDF value isalways smaller than one (cf (9)) Therefore the CCDF valuein (19) is smaller than that in (17) that is
CCDF119875balance+reduced (1198750) le CCDF119875balance (1198750) (20)
International Journal of Antennas and Propagation 7
42 Power Efficiency of HPAs We now analyze the powerefficiency (PE) of high-power amplifiers (HPAs) The drainefficiency of HPAs which is defined as a ratio between thepower drawn from the DC source 119875dc and the average outputpower 119875out is considered in this paper Denote 119875119894in and 119875119894out tobe the average input and output powers of the HPA for the119894th antenna respectively Recall that all HPAs are assumedto have a unity gain that is 119875119894out = 119875119894in forall119894 = 1 2 119899
119879
Hence the instantaneous overall power efficiency of HPAs inthe MIMO-OFDM system can be expressed as [16]
120578PE
=sum119899119879
119894=1119875119894out
119899119879119875dc
=sum119899119879
119894=1119875119894in
119899119879119875dc
= 1205721198991198631205902
119899119879119875dc
=1198991198631205902119875sat
119899119879119875dc
1
119875=
1198991198631205902
2119899119879
1
119875
(21)
In the above manipulations we have used the fact thatsum119899119879
119894=1119875119894in = 120572119899
1198631205902 and119875dc = 2119875sat for class-AHPAs regardless
of the average powers of the input time-domain signalsDenoting CCDFPE (120578PE
0) = Pr(120578PE gt 120578PE
0) to be the CCDF
of the power efficiency we obtain the following result withrespect to 120578
PE
Theorem 2 In per-subcarrier antenna selection MIMO-OFDM systems with linear scaling the probability of achievinghigh instantaneous overall power efficiency of HPAs is thelargest when all transmit antennas have the same number ofallocated data symbols that is
CCDFPEbalance (120578PE0) ge CCDFPEimbalance (120578
PE0) (22)
where
CCDFPEbalance (120578PE0) = (1 minus 119890
minus12120578PE0 )119899119879119870
CCDFPEimbalance (120578PE0) =
119899119879
prod119894=1
(1 minus 119890minus1198991198631198702119899119879119870119894120578
PE0 )119870
(23)
Proof From (18) and (21) it is readily to obtain (22) and (23)With respect to the average value of the overall power
efficiency from (21) we can express
120578PE
= 119864 120578PE =
1198991198631205902
2119899119879
1198641
119875 =
1198991198631205902
2119899119879
int1
119909119901 (119909) 119889119909 (24)
where 119901(119909) is the pdf (probability distribution function) ofthe peak power In the system with a balance constraint (ieonly use Step 1) the pdf of the peak power can be calculatedas
119901balance (119909) =119889
119889119909CDF119875balance (119909) =
119889
119889119909(1 minus 119890
minus1199091205902
119870)119899119879119870
=119899119879119870
1205902119870
119890minus1199091205902
119870(1 minus 119890minus1199091205902
119870)119899119879119870minus1
(25)
Hence
120578PEbalance =
1198991198631205902
2119899119879
int1
119909119901balance (119909) 119889119909
=119899119879119870
2int1198701205902
119870
1205902
119870
1
119909119890minus1199091205902
119870(1 minus 119890minus1199091205902
119870)119899119879119870minus1
119889119909
=119899119879119870
2int119870
1
1
119909119890minus119909
(1 minus 119890minus119909
)119899119879119870minus1
119889119909
(26)
Similarly the power efficiency of HPAs in the conventionalsystem is
120578PEimbalance =
1198991198631205902
2119899119879
int1
119909119901imbalance (119909) 119889119909
=1198991198631198701205902
2119899119879
int119870max120590
2
max
1205902
max
1
119909
119899119879
sum119895=1
119890minus1199091205902
119870119895
(1 minus 119890minus1199091205902
119870119895 ) 1205902119870119895
times
119899119879
prod119894=1
(1 minus 119890minus1199091205902
119870119894 )119870
119889119909
(27)
where 1205902max = max12059021198701
1205902119870119899119879
and 119870max = max1198701
119870119899119879When the peak-power reduction algorithm is also imple-
mented (ie the system employs both Steps 1 and 2) it isreadily from (20) and (21) that
CCDFPEbalance+reduced (120578PE0
) ge CCDFPEbalance (120578PE0
) (28)
where
CCDFPEbalance+reduced (120578PE0
) = 1 minus (1 minus (1 minus 119890minus12120578
PE0 )119899119879119870
)119882
(29)
Also the average power efficiency can now be calculated as
120578PEbalance+reduced =
1198991198631205902
2119899119879
int1
119909119901balance+reduced (119909) 119889119909
=119899119879119870119882
2int119870
1
1
119909119890minus119909
(1 minus 119890minus119909
)119899119879119870minus1
times (1 minus (1 minus 119890minus119909
)119899119879119870
)119882minus1
119889119909
(30)
It can be seen from (30) that the smaller the peak poweris reduced (ie the larger the number of candidates 119882 isused) the higher the power efficiency could be achievedNote that although the integrals in (26) (27) and (30) haveno closed-form solutions they can be evaluated numericallyAlso the average power efficiencies in (26) (27) and (30) aretaken with respect to the input data In other words they areconsidered as instantaneous power efficiencieswith respect tothe channel distribution Consequently the power efficiencyin the systems is obtained by averaging these values over thefading channel distribution
8 International Journal of Antennas and Propagation
5 Analyses of Capacity and Energy Efficiency
It has been shown in (22) and (28) that the proposed systemcould achieve a better power efficiency of HPAs than itscounterpart Thus when the power 119875dc is fixed it is intuitivethat an increased average power efficiency results in anincreased average transmit power and in turn leads to anincrease in the achievable rate Moreover an increase in thedata rate under a constant consumption power will translateinto an improvement in energy efficiency The achievedcapacity and energy efficiency are now investigated in thissection
51 System Capacity We begin by rewriting the mutualinformation in (7) with respect to the average SNR valueof 120588 = 119875
1199051205902119899 where 119875
119905= 120572119899
1198631205902 = 120578
PE119899119879119875dc (cf (21))
The ergodic capacity is then calculated by averaging themutual information over the fading channel distributionthat is 119862(120588) = 119864H119868(120588H) From (6) and (7) the mutualinformation in the proposed and conventional systems canbe expressed respectively as
119868 (120588proposedH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
(31)
119868 (120588imbalanceH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(32)
where 120588proposed = 120578PEproposed119899119879119875dc120590
2
119899and 120588imbalance =
120578PEimbalance119899119879119875dc120590
2
119899 Here 120578
PEproposed = 120578
PEbalance+reduced if the
peak-power reduction algorithm is implemented otherwise120578PEproposed = 120578
PEbalance Also H119896 in (31) denotes the effective
channel matrix on the 119896th subcarrier in the proposed systemwhich is obtainedwhen solving the problem in (8)This chan-nel matrix is generally different from the effective channelmatrix H
119896in the conventional system because the selected
antenna subset may be differentThe difference in the mutualinformation between the two systems can be now calculatedas
Δ119868 = 119868 (120588proposedH) minus 119868 (120588imbalanceH) =1
119870
119870minus1
sum119896=0
Δ119868119896 (33)
where
Δ119868119896= log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
minus log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(34)
For analytical simplicity we focus on the high-SNRregime At the high SNR the mutual information at the 119896thsubcarrier can be approximated as [25]
119868119896= log2(det(
120588
119899119863
Ω119896)) (35)
where
Ω119896= Ω (H
119896) =
H119896H119867119896 119899119877le 119899119863
H119867119896H119896 119899119877gt 119899119863
(36)
Thus the difference in the mutual information can berewritten as
Δ119868 =1
119870
119870minus1
sum119896=0
(log2(det(
120588proposed
119899119863
Ω119896))
minuslog2(det(
120588imbalance119899119863
Ω119896)))
= 119901log2
120578PEproposed
120578PEimbalance
minus1
119870
119870minus1
sum119896=0
Δ119896= 1198791+ 1198792
(37)
where 119901 = min(119899119863 119899119877)Ω119896= Ω(H
119896) and
Δ119896= log2(det (Ω
119896)) minus log
2(det (Ω
119896)) (38)
is the loss in the mutual information associated with the 119896thsubcarrier due to the constrained allocation Note that if bothsystems have the same selected antenna subset at the 119896thsubcarrier then Δ
119896= 0 otherwise Δ
119896gt 0Thus the total loss
in the mutual information Δ = (1119870)sum119870minus1
119896=0Δ119896gt 0
We have some important observations with respect to thevalue of Δ119868 in (37)
(i)The change in mutual information Δ119868 comes fromtwo sources The first source 119879
1is a benefit in mutual
information due to the improvement in the powerefficiency of HPAs The second source 119879
2is a penalty
that incurs because the chosen effective channelmatrices in the proposed system are different from theones in the conventional system(ii) For each channel realization thematrixH
119896is fixed
and the first term 1198791in (37) is a constant Thus the
value of Δ119868 depends on how the effective channelmatrix H
119896is selected in the constrained selection
scheme From this observation it is clear that tomake the value Δ119868 become as positive as possiblethe constrained selection method should result inthe cost penalty Δ as small as possible We note thatthe formulated optimization in (8) could achieve theminimum possible value of the total cost Hence it isexpected that the constrained selection scheme basedon linear optimization will guarantee the maximumachievable value of Δ119868 In addition to have an insightinto the cost penalty we derive the upper bound ofthe expected value of the cost penalty in Appendix BBased on the obtained bound it is observed that forfixed values of 119899
119879and 119899
119863 the cost penalty becomes
smaller with an increasing value of 119902 = max(119899119863 119899119877)
International Journal of Antennas and Propagation 9
(iii) As Δ gt 0 the upper bound of the capacityimprovement can be given as
Δ119862 = 119864H Δ119868 le 119901log2119864H
120578PEproposed
120578PEimbalance
(39)
In (39) we have used Jensenrsquos inequality of119864log(119909) le log(119864119909) as log(119909) is a concavefunction Based on this bound we could estimatethe maximum improvement in capacity that couldbe realized in the proposed system compared to itscounterpart
It is now necessary to evaluate the change in capacitythat is Δ119862 We note that although the distribution of themutual information at high SNRs can be well approximatedby a Gaussian distribution [25] it is still challenging toperform a mathematical evaluation of Δ119862 from a statisticalviewpoint This is mainly due to the fact that the two termsin (37) are complicated dependent random variables Thuswe perform a numerical evaluation of Δ119862 instead Figure 4plots the empirical CCDF of 119879
1 CDF of 119879
2 and CCDF
of Δ119868 In the figure ldquo119882 = 1rdquo stands for the case in whichonly Step 1 in Section 31 is implemented The results areobtained in the systems with 119899
119879= 4 119899
119863= 2 119899
119877= 2 119870= 128
and are averaged over 103 channel realizations Details aboutother simulation parameters are described in Section 6 Thenumerical results confirm that 119879
1gt 0 and 119879
2lt 0 Moreover
as shown in Figure 4(c) Δ119868 is always positive when the peak-power reduction algorithm is implemented (ie 119882= 4 and119882 = 8) For the case of 119882 = 1 the probability of ΔI beingpositive is significant Therefore the proposed system attainsa better ergodic capacity than that in the conventional systemThe achieved capacities in the considered systems will beprovided in Section 6
52 Energy Efficiency In this subsection we further exam-ine the efficacy of the proposed system from an energy-efficiency (EE) perspective Normalized energy efficiency(bitsHzJoule) in MIMO-OFDM systems can be defined as[3 26]
120578EE
=119862 (120588)
119875total (40)
where 119862(120588) is the achievable rate and the total powerconsumption per-subchannel is 119875total = 119899
119879119875dc + 119899
119879119875RF + 119875sp
where 119875RF is the RF power consumption in each transmitbranch excluding the associatedHPA and119875sp is the basebandprocessing power consumption It can be seen from (40)that given a fixed value of 119875total a comparison of energyefficiency achieved in the two systems is based on the capacitycomparison that has been analyzed in Section 51We are nowinterested in evaluating a useful metric of energy efficiency-spectral efficiency performance Recall that the average SNR120588 is given as 120588 = 119875
1199051205902119899= 120578
PE119899119879119875dc1205902
119899 Thus we can rewrite
the energy efficiency in (40) as a function of 119875dc as
120578EE
(119875dc) =119862 (120578
PE119899119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
(41)
Table 2 Simulation parameters
Parameter ValueBandwidth 528MHzFFT size 128Number of samples in zero-padded suffix 37Modulation scheme 4-QAMIEEE 802153a channel model CM1
The energy efficiency of the proposed and conventionalsystems can now be respectively expressed as
120578EEproposed (119875dc) =
119862proposed (120578PEproposed 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEproposed 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(42)
120578EEimbalance (119875dc) =
119862imbalance (120578PEimbalance 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEimbalance 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(43)
Similarly to the case of capacity we compare the energyefficiency achieved in the two systems by means of numericalresults in the next section Note that the calculation of energyefficiency in the proposed system (ie (42)) has assumed thata reduction in spectral efficiency due to the side informationas well as additional processing power required for the peak-power reduction algorithm is negligible In fact a reductionin spectral efficiency is very small For example in a systemwith 16-QAM FFT size of 128 119899
119863= 2 and 119882= 4 (ie 2 bits
are needed for side information) a spectral efficiency lossis 2 bits(128 times 4 times 2 + 2) bits = 019 Also it was shownin [27] that the additional power cost when implementingSLM schemes is minuscule Thus the proposed peak-powerreduction algorithm in Section 32 which is a SLM-basedscheme requires a small additional power cost
6 Numerical Results
In this section we provide numerical results to validatethe analyses mentioned in the previous sections as wellas demonstrate the effectiveness of the proposed allocationscheme over its counterpart A MIMO-OFDM system with119899119879= 4 119899
119863= 2 and 119899
119877= 2 is considered in our simulations
The system parameters are listed in Table 2These parametersare chosen based on the legacy WiMedia MB-OFDM UWB(Multiband-OFDM UWB) standard [28] Also the channelCM1 defined in the IEEE 802153a channel model [29] isbased on ameasurement of a line-of-sight scenario where thedistance between the transmitter and the receiver is up to 4mMoreover the multipath gains are modeled as independentlog normally distributed random variables We assume thatperfect channel state information is available at the receiverAlso the feedback link has no delay and is error-free
10 International Journal of Antennas and Propagation
Empirical CCDF of T110
0
10minus1
10minus2
minus2 0 2
W = 1
W = 4
W = 8
(a)
100
10minus1
10minus2
minus04 minus02 0
Empirical CDF of T2
(b)
Empirical CCDF of (T1 + T2)10
0
10minus1
10minus2
minus1 minus05 0 05 1 15 2
W = 1
W = 4
W = 8
(c)
Figure 4 Statistical distributions (note 1198792is independent of119882)
61 Evaluations of Peak-Power Distribution In Figure 5 weplot the CCDFs of the peak power of time-domain signalsThe analytical curves are based on (16) (17) and (19) Mean-while the simulation curves are empirical CCDF values Thesimulation result confirms that a system with the proposedallocation scheme offers a better CCDF performance than itscounterpart As expected the occurrence of high peak poweris significantly reduced when the peak-power reductionalgorithm is implemented Also it can be seen that theimprovement associated with this algorithm is reduced withincreasing 119882 In other words a very large value of 119882 whilerequiring higher complexity in terms on the number of IFFToperations results in a marginal improvement Thus it isreasonable to choose a relatively small value for 119882 (eg119882 = 4) It is also worth noting that the analytical curvesare relatively close to the simulation curves The small gapsexist due to the fact that the assumption of independentsamples |119904
119894(119899)| to obtain (13) does not strictly hold as we have
sum119870minus1
119899=0|119904119894(119899)|2 = 1205902119870
119894by Parsevalrsquos relation [24]
62 Evaluations of Power Efficiency of HPAs Figure 6 com-pares the CCDFs of the power efficiency achieved in theproposed and conventional systems It can be seen that theprobability of power efficiency being large highly likely occursin the proposed system compared to its counterpart Also
the simulation results agree well with the analytical resultsderived in (23) and (29) In Table 3 we compare the averagepower efficiencies Here the analytical values are obtainedaccording to (26) (27) and (30) Meanwhile the simulationvalues are empirical values based on the original definitionof the drain efficiency in (21) Also these values are averagedover the fading channel realizations It can be seen that thederived expressions approximate well the achieved powerefficiencies Table 3 also provides relative improvements ofthe power efficiencies achieved in the proposed system overthe conventional system Here only 120578
PE (Simulation) valuesare used for calculating these improvements It is clear thatthe proposed system could achieve a significant improvementin terms of average power efficiency
63 Evaluations of Capacity and Energy Efficiency Figure 7shows the system capacity inMbps (ie the normalized valuein (6) is scaled upwith the system bandwidth) versus the SNRvalue of 12059021205902
119899 It is clear that a systemwith the proposed allo-
cation scheme achieves a higher capacity than its counterpartThis agrees with the analysis in Section 51 that the changein capacity Δ119862 is positive In Figure 8 we plot the energyefficiency (MbitsJoule) versus spectral efficiency (MbpsHz)This figure is obtained based on (42) and (43) when varying119875dc Other parameters are 119875RF = 100mW 119875sp = 10mW and
International Journal of Antennas and Propagation 11
Table 3 A comparison of average power efficiencies
Imbalance Proposed (119882 = 1) Proposed (119882 = 4) Proposed (119882 = 8)120578PE (Simulation) 00697 00768 00894 00942
120578PE (Analysis) 00691 00757 00892 00943
Improvement120578PEproposed minus 120578
PEimbalance
120578PEimbalance
mdash 1019 2826 3515
1 2 3 4 5 6 7 8 9
100
10minus1
10minus2
10minus3
Peak power P0
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Pr (P
gtP0)
Figure 5 Comparison of CCDFs of the peak powers
002 004 006 008 01 012 014Power efficiency
CCD
F
100
10minus1
10minus2
10minus3
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Figure 6 Comparison of CCDFs of the power efficiencies
4500
4000
3500
3000
2500
2000
1500
1000
Ergo
dic c
apac
ity (M
bps)
2 4 6 8 10 12 14
SNR (dB)
3300
3200
3100
3000
2900
2800
97 98 99 10 101
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 7 Comparison of the ergodic capacities
12059021205902119899= 15 dB As expected the improvement in the power
efficiency of HPAs results in an improved energy efficiencyIn addition it can be observed that there exists an energyefficiency-spectral efficiency tradeoff in the systems Thistradeoff clearly needs to be taken into consideration whendesigning energy-efficient per-subcarrier antenna selectionbased OFDM wireless systems
7 Conclusions
In this paper a per-subcarrier antenna subset selectionMIMO-OFDM system with linear scaling has been investi-gated from an energy-efficiency perspective We have shownthat an imbalance allocation of data subcarriers associatedwith the conventional selection scheme affects the power effi-ciency of HPAs as well as the energy-efficiency of the wholesystem To deliver the maximum overall power efficiencywe have proposed the two-step strategy consisting of equalallocation data subcarriers across antennas and peak-powerreduction It has been proved from the power-efficiency view-point that the proposed allocation scheme outperforms theconventional scheme We have also derived the expressionsfor measuring the average power efficiency Moreover theimprovements in terms of capacity and energy efficiency
12 International Journal of Antennas and Propagation
0 2 4 6 8 10400
600
800
1000
1200
1400
1600
Spectral efficiency (MbpsHz)
Ener
gy effi
cien
cy (M
bits
J)
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 8 Energy efficiency versus spectral efficiency
resulting from the improved power efficiency have beenanalyzed The analytical results are validated by simulationresults The simulation result also shows that the systemwith the proposed allocation scheme could achieve a betterefficiency efficiency-spectral energy tradeoff compared to itscounterpart
Appendices
A Proof of Theorem 1
Let us consider a function 119891(120592) = 1 minus 119890minus1198750120592 0 lt 120592 le 1205902maxwhere 1205902max = max1205902
1198701 12059021198702
1205902119870119899119879
The second derivativeof this function is
11989110158401015840(120592) =
21198750120592 minus 11987520
1205924119890minus1198750120592 (A1)
From a HPAsrsquo viewpoint it is of interest to consider thesituation when the peak power across antennas 119875
0is large
Thus we consider the scenarios of 1198750
gt 21205902max where 1205902maxis the maximum average power across antennas Under thesesituations it is clear that 11989110158401015840(120592) lt 0 forall120592 isin (0 1205902max] Hencethe function 119891(120592) is concave By applying Jensenrsquos inequalitywe obtain the following inequality
1
119899119879
119899119879
sum119894=1
119891 (1205902
119870119894) le 119891(
1
119899119879
119899119879
sum119894=1
1205902
119870119894)
= 119891(1
119899119879
119899119879
sum119894=1
1205902
119870) = 119891 (120590
2
119870)
(A2)
where the equality comes from the fact that sum119899119879
119894=11205902119870119894
=
sum119899119879
119894=11205902119870
= 1198991198631205902 Expression (A2) can be rewritten as119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le 119899119879(1 minus 119890
minus11987501205902
119870) (A3)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879
On the other hand by applying the arithmetic-geometricmean inequality and note that (1 minus 119890
minus119909) gt 0 forall119909 gt 0 we have
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1
119899119879
119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ))
119899119879
(A4)
Note that the equality in (A4) holds if and only if 1205902119870119894
= 1205902119870
forall119894 = 1 119899119879
Combining (A3) and (A4) results in
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1 minus 119890minus1198750120590
2
119870)119899119879
(A5)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879 Thus we
get the following desired inequality
1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
ge 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(A6)
or
CCDF119875imbalance (1198750) ge CCDF119875balance (1198750) (A7)
This completes the proof
B Upper Bound of an ExpectedValue of Cost Penalty
In this appendix we derive an upper bound of the expectedvalue of Δ
119896 It can be seen from (5) that among all pos-
sible matrices H119896 the matrix H
119896with the highest value of
log2(det(Ω
119896))Ω119896
= Ω(H119896) will be selected as the effective
channel matrix for the 119896th subcarrier in the conventionalscheme Meanwhile in the proposed scheme due to thebalance constraint the effective channel matrix associatedwith the kth subcarrier is not necessarily the one with thehighest log
2(det(Ω
119896)) that is log
2(det(Ω
119896)) le log
2(det(Ω
119896))
Thus the expected value of Δ119896can be computed by using
order statistics In particular an upper bound on the expecteddifference of two-order statistics the Γth and 120574th 1 le 120574 lt Γis given by [30]
119864 Δ119896 = 119864 log
2(det (Ω
119896)) minus 119864 log
2(det (Ω
119896))
le 120590119862radic
Γ (120574 + 1)
120574
(B1)
where 1205902119862is the variance of log
2(det(Ω
119896)) that is assumed to
be the same for all possible matricesH119896
On the other hand suppose that the entries of the 119899119877times119899119879
matrixH119896are iid complex Gaussian random variables with
zero mean and unit variance then for any effective channelmatrix H
119896 Ω119896is a complex Wishart matrix It follows from
[25] that the variance of log2(det(Ω
119896)) can be expressed as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1205951015840(119902 minus 119898 + 1) (B2)
International Journal of Antennas and Propagation 13
where 119901 = min(119899119863 119899119877) 119902 = max(119899
119863 119899119877) and 1205951015840(119909) =
suminfin
120593=11(120593 + 119909 minus 1)
2 is the first derivative of the digammafunction By approximating 1205951015840(119909) asymp 1119909 [25] the simplerexpression for 1205902
119862in (B2) is given as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1
119902 minus 119898 + 1 (B3)
Substitute (B3) into (B1) we finally arrive at
119864 Δ119896 le log
2(119890)radic(
119901
sum119898=1
1
119902 minus 119898 + 1) times
Γ (120574 + 1)
120574 (B4)
Conflict of Interests
The authors declare that there is no conflict of interestsregarding the publication of this paper
References
[1] L M Correia D Zeller O Blume et al ldquoChallenges andenabling technologies for energy aware mobile radio networksrdquoIEEECommunicationsMagazine vol 48 no 11 pp 66ndash72 2010
[2] Z Hasan H Boostanimehr and V K Bhargava ldquoGreen cellularnetworks a survey some research issues and challengesrdquo IEEECommunications Surveys and Tutorials vol 13 no 4 pp 524ndash540 2011
[3] J Joung C K Ho and S Sun ldquoGreenwireless communicationsa power amplifier perspectiverdquo in Proceedings of the 4th Asia-Pacific Signal and Information Processing Association AnnualSummit and Conference (APSIPA ASC rsquo12) pp 1ndash8 December2012
[4] G L Stuber J R Barry S W Mclaughlin Y E Li M AIngram and T G Pratt ldquoBroadband MIMO-OFDM wirelesscommunicationsrdquoProceedings of the IEEE vol 92 no 2 pp 271ndash294 2004
[5] H Bolcskei D Gesbert and A J Paulraj ldquoOn the capacity ofOFDM-based spatial multiplexing systemsrdquo IEEE Transactionson Communications vol 50 no 2 pp 225ndash234 2002
[6] V Tarokh N Seshadri and A R Calderbank ldquoSpace-timecodes for high data rate wireless communication performancecriterion and code constructionrdquo IEEE Transactions on Infor-mation Theory vol 44 no 2 pp 744ndash765 1998
[7] C M Vithanage M Sandell J P Coon and Y Wang ldquoPrecod-ing in OFDM-based multi-antenna ultra-wideband systemsrdquoIEEE Communications Magazine vol 47 no 1 pp 41ndash47 2009
[8] Z Tang H Suzuki and I B Collings ldquoPerformance of antennaselection forMIMO-OFDMsystems based onmeasured indoorcorrelated frequency selective channelsrdquo in Proceedings of theAustralian Telecommunication Networks and Applications Con-ference pp 435ndash439 December 2006
[9] H Zhang and R U Nabar ldquoTransmit antenna selection inMIMO-OFDM systems bulk versus per-tone selectionrdquo inProceedings of the IEEE International Conference on Communi-cations (ICC rsquo08) pp 4371ndash4375 May 2008
[10] H Shi M Katayama T Yamazato H Okada and A OgawaldquoAn adaptive antenna selection scheme for transmit diversityin OFDM systemsrdquo in Proceedings of the IEEE 54th VehicularTechnology Conference (VTC rsquo01) pp 2168ndash2172 October 2001
[11] M Sandell and J P Coon ldquoPer-subcarrier antenna selectionwith power constraints in OFDM systemsrdquo IEEE Transactionson Wireless Communications vol 8 no 2 pp 673ndash677 2009
[12] N P Le F Safaei and L C Tran ldquoTransmit antenna subsetselection for high-rate MIMO-OFDM systems in the presenceof nonlinear power amplifiersrdquo EURASIP Journal on WirelessCommunications and Networking vol 2014 article 27 2014
[13] R PrasadOFDM for Wireless Communications Systems ArtechHouse 1st edition 2004
[14] T Jiang and Y Wu ldquoAn overview peak-to-average power ratioreduction techniques for OFDM signalsrdquo IEEE Transactions onBroadcasting vol 54 no 2 pp 257ndash268 2008
[15] H Ochiai ldquoPerformance analysis of peak power and band-limited OFDM system with linear scalingrdquo IEEE Transactionson Wireless Communications vol 2 no 5 pp 1055ndash1065 2003
[16] C Zhao R J Baxley and G T Zhou ldquoPeak-to-average powerratio and power efficiency considerations in MIMO-OFDMsystemsrdquo IEEE Communications Letters vol 12 no 4 pp 268ndash270 2008
[17] D Wulich and I Gutman ldquoImpact of linear power amplifier onpower loading in OFDM part I principlesrdquo in Proceedings ofthe IEEE 26th Convention of Electrical and Electronics Engineersin Israel (IEEEI rsquo10) pp 360ndash364 November 2010
[18] S Coleri M Ergen A Puri and A Bahai ldquoChannel estimationtechniques based on pilot arrangement in OFDM systemsrdquoIEEE Transactions on Broadcasting vol 48 no 3 pp 223ndash2292002
[19] R W Heath S Sandhu and A Paulraj ldquoAntenna selectionfor spatial multiplexing systems with linear receiversrdquo IEEECommunications Letters vol 5 no 4 pp 142ndash144 2001
[20] R Fletcher Practical Methods of Optimization John Willey ampSons 2nd edition 1987
[21] R W Bauml R F H Fischer and J B Huber ldquoReducingthe peak-to-average power ratio of multicarrier modulation byselected mappingrdquo Electronics Letters vol 32 no 22 pp 2056ndash2057 1996
[22] M Tan Z Latinovic and Y Bar-Ness ldquoSTBC MIMO-OFDMpeak-to-average power ratio reduction by cross-antenna rota-tion and inversionrdquo IEEE Communications Letters vol 9 no 7pp 592ndash594 2005
[23] K M Anstreicher ldquoLinear programming in O(n3lnnL) opera-tionsrdquo SIAM Journal on Optimization vol 9 no 4 pp 803ndash8121999
[24] J G Proakis Digital Communications McGraw Hill 4th edi-tion 2001
[25] O Oyman R U Nabar H Bolcskei and A J Paulraj ldquoChar-acterizing the statistical properties of mutual information inMIMO channelsrdquo IEEE Transactions on Signal Processing vol51 no 11 pp 2784ndash2795 2003
[26] S Cui A J Goldsmith and A Bahai ldquoEnergy-constrainedmodulation optimizationrdquo IEEE Transactions onWireless Com-munications vol 4 no 5 pp 2349ndash2360 2005
[27] R J Baxley and G T Zhou ldquoPower savings analysis of peak-to-average power ratio reduction in OFDMrdquo IEEE Transactions onConsumer Electronics vol 50 no 3 pp 792ndash797 2004
[28] A Batra et al Multiband OFDM Physical Layer SpecificationRelease 1 5 WiMedia Alliance 2009
[29] J Foerster et al ldquoChannel modeling sub-committee reportfinalrdquo IEEE P802 15-02490r1-SG3a 2003
[30] B C Arnold and R A Groeneveld ldquoBounds on expectationsof linear systematic statistics based on dependent samplesrdquoTheAnnals of Statistics vol 7 no 1 pp 220ndash223 1979
International Journal of
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Submit your manuscripts athttpwwwhindawicom
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Shock and Vibration
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Electrical and Computer Engineering
Journal of
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Modelling amp Simulation in EngineeringHindawi Publishing Corporation httpwwwhindawicom Volume 2014
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Chemical EngineeringInternational Journal of Antennas and
Propagation
International Journal of
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Navigation and Observation
International Journal of
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DistributedSensor Networks
International Journal of
International Journal of Antennas and Propagation 5
Antennas
Subcarriers
Tx 1
Tx 2
Tx 3
Tx 4
Data
Not used
(a) Unbalanced-power selection
Data
Not used
Antennas
Subcarriers
Tx 1
Tx 2
Tx 3
Tx 4
(b) Balanced-power selection
Figure 2 Illustration of per-subcarrier antenna subset selection (119899119879= 4 119899
119863= 2 and 119870 = 12)
Ant
enna
s
Subcarriers
1st candidate(original)
x11 x
21
x12
x32
x33 x
43
x24 x
44
0 0
0
00
0 0
0
(a)
2nd candidate (permutedata on the 1st antenna)
Subcarriers
x12 x
24 0 0
00
00
0 0
x11 x
32
x33 x
43
x44
x21
(b)
3rd candidate (permutedata on the 2nd antenna)
Subcarriers
Ant
enna
s
x12
x21 0 0
00
00
0 0
x11 x
33
x32 x
43
x44
x24
(c)
4th candidate (permutedata on the 3rd antenna)
Subcarriers
0 0
00
00
0 0
x11 x
21
x12 x
33
x32 x
44
x43x
24
(d)
Figure 3 Illustration of cross-antenna permutations (119899119879= 4 119899
119863= 2 and 119870 = 4)
receiver as in [22] The proposed algorithm is described asfollows
(1) Create 119882 candidates by performing cross-antennaspermutations An illustration of this process in thesystem with 119899
119863= 2 119899
119879= 4 and 119870 = 4 is
shown in Figure 3 Accordingly the first candidateis the original data allocation The second candidateis obtained by permuting all symbols on the firstantennas with their associated symbols on the otherantennasThe third and fourth candidates are createdin a similar manner To obtain a larger number ofcandidates all symbols on the antenna that are goingbe permutated need first have their phase rotated (iebeing multiplied with an element of a phase set ega 4-phase set is 0 1205872 120587 31205872)
(2) Calculate the peak powers of all available candidates(3) Select the candidate with the minimum peak power
for transmission
To recover the transmitted data the transmitter needs toinform the receiver which candidates have been selectedThus the number of side information bits in this scheme islog2119882 which is similar to that in [22]
33 Complexity Considerations In this subsection the com-plexity of the proposed allocation scheme is compared tothat of the conventional (imbalance) allocation scheme Inthe first step of the proposed scheme to realize an equalallocation of data subcarriers the optimization problem in (8)
needs to be solved at the receiverWenote that this linear opti-mization problem can be solved in polynomial time Morespecifically the complexity to solve this problem using inte-rior point methods can be reduced to 119874([(119870Γ)
3 ln(119870Γ)]120585)
where119874(sdot) denotes an order of complexity and 120585 is the bit sizeof the optimization problem [23] In addition it is noted thatthis step is transparent to the transmitter (ie no additionalcomplexity is required at the transmitter) In the secondstep a major additional complexity lies in the required IFFToperations due to additional 119882 candidates As an 119870 point-IFFT requires 119870log
2119870 complex additions and (1198702)log
2119870
complex multiplications the numbers of complex additionsand complex multiplications in the conventional scheme are119899119879119870log2119870 and 119899
119879(1198702)log
2119870 respectivelyMeanwhile in the
proposed scheme with 119882 candidates 119882119899119879119870log2119870 complex
additions and 119882119899119879(1198702)log
2119870 complex multiplications are
required However as we will show analytically in Section 4and numerically in Section 6 an improvement in the peak-power reduction reduces when 119882 becomes large Thus asmall value of 119882 is generally chosen which does not incurmuch additional complexity Finally the amount of feedbackinformation in the proposed scheme is similar to that in theconventional scheme
4 Analysis of Power Efficiency
41 Statistical Distribution of Peak Power Before proceedingto analyze the power efficiency of HPAs we need to investi-gate the distribution of the peak power of the MIMO-OFDMsignals (ie the peak power across transmit antennas) We
6 International Journal of Antennas and Propagation
consider the complementary cumulative distribution func-tion (CCDF) of the peak power defined as the probability thatthe peak power 119875 exceeds a given threshold 119875
0 that is
CCDF119875 (1198750) = Pr (119875 gt 119875
0) (9)
Note that although a procedure for calculating CCDF ofPAPR in OFDM systems is known to the best of ourknowledge all the CCDF expressions with respect toMIMO-OFDM signals available in the literature assume that all datasubcarriers are active which can be considered as a specialcase in the considered system when all the transmit antennashave the same number of allocated data symbols In thefollowing we calculate the CCDF of the peak power in oursystem
Let us begin with the discrete-time OFDM signal 119904119894(119899)
119899 = 0 1 119870minus1 corresponding to the 119894th transmit antennaThe peak power of this signal is defined as
119875119894= max0le119899le119870minus1
|119904119894 (119899) |2 (10)
For analytical tractability we assume that both the real partand imaginary part of the signal 119904
119894(119899) are asymptotically
independent and identically distributed Gaussian randomvariables Note that this assumption which is based on thecentral limit theorem [24] only holds when the number ofassigned data subcarriers on the 119894th antenna denoted as119870119894 is large enough As a result |119904
119894(119899)| follows the Rayleigh
distribution and |119904119894(119899)|2 has a chi-square distribution with
two degrees of freedom The probability density function ofthe signal |119904
119894(119899)|2 can be expressed as [24]
119901|119904|2 (
100381610038161003816100381611990411989410038161003816100381610038162) =
1
1205902119870119894
119890minus|119904119894|21205902
119870119894 (11)
where 1205902119870119894
= 1205902119870119894119870 is the variance of the signal |119904
119894(119899)| Note
that sum119899119879
119894=1119870119894
= 119899119863119870 thus we have sum
119899119879
119894=11205902119870119894
= 1198991198631205902 The
CDF (cumulative distribution function) of the signal |119904119894(119899)|2
is given as
Pr (100381610038161003816100381611990411989410038161003816100381610038162le 120579) = 1 minus 119890
minus1205791205902
119870119894 120579 ge 0 (12)
Suppose that 119870 samples of |119904119894(119899)| 119899 = 0 1 119870 minus 1 are
independent the CDF of the peak power 119875119894can be expressed
as
CDF119875119894 = Pr (119875119894le 1198750)
= Pr (1003816100381610038161003816119904119894 (0)10038161003816100381610038162le 1198750)Pr (1003816100381610038161003816119904119894 (1)
10038161003816100381610038162le 1198750) sdot sdot sdot
Pr (1003816100381610038161003816119904119894 (119870 minus 1)10038161003816100381610038162le 1198750)
= (1 minus 119890minus1198750120590
2
119870119894 )119870
(13)
In MIMO-OFDM systems with linear scaling the peakpower across transmit antennas 119875 can be defined as
119875 = max1le119894le119899119879
119875119894 (14)
Given the statistical independence of data among transmitantennas which is the case in the considered spatial mul-tiplexed OFDM system the CDF of the peak power 119875 iscalculated as
CDF119875 = Pr (119875 le 1198750)
= Pr (1198751le 1198750)Pr (119875
2le 1198750) sdot sdot sdotPr (119875
119899119879le 1198750)
=
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
(15)
Therefore the CCDF of the peak power of the antennaselection MIMO-OFDM signals can be expressed as
CCDF119875imbalance (1198750) = 1 minus CDF119875
= 1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
(16)
In the MIMO-OFDM system with a power balancingconstraint the number of allocated data subcarriers pertransmit antenna is equal to one another (ie 119870
119894=
119899119863119870119899119879
= 119870 forall119894 = 1 2 119899119879) Thus the variances of the
signals are 1205902119870119894
= 1198991198631205902119899119879= 1205902119870 forall119894 = 1 2 119899
119879 As a result
the CCDF expression could be simplified to as
CCDF119875balance (1198750) = 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(17)
A comparison of the CCDF of the peak powers in the twosystems is presented in the following theorem
Theorem 1 In MIMO-OFDM transmission schemes that con-sist of inactive data subcarriers (eg per-subcarrier antennaselection) the probability of occurrences of high peak power isthe smallest when the same number of data symbols is allocatedto all transmit antennas that is
CCDF119875balance (1198750) le CCDF119875imbalance (1198750) (18)
Proof The proof is given in Appendix AWhen the peak-power reduction algorithm proposed in
Section 32 is implemented in theMIMO-OFDMsystemwitha power-balancing constraint the CCDF of the peak powercan be expressed as
CCDF119875balance+reduced (1198750) = (CCDF119875balance (1198750))119882
= (1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870)119882
(19)
where 119882 is the number of candidates that are assumed tobe independent Recall that by definition the CCDF value isalways smaller than one (cf (9)) Therefore the CCDF valuein (19) is smaller than that in (17) that is
CCDF119875balance+reduced (1198750) le CCDF119875balance (1198750) (20)
International Journal of Antennas and Propagation 7
42 Power Efficiency of HPAs We now analyze the powerefficiency (PE) of high-power amplifiers (HPAs) The drainefficiency of HPAs which is defined as a ratio between thepower drawn from the DC source 119875dc and the average outputpower 119875out is considered in this paper Denote 119875119894in and 119875119894out tobe the average input and output powers of the HPA for the119894th antenna respectively Recall that all HPAs are assumedto have a unity gain that is 119875119894out = 119875119894in forall119894 = 1 2 119899
119879
Hence the instantaneous overall power efficiency of HPAs inthe MIMO-OFDM system can be expressed as [16]
120578PE
=sum119899119879
119894=1119875119894out
119899119879119875dc
=sum119899119879
119894=1119875119894in
119899119879119875dc
= 1205721198991198631205902
119899119879119875dc
=1198991198631205902119875sat
119899119879119875dc
1
119875=
1198991198631205902
2119899119879
1
119875
(21)
In the above manipulations we have used the fact thatsum119899119879
119894=1119875119894in = 120572119899
1198631205902 and119875dc = 2119875sat for class-AHPAs regardless
of the average powers of the input time-domain signalsDenoting CCDFPE (120578PE
0) = Pr(120578PE gt 120578PE
0) to be the CCDF
of the power efficiency we obtain the following result withrespect to 120578
PE
Theorem 2 In per-subcarrier antenna selection MIMO-OFDM systems with linear scaling the probability of achievinghigh instantaneous overall power efficiency of HPAs is thelargest when all transmit antennas have the same number ofallocated data symbols that is
CCDFPEbalance (120578PE0) ge CCDFPEimbalance (120578
PE0) (22)
where
CCDFPEbalance (120578PE0) = (1 minus 119890
minus12120578PE0 )119899119879119870
CCDFPEimbalance (120578PE0) =
119899119879
prod119894=1
(1 minus 119890minus1198991198631198702119899119879119870119894120578
PE0 )119870
(23)
Proof From (18) and (21) it is readily to obtain (22) and (23)With respect to the average value of the overall power
efficiency from (21) we can express
120578PE
= 119864 120578PE =
1198991198631205902
2119899119879
1198641
119875 =
1198991198631205902
2119899119879
int1
119909119901 (119909) 119889119909 (24)
where 119901(119909) is the pdf (probability distribution function) ofthe peak power In the system with a balance constraint (ieonly use Step 1) the pdf of the peak power can be calculatedas
119901balance (119909) =119889
119889119909CDF119875balance (119909) =
119889
119889119909(1 minus 119890
minus1199091205902
119870)119899119879119870
=119899119879119870
1205902119870
119890minus1199091205902
119870(1 minus 119890minus1199091205902
119870)119899119879119870minus1
(25)
Hence
120578PEbalance =
1198991198631205902
2119899119879
int1
119909119901balance (119909) 119889119909
=119899119879119870
2int1198701205902
119870
1205902
119870
1
119909119890minus1199091205902
119870(1 minus 119890minus1199091205902
119870)119899119879119870minus1
119889119909
=119899119879119870
2int119870
1
1
119909119890minus119909
(1 minus 119890minus119909
)119899119879119870minus1
119889119909
(26)
Similarly the power efficiency of HPAs in the conventionalsystem is
120578PEimbalance =
1198991198631205902
2119899119879
int1
119909119901imbalance (119909) 119889119909
=1198991198631198701205902
2119899119879
int119870max120590
2
max
1205902
max
1
119909
119899119879
sum119895=1
119890minus1199091205902
119870119895
(1 minus 119890minus1199091205902
119870119895 ) 1205902119870119895
times
119899119879
prod119894=1
(1 minus 119890minus1199091205902
119870119894 )119870
119889119909
(27)
where 1205902max = max12059021198701
1205902119870119899119879
and 119870max = max1198701
119870119899119879When the peak-power reduction algorithm is also imple-
mented (ie the system employs both Steps 1 and 2) it isreadily from (20) and (21) that
CCDFPEbalance+reduced (120578PE0
) ge CCDFPEbalance (120578PE0
) (28)
where
CCDFPEbalance+reduced (120578PE0
) = 1 minus (1 minus (1 minus 119890minus12120578
PE0 )119899119879119870
)119882
(29)
Also the average power efficiency can now be calculated as
120578PEbalance+reduced =
1198991198631205902
2119899119879
int1
119909119901balance+reduced (119909) 119889119909
=119899119879119870119882
2int119870
1
1
119909119890minus119909
(1 minus 119890minus119909
)119899119879119870minus1
times (1 minus (1 minus 119890minus119909
)119899119879119870
)119882minus1
119889119909
(30)
It can be seen from (30) that the smaller the peak poweris reduced (ie the larger the number of candidates 119882 isused) the higher the power efficiency could be achievedNote that although the integrals in (26) (27) and (30) haveno closed-form solutions they can be evaluated numericallyAlso the average power efficiencies in (26) (27) and (30) aretaken with respect to the input data In other words they areconsidered as instantaneous power efficiencieswith respect tothe channel distribution Consequently the power efficiencyin the systems is obtained by averaging these values over thefading channel distribution
8 International Journal of Antennas and Propagation
5 Analyses of Capacity and Energy Efficiency
It has been shown in (22) and (28) that the proposed systemcould achieve a better power efficiency of HPAs than itscounterpart Thus when the power 119875dc is fixed it is intuitivethat an increased average power efficiency results in anincreased average transmit power and in turn leads to anincrease in the achievable rate Moreover an increase in thedata rate under a constant consumption power will translateinto an improvement in energy efficiency The achievedcapacity and energy efficiency are now investigated in thissection
51 System Capacity We begin by rewriting the mutualinformation in (7) with respect to the average SNR valueof 120588 = 119875
1199051205902119899 where 119875
119905= 120572119899
1198631205902 = 120578
PE119899119879119875dc (cf (21))
The ergodic capacity is then calculated by averaging themutual information over the fading channel distributionthat is 119862(120588) = 119864H119868(120588H) From (6) and (7) the mutualinformation in the proposed and conventional systems canbe expressed respectively as
119868 (120588proposedH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
(31)
119868 (120588imbalanceH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(32)
where 120588proposed = 120578PEproposed119899119879119875dc120590
2
119899and 120588imbalance =
120578PEimbalance119899119879119875dc120590
2
119899 Here 120578
PEproposed = 120578
PEbalance+reduced if the
peak-power reduction algorithm is implemented otherwise120578PEproposed = 120578
PEbalance Also H119896 in (31) denotes the effective
channel matrix on the 119896th subcarrier in the proposed systemwhich is obtainedwhen solving the problem in (8)This chan-nel matrix is generally different from the effective channelmatrix H
119896in the conventional system because the selected
antenna subset may be differentThe difference in the mutualinformation between the two systems can be now calculatedas
Δ119868 = 119868 (120588proposedH) minus 119868 (120588imbalanceH) =1
119870
119870minus1
sum119896=0
Δ119868119896 (33)
where
Δ119868119896= log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
minus log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(34)
For analytical simplicity we focus on the high-SNRregime At the high SNR the mutual information at the 119896thsubcarrier can be approximated as [25]
119868119896= log2(det(
120588
119899119863
Ω119896)) (35)
where
Ω119896= Ω (H
119896) =
H119896H119867119896 119899119877le 119899119863
H119867119896H119896 119899119877gt 119899119863
(36)
Thus the difference in the mutual information can berewritten as
Δ119868 =1
119870
119870minus1
sum119896=0
(log2(det(
120588proposed
119899119863
Ω119896))
minuslog2(det(
120588imbalance119899119863
Ω119896)))
= 119901log2
120578PEproposed
120578PEimbalance
minus1
119870
119870minus1
sum119896=0
Δ119896= 1198791+ 1198792
(37)
where 119901 = min(119899119863 119899119877)Ω119896= Ω(H
119896) and
Δ119896= log2(det (Ω
119896)) minus log
2(det (Ω
119896)) (38)
is the loss in the mutual information associated with the 119896thsubcarrier due to the constrained allocation Note that if bothsystems have the same selected antenna subset at the 119896thsubcarrier then Δ
119896= 0 otherwise Δ
119896gt 0Thus the total loss
in the mutual information Δ = (1119870)sum119870minus1
119896=0Δ119896gt 0
We have some important observations with respect to thevalue of Δ119868 in (37)
(i)The change in mutual information Δ119868 comes fromtwo sources The first source 119879
1is a benefit in mutual
information due to the improvement in the powerefficiency of HPAs The second source 119879
2is a penalty
that incurs because the chosen effective channelmatrices in the proposed system are different from theones in the conventional system(ii) For each channel realization thematrixH
119896is fixed
and the first term 1198791in (37) is a constant Thus the
value of Δ119868 depends on how the effective channelmatrix H
119896is selected in the constrained selection
scheme From this observation it is clear that tomake the value Δ119868 become as positive as possiblethe constrained selection method should result inthe cost penalty Δ as small as possible We note thatthe formulated optimization in (8) could achieve theminimum possible value of the total cost Hence it isexpected that the constrained selection scheme basedon linear optimization will guarantee the maximumachievable value of Δ119868 In addition to have an insightinto the cost penalty we derive the upper bound ofthe expected value of the cost penalty in Appendix BBased on the obtained bound it is observed that forfixed values of 119899
119879and 119899
119863 the cost penalty becomes
smaller with an increasing value of 119902 = max(119899119863 119899119877)
International Journal of Antennas and Propagation 9
(iii) As Δ gt 0 the upper bound of the capacityimprovement can be given as
Δ119862 = 119864H Δ119868 le 119901log2119864H
120578PEproposed
120578PEimbalance
(39)
In (39) we have used Jensenrsquos inequality of119864log(119909) le log(119864119909) as log(119909) is a concavefunction Based on this bound we could estimatethe maximum improvement in capacity that couldbe realized in the proposed system compared to itscounterpart
It is now necessary to evaluate the change in capacitythat is Δ119862 We note that although the distribution of themutual information at high SNRs can be well approximatedby a Gaussian distribution [25] it is still challenging toperform a mathematical evaluation of Δ119862 from a statisticalviewpoint This is mainly due to the fact that the two termsin (37) are complicated dependent random variables Thuswe perform a numerical evaluation of Δ119862 instead Figure 4plots the empirical CCDF of 119879
1 CDF of 119879
2 and CCDF
of Δ119868 In the figure ldquo119882 = 1rdquo stands for the case in whichonly Step 1 in Section 31 is implemented The results areobtained in the systems with 119899
119879= 4 119899
119863= 2 119899
119877= 2 119870= 128
and are averaged over 103 channel realizations Details aboutother simulation parameters are described in Section 6 Thenumerical results confirm that 119879
1gt 0 and 119879
2lt 0 Moreover
as shown in Figure 4(c) Δ119868 is always positive when the peak-power reduction algorithm is implemented (ie 119882= 4 and119882 = 8) For the case of 119882 = 1 the probability of ΔI beingpositive is significant Therefore the proposed system attainsa better ergodic capacity than that in the conventional systemThe achieved capacities in the considered systems will beprovided in Section 6
52 Energy Efficiency In this subsection we further exam-ine the efficacy of the proposed system from an energy-efficiency (EE) perspective Normalized energy efficiency(bitsHzJoule) in MIMO-OFDM systems can be defined as[3 26]
120578EE
=119862 (120588)
119875total (40)
where 119862(120588) is the achievable rate and the total powerconsumption per-subchannel is 119875total = 119899
119879119875dc + 119899
119879119875RF + 119875sp
where 119875RF is the RF power consumption in each transmitbranch excluding the associatedHPA and119875sp is the basebandprocessing power consumption It can be seen from (40)that given a fixed value of 119875total a comparison of energyefficiency achieved in the two systems is based on the capacitycomparison that has been analyzed in Section 51We are nowinterested in evaluating a useful metric of energy efficiency-spectral efficiency performance Recall that the average SNR120588 is given as 120588 = 119875
1199051205902119899= 120578
PE119899119879119875dc1205902
119899 Thus we can rewrite
the energy efficiency in (40) as a function of 119875dc as
120578EE
(119875dc) =119862 (120578
PE119899119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
(41)
Table 2 Simulation parameters
Parameter ValueBandwidth 528MHzFFT size 128Number of samples in zero-padded suffix 37Modulation scheme 4-QAMIEEE 802153a channel model CM1
The energy efficiency of the proposed and conventionalsystems can now be respectively expressed as
120578EEproposed (119875dc) =
119862proposed (120578PEproposed 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEproposed 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(42)
120578EEimbalance (119875dc) =
119862imbalance (120578PEimbalance 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEimbalance 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(43)
Similarly to the case of capacity we compare the energyefficiency achieved in the two systems by means of numericalresults in the next section Note that the calculation of energyefficiency in the proposed system (ie (42)) has assumed thata reduction in spectral efficiency due to the side informationas well as additional processing power required for the peak-power reduction algorithm is negligible In fact a reductionin spectral efficiency is very small For example in a systemwith 16-QAM FFT size of 128 119899
119863= 2 and 119882= 4 (ie 2 bits
are needed for side information) a spectral efficiency lossis 2 bits(128 times 4 times 2 + 2) bits = 019 Also it was shownin [27] that the additional power cost when implementingSLM schemes is minuscule Thus the proposed peak-powerreduction algorithm in Section 32 which is a SLM-basedscheme requires a small additional power cost
6 Numerical Results
In this section we provide numerical results to validatethe analyses mentioned in the previous sections as wellas demonstrate the effectiveness of the proposed allocationscheme over its counterpart A MIMO-OFDM system with119899119879= 4 119899
119863= 2 and 119899
119877= 2 is considered in our simulations
The system parameters are listed in Table 2These parametersare chosen based on the legacy WiMedia MB-OFDM UWB(Multiband-OFDM UWB) standard [28] Also the channelCM1 defined in the IEEE 802153a channel model [29] isbased on ameasurement of a line-of-sight scenario where thedistance between the transmitter and the receiver is up to 4mMoreover the multipath gains are modeled as independentlog normally distributed random variables We assume thatperfect channel state information is available at the receiverAlso the feedback link has no delay and is error-free
10 International Journal of Antennas and Propagation
Empirical CCDF of T110
0
10minus1
10minus2
minus2 0 2
W = 1
W = 4
W = 8
(a)
100
10minus1
10minus2
minus04 minus02 0
Empirical CDF of T2
(b)
Empirical CCDF of (T1 + T2)10
0
10minus1
10minus2
minus1 minus05 0 05 1 15 2
W = 1
W = 4
W = 8
(c)
Figure 4 Statistical distributions (note 1198792is independent of119882)
61 Evaluations of Peak-Power Distribution In Figure 5 weplot the CCDFs of the peak power of time-domain signalsThe analytical curves are based on (16) (17) and (19) Mean-while the simulation curves are empirical CCDF values Thesimulation result confirms that a system with the proposedallocation scheme offers a better CCDF performance than itscounterpart As expected the occurrence of high peak poweris significantly reduced when the peak-power reductionalgorithm is implemented Also it can be seen that theimprovement associated with this algorithm is reduced withincreasing 119882 In other words a very large value of 119882 whilerequiring higher complexity in terms on the number of IFFToperations results in a marginal improvement Thus it isreasonable to choose a relatively small value for 119882 (eg119882 = 4) It is also worth noting that the analytical curvesare relatively close to the simulation curves The small gapsexist due to the fact that the assumption of independentsamples |119904
119894(119899)| to obtain (13) does not strictly hold as we have
sum119870minus1
119899=0|119904119894(119899)|2 = 1205902119870
119894by Parsevalrsquos relation [24]
62 Evaluations of Power Efficiency of HPAs Figure 6 com-pares the CCDFs of the power efficiency achieved in theproposed and conventional systems It can be seen that theprobability of power efficiency being large highly likely occursin the proposed system compared to its counterpart Also
the simulation results agree well with the analytical resultsderived in (23) and (29) In Table 3 we compare the averagepower efficiencies Here the analytical values are obtainedaccording to (26) (27) and (30) Meanwhile the simulationvalues are empirical values based on the original definitionof the drain efficiency in (21) Also these values are averagedover the fading channel realizations It can be seen that thederived expressions approximate well the achieved powerefficiencies Table 3 also provides relative improvements ofthe power efficiencies achieved in the proposed system overthe conventional system Here only 120578
PE (Simulation) valuesare used for calculating these improvements It is clear thatthe proposed system could achieve a significant improvementin terms of average power efficiency
63 Evaluations of Capacity and Energy Efficiency Figure 7shows the system capacity inMbps (ie the normalized valuein (6) is scaled upwith the system bandwidth) versus the SNRvalue of 12059021205902
119899 It is clear that a systemwith the proposed allo-
cation scheme achieves a higher capacity than its counterpartThis agrees with the analysis in Section 51 that the changein capacity Δ119862 is positive In Figure 8 we plot the energyefficiency (MbitsJoule) versus spectral efficiency (MbpsHz)This figure is obtained based on (42) and (43) when varying119875dc Other parameters are 119875RF = 100mW 119875sp = 10mW and
International Journal of Antennas and Propagation 11
Table 3 A comparison of average power efficiencies
Imbalance Proposed (119882 = 1) Proposed (119882 = 4) Proposed (119882 = 8)120578PE (Simulation) 00697 00768 00894 00942
120578PE (Analysis) 00691 00757 00892 00943
Improvement120578PEproposed minus 120578
PEimbalance
120578PEimbalance
mdash 1019 2826 3515
1 2 3 4 5 6 7 8 9
100
10minus1
10minus2
10minus3
Peak power P0
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Pr (P
gtP0)
Figure 5 Comparison of CCDFs of the peak powers
002 004 006 008 01 012 014Power efficiency
CCD
F
100
10minus1
10minus2
10minus3
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Figure 6 Comparison of CCDFs of the power efficiencies
4500
4000
3500
3000
2500
2000
1500
1000
Ergo
dic c
apac
ity (M
bps)
2 4 6 8 10 12 14
SNR (dB)
3300
3200
3100
3000
2900
2800
97 98 99 10 101
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 7 Comparison of the ergodic capacities
12059021205902119899= 15 dB As expected the improvement in the power
efficiency of HPAs results in an improved energy efficiencyIn addition it can be observed that there exists an energyefficiency-spectral efficiency tradeoff in the systems Thistradeoff clearly needs to be taken into consideration whendesigning energy-efficient per-subcarrier antenna selectionbased OFDM wireless systems
7 Conclusions
In this paper a per-subcarrier antenna subset selectionMIMO-OFDM system with linear scaling has been investi-gated from an energy-efficiency perspective We have shownthat an imbalance allocation of data subcarriers associatedwith the conventional selection scheme affects the power effi-ciency of HPAs as well as the energy-efficiency of the wholesystem To deliver the maximum overall power efficiencywe have proposed the two-step strategy consisting of equalallocation data subcarriers across antennas and peak-powerreduction It has been proved from the power-efficiency view-point that the proposed allocation scheme outperforms theconventional scheme We have also derived the expressionsfor measuring the average power efficiency Moreover theimprovements in terms of capacity and energy efficiency
12 International Journal of Antennas and Propagation
0 2 4 6 8 10400
600
800
1000
1200
1400
1600
Spectral efficiency (MbpsHz)
Ener
gy effi
cien
cy (M
bits
J)
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 8 Energy efficiency versus spectral efficiency
resulting from the improved power efficiency have beenanalyzed The analytical results are validated by simulationresults The simulation result also shows that the systemwith the proposed allocation scheme could achieve a betterefficiency efficiency-spectral energy tradeoff compared to itscounterpart
Appendices
A Proof of Theorem 1
Let us consider a function 119891(120592) = 1 minus 119890minus1198750120592 0 lt 120592 le 1205902maxwhere 1205902max = max1205902
1198701 12059021198702
1205902119870119899119879
The second derivativeof this function is
11989110158401015840(120592) =
21198750120592 minus 11987520
1205924119890minus1198750120592 (A1)
From a HPAsrsquo viewpoint it is of interest to consider thesituation when the peak power across antennas 119875
0is large
Thus we consider the scenarios of 1198750
gt 21205902max where 1205902maxis the maximum average power across antennas Under thesesituations it is clear that 11989110158401015840(120592) lt 0 forall120592 isin (0 1205902max] Hencethe function 119891(120592) is concave By applying Jensenrsquos inequalitywe obtain the following inequality
1
119899119879
119899119879
sum119894=1
119891 (1205902
119870119894) le 119891(
1
119899119879
119899119879
sum119894=1
1205902
119870119894)
= 119891(1
119899119879
119899119879
sum119894=1
1205902
119870) = 119891 (120590
2
119870)
(A2)
where the equality comes from the fact that sum119899119879
119894=11205902119870119894
=
sum119899119879
119894=11205902119870
= 1198991198631205902 Expression (A2) can be rewritten as119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le 119899119879(1 minus 119890
minus11987501205902
119870) (A3)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879
On the other hand by applying the arithmetic-geometricmean inequality and note that (1 minus 119890
minus119909) gt 0 forall119909 gt 0 we have
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1
119899119879
119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ))
119899119879
(A4)
Note that the equality in (A4) holds if and only if 1205902119870119894
= 1205902119870
forall119894 = 1 119899119879
Combining (A3) and (A4) results in
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1 minus 119890minus1198750120590
2
119870)119899119879
(A5)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879 Thus we
get the following desired inequality
1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
ge 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(A6)
or
CCDF119875imbalance (1198750) ge CCDF119875balance (1198750) (A7)
This completes the proof
B Upper Bound of an ExpectedValue of Cost Penalty
In this appendix we derive an upper bound of the expectedvalue of Δ
119896 It can be seen from (5) that among all pos-
sible matrices H119896 the matrix H
119896with the highest value of
log2(det(Ω
119896))Ω119896
= Ω(H119896) will be selected as the effective
channel matrix for the 119896th subcarrier in the conventionalscheme Meanwhile in the proposed scheme due to thebalance constraint the effective channel matrix associatedwith the kth subcarrier is not necessarily the one with thehighest log
2(det(Ω
119896)) that is log
2(det(Ω
119896)) le log
2(det(Ω
119896))
Thus the expected value of Δ119896can be computed by using
order statistics In particular an upper bound on the expecteddifference of two-order statistics the Γth and 120574th 1 le 120574 lt Γis given by [30]
119864 Δ119896 = 119864 log
2(det (Ω
119896)) minus 119864 log
2(det (Ω
119896))
le 120590119862radic
Γ (120574 + 1)
120574
(B1)
where 1205902119862is the variance of log
2(det(Ω
119896)) that is assumed to
be the same for all possible matricesH119896
On the other hand suppose that the entries of the 119899119877times119899119879
matrixH119896are iid complex Gaussian random variables with
zero mean and unit variance then for any effective channelmatrix H
119896 Ω119896is a complex Wishart matrix It follows from
[25] that the variance of log2(det(Ω
119896)) can be expressed as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1205951015840(119902 minus 119898 + 1) (B2)
International Journal of Antennas and Propagation 13
where 119901 = min(119899119863 119899119877) 119902 = max(119899
119863 119899119877) and 1205951015840(119909) =
suminfin
120593=11(120593 + 119909 minus 1)
2 is the first derivative of the digammafunction By approximating 1205951015840(119909) asymp 1119909 [25] the simplerexpression for 1205902
119862in (B2) is given as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1
119902 minus 119898 + 1 (B3)
Substitute (B3) into (B1) we finally arrive at
119864 Δ119896 le log
2(119890)radic(
119901
sum119898=1
1
119902 minus 119898 + 1) times
Γ (120574 + 1)
120574 (B4)
Conflict of Interests
The authors declare that there is no conflict of interestsregarding the publication of this paper
References
[1] L M Correia D Zeller O Blume et al ldquoChallenges andenabling technologies for energy aware mobile radio networksrdquoIEEECommunicationsMagazine vol 48 no 11 pp 66ndash72 2010
[2] Z Hasan H Boostanimehr and V K Bhargava ldquoGreen cellularnetworks a survey some research issues and challengesrdquo IEEECommunications Surveys and Tutorials vol 13 no 4 pp 524ndash540 2011
[3] J Joung C K Ho and S Sun ldquoGreenwireless communicationsa power amplifier perspectiverdquo in Proceedings of the 4th Asia-Pacific Signal and Information Processing Association AnnualSummit and Conference (APSIPA ASC rsquo12) pp 1ndash8 December2012
[4] G L Stuber J R Barry S W Mclaughlin Y E Li M AIngram and T G Pratt ldquoBroadband MIMO-OFDM wirelesscommunicationsrdquoProceedings of the IEEE vol 92 no 2 pp 271ndash294 2004
[5] H Bolcskei D Gesbert and A J Paulraj ldquoOn the capacity ofOFDM-based spatial multiplexing systemsrdquo IEEE Transactionson Communications vol 50 no 2 pp 225ndash234 2002
[6] V Tarokh N Seshadri and A R Calderbank ldquoSpace-timecodes for high data rate wireless communication performancecriterion and code constructionrdquo IEEE Transactions on Infor-mation Theory vol 44 no 2 pp 744ndash765 1998
[7] C M Vithanage M Sandell J P Coon and Y Wang ldquoPrecod-ing in OFDM-based multi-antenna ultra-wideband systemsrdquoIEEE Communications Magazine vol 47 no 1 pp 41ndash47 2009
[8] Z Tang H Suzuki and I B Collings ldquoPerformance of antennaselection forMIMO-OFDMsystems based onmeasured indoorcorrelated frequency selective channelsrdquo in Proceedings of theAustralian Telecommunication Networks and Applications Con-ference pp 435ndash439 December 2006
[9] H Zhang and R U Nabar ldquoTransmit antenna selection inMIMO-OFDM systems bulk versus per-tone selectionrdquo inProceedings of the IEEE International Conference on Communi-cations (ICC rsquo08) pp 4371ndash4375 May 2008
[10] H Shi M Katayama T Yamazato H Okada and A OgawaldquoAn adaptive antenna selection scheme for transmit diversityin OFDM systemsrdquo in Proceedings of the IEEE 54th VehicularTechnology Conference (VTC rsquo01) pp 2168ndash2172 October 2001
[11] M Sandell and J P Coon ldquoPer-subcarrier antenna selectionwith power constraints in OFDM systemsrdquo IEEE Transactionson Wireless Communications vol 8 no 2 pp 673ndash677 2009
[12] N P Le F Safaei and L C Tran ldquoTransmit antenna subsetselection for high-rate MIMO-OFDM systems in the presenceof nonlinear power amplifiersrdquo EURASIP Journal on WirelessCommunications and Networking vol 2014 article 27 2014
[13] R PrasadOFDM for Wireless Communications Systems ArtechHouse 1st edition 2004
[14] T Jiang and Y Wu ldquoAn overview peak-to-average power ratioreduction techniques for OFDM signalsrdquo IEEE Transactions onBroadcasting vol 54 no 2 pp 257ndash268 2008
[15] H Ochiai ldquoPerformance analysis of peak power and band-limited OFDM system with linear scalingrdquo IEEE Transactionson Wireless Communications vol 2 no 5 pp 1055ndash1065 2003
[16] C Zhao R J Baxley and G T Zhou ldquoPeak-to-average powerratio and power efficiency considerations in MIMO-OFDMsystemsrdquo IEEE Communications Letters vol 12 no 4 pp 268ndash270 2008
[17] D Wulich and I Gutman ldquoImpact of linear power amplifier onpower loading in OFDM part I principlesrdquo in Proceedings ofthe IEEE 26th Convention of Electrical and Electronics Engineersin Israel (IEEEI rsquo10) pp 360ndash364 November 2010
[18] S Coleri M Ergen A Puri and A Bahai ldquoChannel estimationtechniques based on pilot arrangement in OFDM systemsrdquoIEEE Transactions on Broadcasting vol 48 no 3 pp 223ndash2292002
[19] R W Heath S Sandhu and A Paulraj ldquoAntenna selectionfor spatial multiplexing systems with linear receiversrdquo IEEECommunications Letters vol 5 no 4 pp 142ndash144 2001
[20] R Fletcher Practical Methods of Optimization John Willey ampSons 2nd edition 1987
[21] R W Bauml R F H Fischer and J B Huber ldquoReducingthe peak-to-average power ratio of multicarrier modulation byselected mappingrdquo Electronics Letters vol 32 no 22 pp 2056ndash2057 1996
[22] M Tan Z Latinovic and Y Bar-Ness ldquoSTBC MIMO-OFDMpeak-to-average power ratio reduction by cross-antenna rota-tion and inversionrdquo IEEE Communications Letters vol 9 no 7pp 592ndash594 2005
[23] K M Anstreicher ldquoLinear programming in O(n3lnnL) opera-tionsrdquo SIAM Journal on Optimization vol 9 no 4 pp 803ndash8121999
[24] J G Proakis Digital Communications McGraw Hill 4th edi-tion 2001
[25] O Oyman R U Nabar H Bolcskei and A J Paulraj ldquoChar-acterizing the statistical properties of mutual information inMIMO channelsrdquo IEEE Transactions on Signal Processing vol51 no 11 pp 2784ndash2795 2003
[26] S Cui A J Goldsmith and A Bahai ldquoEnergy-constrainedmodulation optimizationrdquo IEEE Transactions onWireless Com-munications vol 4 no 5 pp 2349ndash2360 2005
[27] R J Baxley and G T Zhou ldquoPower savings analysis of peak-to-average power ratio reduction in OFDMrdquo IEEE Transactions onConsumer Electronics vol 50 no 3 pp 792ndash797 2004
[28] A Batra et al Multiband OFDM Physical Layer SpecificationRelease 1 5 WiMedia Alliance 2009
[29] J Foerster et al ldquoChannel modeling sub-committee reportfinalrdquo IEEE P802 15-02490r1-SG3a 2003
[30] B C Arnold and R A Groeneveld ldquoBounds on expectationsof linear systematic statistics based on dependent samplesrdquoTheAnnals of Statistics vol 7 no 1 pp 220ndash223 1979
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Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Navigation and Observation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
DistributedSensor Networks
International Journal of
6 International Journal of Antennas and Propagation
consider the complementary cumulative distribution func-tion (CCDF) of the peak power defined as the probability thatthe peak power 119875 exceeds a given threshold 119875
0 that is
CCDF119875 (1198750) = Pr (119875 gt 119875
0) (9)
Note that although a procedure for calculating CCDF ofPAPR in OFDM systems is known to the best of ourknowledge all the CCDF expressions with respect toMIMO-OFDM signals available in the literature assume that all datasubcarriers are active which can be considered as a specialcase in the considered system when all the transmit antennashave the same number of allocated data symbols In thefollowing we calculate the CCDF of the peak power in oursystem
Let us begin with the discrete-time OFDM signal 119904119894(119899)
119899 = 0 1 119870minus1 corresponding to the 119894th transmit antennaThe peak power of this signal is defined as
119875119894= max0le119899le119870minus1
|119904119894 (119899) |2 (10)
For analytical tractability we assume that both the real partand imaginary part of the signal 119904
119894(119899) are asymptotically
independent and identically distributed Gaussian randomvariables Note that this assumption which is based on thecentral limit theorem [24] only holds when the number ofassigned data subcarriers on the 119894th antenna denoted as119870119894 is large enough As a result |119904
119894(119899)| follows the Rayleigh
distribution and |119904119894(119899)|2 has a chi-square distribution with
two degrees of freedom The probability density function ofthe signal |119904
119894(119899)|2 can be expressed as [24]
119901|119904|2 (
100381610038161003816100381611990411989410038161003816100381610038162) =
1
1205902119870119894
119890minus|119904119894|21205902
119870119894 (11)
where 1205902119870119894
= 1205902119870119894119870 is the variance of the signal |119904
119894(119899)| Note
that sum119899119879
119894=1119870119894
= 119899119863119870 thus we have sum
119899119879
119894=11205902119870119894
= 1198991198631205902 The
CDF (cumulative distribution function) of the signal |119904119894(119899)|2
is given as
Pr (100381610038161003816100381611990411989410038161003816100381610038162le 120579) = 1 minus 119890
minus1205791205902
119870119894 120579 ge 0 (12)
Suppose that 119870 samples of |119904119894(119899)| 119899 = 0 1 119870 minus 1 are
independent the CDF of the peak power 119875119894can be expressed
as
CDF119875119894 = Pr (119875119894le 1198750)
= Pr (1003816100381610038161003816119904119894 (0)10038161003816100381610038162le 1198750)Pr (1003816100381610038161003816119904119894 (1)
10038161003816100381610038162le 1198750) sdot sdot sdot
Pr (1003816100381610038161003816119904119894 (119870 minus 1)10038161003816100381610038162le 1198750)
= (1 minus 119890minus1198750120590
2
119870119894 )119870
(13)
In MIMO-OFDM systems with linear scaling the peakpower across transmit antennas 119875 can be defined as
119875 = max1le119894le119899119879
119875119894 (14)
Given the statistical independence of data among transmitantennas which is the case in the considered spatial mul-tiplexed OFDM system the CDF of the peak power 119875 iscalculated as
CDF119875 = Pr (119875 le 1198750)
= Pr (1198751le 1198750)Pr (119875
2le 1198750) sdot sdot sdotPr (119875
119899119879le 1198750)
=
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
(15)
Therefore the CCDF of the peak power of the antennaselection MIMO-OFDM signals can be expressed as
CCDF119875imbalance (1198750) = 1 minus CDF119875
= 1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
(16)
In the MIMO-OFDM system with a power balancingconstraint the number of allocated data subcarriers pertransmit antenna is equal to one another (ie 119870
119894=
119899119863119870119899119879
= 119870 forall119894 = 1 2 119899119879) Thus the variances of the
signals are 1205902119870119894
= 1198991198631205902119899119879= 1205902119870 forall119894 = 1 2 119899
119879 As a result
the CCDF expression could be simplified to as
CCDF119875balance (1198750) = 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(17)
A comparison of the CCDF of the peak powers in the twosystems is presented in the following theorem
Theorem 1 In MIMO-OFDM transmission schemes that con-sist of inactive data subcarriers (eg per-subcarrier antennaselection) the probability of occurrences of high peak power isthe smallest when the same number of data symbols is allocatedto all transmit antennas that is
CCDF119875balance (1198750) le CCDF119875imbalance (1198750) (18)
Proof The proof is given in Appendix AWhen the peak-power reduction algorithm proposed in
Section 32 is implemented in theMIMO-OFDMsystemwitha power-balancing constraint the CCDF of the peak powercan be expressed as
CCDF119875balance+reduced (1198750) = (CCDF119875balance (1198750))119882
= (1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870)119882
(19)
where 119882 is the number of candidates that are assumed tobe independent Recall that by definition the CCDF value isalways smaller than one (cf (9)) Therefore the CCDF valuein (19) is smaller than that in (17) that is
CCDF119875balance+reduced (1198750) le CCDF119875balance (1198750) (20)
International Journal of Antennas and Propagation 7
42 Power Efficiency of HPAs We now analyze the powerefficiency (PE) of high-power amplifiers (HPAs) The drainefficiency of HPAs which is defined as a ratio between thepower drawn from the DC source 119875dc and the average outputpower 119875out is considered in this paper Denote 119875119894in and 119875119894out tobe the average input and output powers of the HPA for the119894th antenna respectively Recall that all HPAs are assumedto have a unity gain that is 119875119894out = 119875119894in forall119894 = 1 2 119899
119879
Hence the instantaneous overall power efficiency of HPAs inthe MIMO-OFDM system can be expressed as [16]
120578PE
=sum119899119879
119894=1119875119894out
119899119879119875dc
=sum119899119879
119894=1119875119894in
119899119879119875dc
= 1205721198991198631205902
119899119879119875dc
=1198991198631205902119875sat
119899119879119875dc
1
119875=
1198991198631205902
2119899119879
1
119875
(21)
In the above manipulations we have used the fact thatsum119899119879
119894=1119875119894in = 120572119899
1198631205902 and119875dc = 2119875sat for class-AHPAs regardless
of the average powers of the input time-domain signalsDenoting CCDFPE (120578PE
0) = Pr(120578PE gt 120578PE
0) to be the CCDF
of the power efficiency we obtain the following result withrespect to 120578
PE
Theorem 2 In per-subcarrier antenna selection MIMO-OFDM systems with linear scaling the probability of achievinghigh instantaneous overall power efficiency of HPAs is thelargest when all transmit antennas have the same number ofallocated data symbols that is
CCDFPEbalance (120578PE0) ge CCDFPEimbalance (120578
PE0) (22)
where
CCDFPEbalance (120578PE0) = (1 minus 119890
minus12120578PE0 )119899119879119870
CCDFPEimbalance (120578PE0) =
119899119879
prod119894=1
(1 minus 119890minus1198991198631198702119899119879119870119894120578
PE0 )119870
(23)
Proof From (18) and (21) it is readily to obtain (22) and (23)With respect to the average value of the overall power
efficiency from (21) we can express
120578PE
= 119864 120578PE =
1198991198631205902
2119899119879
1198641
119875 =
1198991198631205902
2119899119879
int1
119909119901 (119909) 119889119909 (24)
where 119901(119909) is the pdf (probability distribution function) ofthe peak power In the system with a balance constraint (ieonly use Step 1) the pdf of the peak power can be calculatedas
119901balance (119909) =119889
119889119909CDF119875balance (119909) =
119889
119889119909(1 minus 119890
minus1199091205902
119870)119899119879119870
=119899119879119870
1205902119870
119890minus1199091205902
119870(1 minus 119890minus1199091205902
119870)119899119879119870minus1
(25)
Hence
120578PEbalance =
1198991198631205902
2119899119879
int1
119909119901balance (119909) 119889119909
=119899119879119870
2int1198701205902
119870
1205902
119870
1
119909119890minus1199091205902
119870(1 minus 119890minus1199091205902
119870)119899119879119870minus1
119889119909
=119899119879119870
2int119870
1
1
119909119890minus119909
(1 minus 119890minus119909
)119899119879119870minus1
119889119909
(26)
Similarly the power efficiency of HPAs in the conventionalsystem is
120578PEimbalance =
1198991198631205902
2119899119879
int1
119909119901imbalance (119909) 119889119909
=1198991198631198701205902
2119899119879
int119870max120590
2
max
1205902
max
1
119909
119899119879
sum119895=1
119890minus1199091205902
119870119895
(1 minus 119890minus1199091205902
119870119895 ) 1205902119870119895
times
119899119879
prod119894=1
(1 minus 119890minus1199091205902
119870119894 )119870
119889119909
(27)
where 1205902max = max12059021198701
1205902119870119899119879
and 119870max = max1198701
119870119899119879When the peak-power reduction algorithm is also imple-
mented (ie the system employs both Steps 1 and 2) it isreadily from (20) and (21) that
CCDFPEbalance+reduced (120578PE0
) ge CCDFPEbalance (120578PE0
) (28)
where
CCDFPEbalance+reduced (120578PE0
) = 1 minus (1 minus (1 minus 119890minus12120578
PE0 )119899119879119870
)119882
(29)
Also the average power efficiency can now be calculated as
120578PEbalance+reduced =
1198991198631205902
2119899119879
int1
119909119901balance+reduced (119909) 119889119909
=119899119879119870119882
2int119870
1
1
119909119890minus119909
(1 minus 119890minus119909
)119899119879119870minus1
times (1 minus (1 minus 119890minus119909
)119899119879119870
)119882minus1
119889119909
(30)
It can be seen from (30) that the smaller the peak poweris reduced (ie the larger the number of candidates 119882 isused) the higher the power efficiency could be achievedNote that although the integrals in (26) (27) and (30) haveno closed-form solutions they can be evaluated numericallyAlso the average power efficiencies in (26) (27) and (30) aretaken with respect to the input data In other words they areconsidered as instantaneous power efficiencieswith respect tothe channel distribution Consequently the power efficiencyin the systems is obtained by averaging these values over thefading channel distribution
8 International Journal of Antennas and Propagation
5 Analyses of Capacity and Energy Efficiency
It has been shown in (22) and (28) that the proposed systemcould achieve a better power efficiency of HPAs than itscounterpart Thus when the power 119875dc is fixed it is intuitivethat an increased average power efficiency results in anincreased average transmit power and in turn leads to anincrease in the achievable rate Moreover an increase in thedata rate under a constant consumption power will translateinto an improvement in energy efficiency The achievedcapacity and energy efficiency are now investigated in thissection
51 System Capacity We begin by rewriting the mutualinformation in (7) with respect to the average SNR valueof 120588 = 119875
1199051205902119899 where 119875
119905= 120572119899
1198631205902 = 120578
PE119899119879119875dc (cf (21))
The ergodic capacity is then calculated by averaging themutual information over the fading channel distributionthat is 119862(120588) = 119864H119868(120588H) From (6) and (7) the mutualinformation in the proposed and conventional systems canbe expressed respectively as
119868 (120588proposedH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
(31)
119868 (120588imbalanceH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(32)
where 120588proposed = 120578PEproposed119899119879119875dc120590
2
119899and 120588imbalance =
120578PEimbalance119899119879119875dc120590
2
119899 Here 120578
PEproposed = 120578
PEbalance+reduced if the
peak-power reduction algorithm is implemented otherwise120578PEproposed = 120578
PEbalance Also H119896 in (31) denotes the effective
channel matrix on the 119896th subcarrier in the proposed systemwhich is obtainedwhen solving the problem in (8)This chan-nel matrix is generally different from the effective channelmatrix H
119896in the conventional system because the selected
antenna subset may be differentThe difference in the mutualinformation between the two systems can be now calculatedas
Δ119868 = 119868 (120588proposedH) minus 119868 (120588imbalanceH) =1
119870
119870minus1
sum119896=0
Δ119868119896 (33)
where
Δ119868119896= log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
minus log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(34)
For analytical simplicity we focus on the high-SNRregime At the high SNR the mutual information at the 119896thsubcarrier can be approximated as [25]
119868119896= log2(det(
120588
119899119863
Ω119896)) (35)
where
Ω119896= Ω (H
119896) =
H119896H119867119896 119899119877le 119899119863
H119867119896H119896 119899119877gt 119899119863
(36)
Thus the difference in the mutual information can berewritten as
Δ119868 =1
119870
119870minus1
sum119896=0
(log2(det(
120588proposed
119899119863
Ω119896))
minuslog2(det(
120588imbalance119899119863
Ω119896)))
= 119901log2
120578PEproposed
120578PEimbalance
minus1
119870
119870minus1
sum119896=0
Δ119896= 1198791+ 1198792
(37)
where 119901 = min(119899119863 119899119877)Ω119896= Ω(H
119896) and
Δ119896= log2(det (Ω
119896)) minus log
2(det (Ω
119896)) (38)
is the loss in the mutual information associated with the 119896thsubcarrier due to the constrained allocation Note that if bothsystems have the same selected antenna subset at the 119896thsubcarrier then Δ
119896= 0 otherwise Δ
119896gt 0Thus the total loss
in the mutual information Δ = (1119870)sum119870minus1
119896=0Δ119896gt 0
We have some important observations with respect to thevalue of Δ119868 in (37)
(i)The change in mutual information Δ119868 comes fromtwo sources The first source 119879
1is a benefit in mutual
information due to the improvement in the powerefficiency of HPAs The second source 119879
2is a penalty
that incurs because the chosen effective channelmatrices in the proposed system are different from theones in the conventional system(ii) For each channel realization thematrixH
119896is fixed
and the first term 1198791in (37) is a constant Thus the
value of Δ119868 depends on how the effective channelmatrix H
119896is selected in the constrained selection
scheme From this observation it is clear that tomake the value Δ119868 become as positive as possiblethe constrained selection method should result inthe cost penalty Δ as small as possible We note thatthe formulated optimization in (8) could achieve theminimum possible value of the total cost Hence it isexpected that the constrained selection scheme basedon linear optimization will guarantee the maximumachievable value of Δ119868 In addition to have an insightinto the cost penalty we derive the upper bound ofthe expected value of the cost penalty in Appendix BBased on the obtained bound it is observed that forfixed values of 119899
119879and 119899
119863 the cost penalty becomes
smaller with an increasing value of 119902 = max(119899119863 119899119877)
International Journal of Antennas and Propagation 9
(iii) As Δ gt 0 the upper bound of the capacityimprovement can be given as
Δ119862 = 119864H Δ119868 le 119901log2119864H
120578PEproposed
120578PEimbalance
(39)
In (39) we have used Jensenrsquos inequality of119864log(119909) le log(119864119909) as log(119909) is a concavefunction Based on this bound we could estimatethe maximum improvement in capacity that couldbe realized in the proposed system compared to itscounterpart
It is now necessary to evaluate the change in capacitythat is Δ119862 We note that although the distribution of themutual information at high SNRs can be well approximatedby a Gaussian distribution [25] it is still challenging toperform a mathematical evaluation of Δ119862 from a statisticalviewpoint This is mainly due to the fact that the two termsin (37) are complicated dependent random variables Thuswe perform a numerical evaluation of Δ119862 instead Figure 4plots the empirical CCDF of 119879
1 CDF of 119879
2 and CCDF
of Δ119868 In the figure ldquo119882 = 1rdquo stands for the case in whichonly Step 1 in Section 31 is implemented The results areobtained in the systems with 119899
119879= 4 119899
119863= 2 119899
119877= 2 119870= 128
and are averaged over 103 channel realizations Details aboutother simulation parameters are described in Section 6 Thenumerical results confirm that 119879
1gt 0 and 119879
2lt 0 Moreover
as shown in Figure 4(c) Δ119868 is always positive when the peak-power reduction algorithm is implemented (ie 119882= 4 and119882 = 8) For the case of 119882 = 1 the probability of ΔI beingpositive is significant Therefore the proposed system attainsa better ergodic capacity than that in the conventional systemThe achieved capacities in the considered systems will beprovided in Section 6
52 Energy Efficiency In this subsection we further exam-ine the efficacy of the proposed system from an energy-efficiency (EE) perspective Normalized energy efficiency(bitsHzJoule) in MIMO-OFDM systems can be defined as[3 26]
120578EE
=119862 (120588)
119875total (40)
where 119862(120588) is the achievable rate and the total powerconsumption per-subchannel is 119875total = 119899
119879119875dc + 119899
119879119875RF + 119875sp
where 119875RF is the RF power consumption in each transmitbranch excluding the associatedHPA and119875sp is the basebandprocessing power consumption It can be seen from (40)that given a fixed value of 119875total a comparison of energyefficiency achieved in the two systems is based on the capacitycomparison that has been analyzed in Section 51We are nowinterested in evaluating a useful metric of energy efficiency-spectral efficiency performance Recall that the average SNR120588 is given as 120588 = 119875
1199051205902119899= 120578
PE119899119879119875dc1205902
119899 Thus we can rewrite
the energy efficiency in (40) as a function of 119875dc as
120578EE
(119875dc) =119862 (120578
PE119899119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
(41)
Table 2 Simulation parameters
Parameter ValueBandwidth 528MHzFFT size 128Number of samples in zero-padded suffix 37Modulation scheme 4-QAMIEEE 802153a channel model CM1
The energy efficiency of the proposed and conventionalsystems can now be respectively expressed as
120578EEproposed (119875dc) =
119862proposed (120578PEproposed 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEproposed 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(42)
120578EEimbalance (119875dc) =
119862imbalance (120578PEimbalance 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEimbalance 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(43)
Similarly to the case of capacity we compare the energyefficiency achieved in the two systems by means of numericalresults in the next section Note that the calculation of energyefficiency in the proposed system (ie (42)) has assumed thata reduction in spectral efficiency due to the side informationas well as additional processing power required for the peak-power reduction algorithm is negligible In fact a reductionin spectral efficiency is very small For example in a systemwith 16-QAM FFT size of 128 119899
119863= 2 and 119882= 4 (ie 2 bits
are needed for side information) a spectral efficiency lossis 2 bits(128 times 4 times 2 + 2) bits = 019 Also it was shownin [27] that the additional power cost when implementingSLM schemes is minuscule Thus the proposed peak-powerreduction algorithm in Section 32 which is a SLM-basedscheme requires a small additional power cost
6 Numerical Results
In this section we provide numerical results to validatethe analyses mentioned in the previous sections as wellas demonstrate the effectiveness of the proposed allocationscheme over its counterpart A MIMO-OFDM system with119899119879= 4 119899
119863= 2 and 119899
119877= 2 is considered in our simulations
The system parameters are listed in Table 2These parametersare chosen based on the legacy WiMedia MB-OFDM UWB(Multiband-OFDM UWB) standard [28] Also the channelCM1 defined in the IEEE 802153a channel model [29] isbased on ameasurement of a line-of-sight scenario where thedistance between the transmitter and the receiver is up to 4mMoreover the multipath gains are modeled as independentlog normally distributed random variables We assume thatperfect channel state information is available at the receiverAlso the feedback link has no delay and is error-free
10 International Journal of Antennas and Propagation
Empirical CCDF of T110
0
10minus1
10minus2
minus2 0 2
W = 1
W = 4
W = 8
(a)
100
10minus1
10minus2
minus04 minus02 0
Empirical CDF of T2
(b)
Empirical CCDF of (T1 + T2)10
0
10minus1
10minus2
minus1 minus05 0 05 1 15 2
W = 1
W = 4
W = 8
(c)
Figure 4 Statistical distributions (note 1198792is independent of119882)
61 Evaluations of Peak-Power Distribution In Figure 5 weplot the CCDFs of the peak power of time-domain signalsThe analytical curves are based on (16) (17) and (19) Mean-while the simulation curves are empirical CCDF values Thesimulation result confirms that a system with the proposedallocation scheme offers a better CCDF performance than itscounterpart As expected the occurrence of high peak poweris significantly reduced when the peak-power reductionalgorithm is implemented Also it can be seen that theimprovement associated with this algorithm is reduced withincreasing 119882 In other words a very large value of 119882 whilerequiring higher complexity in terms on the number of IFFToperations results in a marginal improvement Thus it isreasonable to choose a relatively small value for 119882 (eg119882 = 4) It is also worth noting that the analytical curvesare relatively close to the simulation curves The small gapsexist due to the fact that the assumption of independentsamples |119904
119894(119899)| to obtain (13) does not strictly hold as we have
sum119870minus1
119899=0|119904119894(119899)|2 = 1205902119870
119894by Parsevalrsquos relation [24]
62 Evaluations of Power Efficiency of HPAs Figure 6 com-pares the CCDFs of the power efficiency achieved in theproposed and conventional systems It can be seen that theprobability of power efficiency being large highly likely occursin the proposed system compared to its counterpart Also
the simulation results agree well with the analytical resultsderived in (23) and (29) In Table 3 we compare the averagepower efficiencies Here the analytical values are obtainedaccording to (26) (27) and (30) Meanwhile the simulationvalues are empirical values based on the original definitionof the drain efficiency in (21) Also these values are averagedover the fading channel realizations It can be seen that thederived expressions approximate well the achieved powerefficiencies Table 3 also provides relative improvements ofthe power efficiencies achieved in the proposed system overthe conventional system Here only 120578
PE (Simulation) valuesare used for calculating these improvements It is clear thatthe proposed system could achieve a significant improvementin terms of average power efficiency
63 Evaluations of Capacity and Energy Efficiency Figure 7shows the system capacity inMbps (ie the normalized valuein (6) is scaled upwith the system bandwidth) versus the SNRvalue of 12059021205902
119899 It is clear that a systemwith the proposed allo-
cation scheme achieves a higher capacity than its counterpartThis agrees with the analysis in Section 51 that the changein capacity Δ119862 is positive In Figure 8 we plot the energyefficiency (MbitsJoule) versus spectral efficiency (MbpsHz)This figure is obtained based on (42) and (43) when varying119875dc Other parameters are 119875RF = 100mW 119875sp = 10mW and
International Journal of Antennas and Propagation 11
Table 3 A comparison of average power efficiencies
Imbalance Proposed (119882 = 1) Proposed (119882 = 4) Proposed (119882 = 8)120578PE (Simulation) 00697 00768 00894 00942
120578PE (Analysis) 00691 00757 00892 00943
Improvement120578PEproposed minus 120578
PEimbalance
120578PEimbalance
mdash 1019 2826 3515
1 2 3 4 5 6 7 8 9
100
10minus1
10minus2
10minus3
Peak power P0
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Pr (P
gtP0)
Figure 5 Comparison of CCDFs of the peak powers
002 004 006 008 01 012 014Power efficiency
CCD
F
100
10minus1
10minus2
10minus3
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Figure 6 Comparison of CCDFs of the power efficiencies
4500
4000
3500
3000
2500
2000
1500
1000
Ergo
dic c
apac
ity (M
bps)
2 4 6 8 10 12 14
SNR (dB)
3300
3200
3100
3000
2900
2800
97 98 99 10 101
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 7 Comparison of the ergodic capacities
12059021205902119899= 15 dB As expected the improvement in the power
efficiency of HPAs results in an improved energy efficiencyIn addition it can be observed that there exists an energyefficiency-spectral efficiency tradeoff in the systems Thistradeoff clearly needs to be taken into consideration whendesigning energy-efficient per-subcarrier antenna selectionbased OFDM wireless systems
7 Conclusions
In this paper a per-subcarrier antenna subset selectionMIMO-OFDM system with linear scaling has been investi-gated from an energy-efficiency perspective We have shownthat an imbalance allocation of data subcarriers associatedwith the conventional selection scheme affects the power effi-ciency of HPAs as well as the energy-efficiency of the wholesystem To deliver the maximum overall power efficiencywe have proposed the two-step strategy consisting of equalallocation data subcarriers across antennas and peak-powerreduction It has been proved from the power-efficiency view-point that the proposed allocation scheme outperforms theconventional scheme We have also derived the expressionsfor measuring the average power efficiency Moreover theimprovements in terms of capacity and energy efficiency
12 International Journal of Antennas and Propagation
0 2 4 6 8 10400
600
800
1000
1200
1400
1600
Spectral efficiency (MbpsHz)
Ener
gy effi
cien
cy (M
bits
J)
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 8 Energy efficiency versus spectral efficiency
resulting from the improved power efficiency have beenanalyzed The analytical results are validated by simulationresults The simulation result also shows that the systemwith the proposed allocation scheme could achieve a betterefficiency efficiency-spectral energy tradeoff compared to itscounterpart
Appendices
A Proof of Theorem 1
Let us consider a function 119891(120592) = 1 minus 119890minus1198750120592 0 lt 120592 le 1205902maxwhere 1205902max = max1205902
1198701 12059021198702
1205902119870119899119879
The second derivativeof this function is
11989110158401015840(120592) =
21198750120592 minus 11987520
1205924119890minus1198750120592 (A1)
From a HPAsrsquo viewpoint it is of interest to consider thesituation when the peak power across antennas 119875
0is large
Thus we consider the scenarios of 1198750
gt 21205902max where 1205902maxis the maximum average power across antennas Under thesesituations it is clear that 11989110158401015840(120592) lt 0 forall120592 isin (0 1205902max] Hencethe function 119891(120592) is concave By applying Jensenrsquos inequalitywe obtain the following inequality
1
119899119879
119899119879
sum119894=1
119891 (1205902
119870119894) le 119891(
1
119899119879
119899119879
sum119894=1
1205902
119870119894)
= 119891(1
119899119879
119899119879
sum119894=1
1205902
119870) = 119891 (120590
2
119870)
(A2)
where the equality comes from the fact that sum119899119879
119894=11205902119870119894
=
sum119899119879
119894=11205902119870
= 1198991198631205902 Expression (A2) can be rewritten as119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le 119899119879(1 minus 119890
minus11987501205902
119870) (A3)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879
On the other hand by applying the arithmetic-geometricmean inequality and note that (1 minus 119890
minus119909) gt 0 forall119909 gt 0 we have
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1
119899119879
119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ))
119899119879
(A4)
Note that the equality in (A4) holds if and only if 1205902119870119894
= 1205902119870
forall119894 = 1 119899119879
Combining (A3) and (A4) results in
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1 minus 119890minus1198750120590
2
119870)119899119879
(A5)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879 Thus we
get the following desired inequality
1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
ge 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(A6)
or
CCDF119875imbalance (1198750) ge CCDF119875balance (1198750) (A7)
This completes the proof
B Upper Bound of an ExpectedValue of Cost Penalty
In this appendix we derive an upper bound of the expectedvalue of Δ
119896 It can be seen from (5) that among all pos-
sible matrices H119896 the matrix H
119896with the highest value of
log2(det(Ω
119896))Ω119896
= Ω(H119896) will be selected as the effective
channel matrix for the 119896th subcarrier in the conventionalscheme Meanwhile in the proposed scheme due to thebalance constraint the effective channel matrix associatedwith the kth subcarrier is not necessarily the one with thehighest log
2(det(Ω
119896)) that is log
2(det(Ω
119896)) le log
2(det(Ω
119896))
Thus the expected value of Δ119896can be computed by using
order statistics In particular an upper bound on the expecteddifference of two-order statistics the Γth and 120574th 1 le 120574 lt Γis given by [30]
119864 Δ119896 = 119864 log
2(det (Ω
119896)) minus 119864 log
2(det (Ω
119896))
le 120590119862radic
Γ (120574 + 1)
120574
(B1)
where 1205902119862is the variance of log
2(det(Ω
119896)) that is assumed to
be the same for all possible matricesH119896
On the other hand suppose that the entries of the 119899119877times119899119879
matrixH119896are iid complex Gaussian random variables with
zero mean and unit variance then for any effective channelmatrix H
119896 Ω119896is a complex Wishart matrix It follows from
[25] that the variance of log2(det(Ω
119896)) can be expressed as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1205951015840(119902 minus 119898 + 1) (B2)
International Journal of Antennas and Propagation 13
where 119901 = min(119899119863 119899119877) 119902 = max(119899
119863 119899119877) and 1205951015840(119909) =
suminfin
120593=11(120593 + 119909 minus 1)
2 is the first derivative of the digammafunction By approximating 1205951015840(119909) asymp 1119909 [25] the simplerexpression for 1205902
119862in (B2) is given as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1
119902 minus 119898 + 1 (B3)
Substitute (B3) into (B1) we finally arrive at
119864 Δ119896 le log
2(119890)radic(
119901
sum119898=1
1
119902 minus 119898 + 1) times
Γ (120574 + 1)
120574 (B4)
Conflict of Interests
The authors declare that there is no conflict of interestsregarding the publication of this paper
References
[1] L M Correia D Zeller O Blume et al ldquoChallenges andenabling technologies for energy aware mobile radio networksrdquoIEEECommunicationsMagazine vol 48 no 11 pp 66ndash72 2010
[2] Z Hasan H Boostanimehr and V K Bhargava ldquoGreen cellularnetworks a survey some research issues and challengesrdquo IEEECommunications Surveys and Tutorials vol 13 no 4 pp 524ndash540 2011
[3] J Joung C K Ho and S Sun ldquoGreenwireless communicationsa power amplifier perspectiverdquo in Proceedings of the 4th Asia-Pacific Signal and Information Processing Association AnnualSummit and Conference (APSIPA ASC rsquo12) pp 1ndash8 December2012
[4] G L Stuber J R Barry S W Mclaughlin Y E Li M AIngram and T G Pratt ldquoBroadband MIMO-OFDM wirelesscommunicationsrdquoProceedings of the IEEE vol 92 no 2 pp 271ndash294 2004
[5] H Bolcskei D Gesbert and A J Paulraj ldquoOn the capacity ofOFDM-based spatial multiplexing systemsrdquo IEEE Transactionson Communications vol 50 no 2 pp 225ndash234 2002
[6] V Tarokh N Seshadri and A R Calderbank ldquoSpace-timecodes for high data rate wireless communication performancecriterion and code constructionrdquo IEEE Transactions on Infor-mation Theory vol 44 no 2 pp 744ndash765 1998
[7] C M Vithanage M Sandell J P Coon and Y Wang ldquoPrecod-ing in OFDM-based multi-antenna ultra-wideband systemsrdquoIEEE Communications Magazine vol 47 no 1 pp 41ndash47 2009
[8] Z Tang H Suzuki and I B Collings ldquoPerformance of antennaselection forMIMO-OFDMsystems based onmeasured indoorcorrelated frequency selective channelsrdquo in Proceedings of theAustralian Telecommunication Networks and Applications Con-ference pp 435ndash439 December 2006
[9] H Zhang and R U Nabar ldquoTransmit antenna selection inMIMO-OFDM systems bulk versus per-tone selectionrdquo inProceedings of the IEEE International Conference on Communi-cations (ICC rsquo08) pp 4371ndash4375 May 2008
[10] H Shi M Katayama T Yamazato H Okada and A OgawaldquoAn adaptive antenna selection scheme for transmit diversityin OFDM systemsrdquo in Proceedings of the IEEE 54th VehicularTechnology Conference (VTC rsquo01) pp 2168ndash2172 October 2001
[11] M Sandell and J P Coon ldquoPer-subcarrier antenna selectionwith power constraints in OFDM systemsrdquo IEEE Transactionson Wireless Communications vol 8 no 2 pp 673ndash677 2009
[12] N P Le F Safaei and L C Tran ldquoTransmit antenna subsetselection for high-rate MIMO-OFDM systems in the presenceof nonlinear power amplifiersrdquo EURASIP Journal on WirelessCommunications and Networking vol 2014 article 27 2014
[13] R PrasadOFDM for Wireless Communications Systems ArtechHouse 1st edition 2004
[14] T Jiang and Y Wu ldquoAn overview peak-to-average power ratioreduction techniques for OFDM signalsrdquo IEEE Transactions onBroadcasting vol 54 no 2 pp 257ndash268 2008
[15] H Ochiai ldquoPerformance analysis of peak power and band-limited OFDM system with linear scalingrdquo IEEE Transactionson Wireless Communications vol 2 no 5 pp 1055ndash1065 2003
[16] C Zhao R J Baxley and G T Zhou ldquoPeak-to-average powerratio and power efficiency considerations in MIMO-OFDMsystemsrdquo IEEE Communications Letters vol 12 no 4 pp 268ndash270 2008
[17] D Wulich and I Gutman ldquoImpact of linear power amplifier onpower loading in OFDM part I principlesrdquo in Proceedings ofthe IEEE 26th Convention of Electrical and Electronics Engineersin Israel (IEEEI rsquo10) pp 360ndash364 November 2010
[18] S Coleri M Ergen A Puri and A Bahai ldquoChannel estimationtechniques based on pilot arrangement in OFDM systemsrdquoIEEE Transactions on Broadcasting vol 48 no 3 pp 223ndash2292002
[19] R W Heath S Sandhu and A Paulraj ldquoAntenna selectionfor spatial multiplexing systems with linear receiversrdquo IEEECommunications Letters vol 5 no 4 pp 142ndash144 2001
[20] R Fletcher Practical Methods of Optimization John Willey ampSons 2nd edition 1987
[21] R W Bauml R F H Fischer and J B Huber ldquoReducingthe peak-to-average power ratio of multicarrier modulation byselected mappingrdquo Electronics Letters vol 32 no 22 pp 2056ndash2057 1996
[22] M Tan Z Latinovic and Y Bar-Ness ldquoSTBC MIMO-OFDMpeak-to-average power ratio reduction by cross-antenna rota-tion and inversionrdquo IEEE Communications Letters vol 9 no 7pp 592ndash594 2005
[23] K M Anstreicher ldquoLinear programming in O(n3lnnL) opera-tionsrdquo SIAM Journal on Optimization vol 9 no 4 pp 803ndash8121999
[24] J G Proakis Digital Communications McGraw Hill 4th edi-tion 2001
[25] O Oyman R U Nabar H Bolcskei and A J Paulraj ldquoChar-acterizing the statistical properties of mutual information inMIMO channelsrdquo IEEE Transactions on Signal Processing vol51 no 11 pp 2784ndash2795 2003
[26] S Cui A J Goldsmith and A Bahai ldquoEnergy-constrainedmodulation optimizationrdquo IEEE Transactions onWireless Com-munications vol 4 no 5 pp 2349ndash2360 2005
[27] R J Baxley and G T Zhou ldquoPower savings analysis of peak-to-average power ratio reduction in OFDMrdquo IEEE Transactions onConsumer Electronics vol 50 no 3 pp 792ndash797 2004
[28] A Batra et al Multiband OFDM Physical Layer SpecificationRelease 1 5 WiMedia Alliance 2009
[29] J Foerster et al ldquoChannel modeling sub-committee reportfinalrdquo IEEE P802 15-02490r1-SG3a 2003
[30] B C Arnold and R A Groeneveld ldquoBounds on expectationsof linear systematic statistics based on dependent samplesrdquoTheAnnals of Statistics vol 7 no 1 pp 220ndash223 1979
International Journal of
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Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
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RotatingMachinery
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
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Journal ofEngineeringVolume 2014
Submit your manuscripts athttpwwwhindawicom
VLSI Design
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
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Shock and Vibration
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Civil EngineeringAdvances in
Acoustics and VibrationAdvances in
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Electrical and Computer Engineering
Journal of
Advances inOptoElectronics
Hindawi Publishing Corporation httpwwwhindawicom
Volume 2014
The Scientific World JournalHindawi Publishing Corporation httpwwwhindawicom Volume 2014
SensorsJournal of
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Modelling amp Simulation in EngineeringHindawi Publishing Corporation httpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Chemical EngineeringInternational Journal of Antennas and
Propagation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
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Navigation and Observation
International Journal of
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DistributedSensor Networks
International Journal of
International Journal of Antennas and Propagation 7
42 Power Efficiency of HPAs We now analyze the powerefficiency (PE) of high-power amplifiers (HPAs) The drainefficiency of HPAs which is defined as a ratio between thepower drawn from the DC source 119875dc and the average outputpower 119875out is considered in this paper Denote 119875119894in and 119875119894out tobe the average input and output powers of the HPA for the119894th antenna respectively Recall that all HPAs are assumedto have a unity gain that is 119875119894out = 119875119894in forall119894 = 1 2 119899
119879
Hence the instantaneous overall power efficiency of HPAs inthe MIMO-OFDM system can be expressed as [16]
120578PE
=sum119899119879
119894=1119875119894out
119899119879119875dc
=sum119899119879
119894=1119875119894in
119899119879119875dc
= 1205721198991198631205902
119899119879119875dc
=1198991198631205902119875sat
119899119879119875dc
1
119875=
1198991198631205902
2119899119879
1
119875
(21)
In the above manipulations we have used the fact thatsum119899119879
119894=1119875119894in = 120572119899
1198631205902 and119875dc = 2119875sat for class-AHPAs regardless
of the average powers of the input time-domain signalsDenoting CCDFPE (120578PE
0) = Pr(120578PE gt 120578PE
0) to be the CCDF
of the power efficiency we obtain the following result withrespect to 120578
PE
Theorem 2 In per-subcarrier antenna selection MIMO-OFDM systems with linear scaling the probability of achievinghigh instantaneous overall power efficiency of HPAs is thelargest when all transmit antennas have the same number ofallocated data symbols that is
CCDFPEbalance (120578PE0) ge CCDFPEimbalance (120578
PE0) (22)
where
CCDFPEbalance (120578PE0) = (1 minus 119890
minus12120578PE0 )119899119879119870
CCDFPEimbalance (120578PE0) =
119899119879
prod119894=1
(1 minus 119890minus1198991198631198702119899119879119870119894120578
PE0 )119870
(23)
Proof From (18) and (21) it is readily to obtain (22) and (23)With respect to the average value of the overall power
efficiency from (21) we can express
120578PE
= 119864 120578PE =
1198991198631205902
2119899119879
1198641
119875 =
1198991198631205902
2119899119879
int1
119909119901 (119909) 119889119909 (24)
where 119901(119909) is the pdf (probability distribution function) ofthe peak power In the system with a balance constraint (ieonly use Step 1) the pdf of the peak power can be calculatedas
119901balance (119909) =119889
119889119909CDF119875balance (119909) =
119889
119889119909(1 minus 119890
minus1199091205902
119870)119899119879119870
=119899119879119870
1205902119870
119890minus1199091205902
119870(1 minus 119890minus1199091205902
119870)119899119879119870minus1
(25)
Hence
120578PEbalance =
1198991198631205902
2119899119879
int1
119909119901balance (119909) 119889119909
=119899119879119870
2int1198701205902
119870
1205902
119870
1
119909119890minus1199091205902
119870(1 minus 119890minus1199091205902
119870)119899119879119870minus1
119889119909
=119899119879119870
2int119870
1
1
119909119890minus119909
(1 minus 119890minus119909
)119899119879119870minus1
119889119909
(26)
Similarly the power efficiency of HPAs in the conventionalsystem is
120578PEimbalance =
1198991198631205902
2119899119879
int1
119909119901imbalance (119909) 119889119909
=1198991198631198701205902
2119899119879
int119870max120590
2
max
1205902
max
1
119909
119899119879
sum119895=1
119890minus1199091205902
119870119895
(1 minus 119890minus1199091205902
119870119895 ) 1205902119870119895
times
119899119879
prod119894=1
(1 minus 119890minus1199091205902
119870119894 )119870
119889119909
(27)
where 1205902max = max12059021198701
1205902119870119899119879
and 119870max = max1198701
119870119899119879When the peak-power reduction algorithm is also imple-
mented (ie the system employs both Steps 1 and 2) it isreadily from (20) and (21) that
CCDFPEbalance+reduced (120578PE0
) ge CCDFPEbalance (120578PE0
) (28)
where
CCDFPEbalance+reduced (120578PE0
) = 1 minus (1 minus (1 minus 119890minus12120578
PE0 )119899119879119870
)119882
(29)
Also the average power efficiency can now be calculated as
120578PEbalance+reduced =
1198991198631205902
2119899119879
int1
119909119901balance+reduced (119909) 119889119909
=119899119879119870119882
2int119870
1
1
119909119890minus119909
(1 minus 119890minus119909
)119899119879119870minus1
times (1 minus (1 minus 119890minus119909
)119899119879119870
)119882minus1
119889119909
(30)
It can be seen from (30) that the smaller the peak poweris reduced (ie the larger the number of candidates 119882 isused) the higher the power efficiency could be achievedNote that although the integrals in (26) (27) and (30) haveno closed-form solutions they can be evaluated numericallyAlso the average power efficiencies in (26) (27) and (30) aretaken with respect to the input data In other words they areconsidered as instantaneous power efficiencieswith respect tothe channel distribution Consequently the power efficiencyin the systems is obtained by averaging these values over thefading channel distribution
8 International Journal of Antennas and Propagation
5 Analyses of Capacity and Energy Efficiency
It has been shown in (22) and (28) that the proposed systemcould achieve a better power efficiency of HPAs than itscounterpart Thus when the power 119875dc is fixed it is intuitivethat an increased average power efficiency results in anincreased average transmit power and in turn leads to anincrease in the achievable rate Moreover an increase in thedata rate under a constant consumption power will translateinto an improvement in energy efficiency The achievedcapacity and energy efficiency are now investigated in thissection
51 System Capacity We begin by rewriting the mutualinformation in (7) with respect to the average SNR valueof 120588 = 119875
1199051205902119899 where 119875
119905= 120572119899
1198631205902 = 120578
PE119899119879119875dc (cf (21))
The ergodic capacity is then calculated by averaging themutual information over the fading channel distributionthat is 119862(120588) = 119864H119868(120588H) From (6) and (7) the mutualinformation in the proposed and conventional systems canbe expressed respectively as
119868 (120588proposedH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
(31)
119868 (120588imbalanceH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(32)
where 120588proposed = 120578PEproposed119899119879119875dc120590
2
119899and 120588imbalance =
120578PEimbalance119899119879119875dc120590
2
119899 Here 120578
PEproposed = 120578
PEbalance+reduced if the
peak-power reduction algorithm is implemented otherwise120578PEproposed = 120578
PEbalance Also H119896 in (31) denotes the effective
channel matrix on the 119896th subcarrier in the proposed systemwhich is obtainedwhen solving the problem in (8)This chan-nel matrix is generally different from the effective channelmatrix H
119896in the conventional system because the selected
antenna subset may be differentThe difference in the mutualinformation between the two systems can be now calculatedas
Δ119868 = 119868 (120588proposedH) minus 119868 (120588imbalanceH) =1
119870
119870minus1
sum119896=0
Δ119868119896 (33)
where
Δ119868119896= log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
minus log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(34)
For analytical simplicity we focus on the high-SNRregime At the high SNR the mutual information at the 119896thsubcarrier can be approximated as [25]
119868119896= log2(det(
120588
119899119863
Ω119896)) (35)
where
Ω119896= Ω (H
119896) =
H119896H119867119896 119899119877le 119899119863
H119867119896H119896 119899119877gt 119899119863
(36)
Thus the difference in the mutual information can berewritten as
Δ119868 =1
119870
119870minus1
sum119896=0
(log2(det(
120588proposed
119899119863
Ω119896))
minuslog2(det(
120588imbalance119899119863
Ω119896)))
= 119901log2
120578PEproposed
120578PEimbalance
minus1
119870
119870minus1
sum119896=0
Δ119896= 1198791+ 1198792
(37)
where 119901 = min(119899119863 119899119877)Ω119896= Ω(H
119896) and
Δ119896= log2(det (Ω
119896)) minus log
2(det (Ω
119896)) (38)
is the loss in the mutual information associated with the 119896thsubcarrier due to the constrained allocation Note that if bothsystems have the same selected antenna subset at the 119896thsubcarrier then Δ
119896= 0 otherwise Δ
119896gt 0Thus the total loss
in the mutual information Δ = (1119870)sum119870minus1
119896=0Δ119896gt 0
We have some important observations with respect to thevalue of Δ119868 in (37)
(i)The change in mutual information Δ119868 comes fromtwo sources The first source 119879
1is a benefit in mutual
information due to the improvement in the powerefficiency of HPAs The second source 119879
2is a penalty
that incurs because the chosen effective channelmatrices in the proposed system are different from theones in the conventional system(ii) For each channel realization thematrixH
119896is fixed
and the first term 1198791in (37) is a constant Thus the
value of Δ119868 depends on how the effective channelmatrix H
119896is selected in the constrained selection
scheme From this observation it is clear that tomake the value Δ119868 become as positive as possiblethe constrained selection method should result inthe cost penalty Δ as small as possible We note thatthe formulated optimization in (8) could achieve theminimum possible value of the total cost Hence it isexpected that the constrained selection scheme basedon linear optimization will guarantee the maximumachievable value of Δ119868 In addition to have an insightinto the cost penalty we derive the upper bound ofthe expected value of the cost penalty in Appendix BBased on the obtained bound it is observed that forfixed values of 119899
119879and 119899
119863 the cost penalty becomes
smaller with an increasing value of 119902 = max(119899119863 119899119877)
International Journal of Antennas and Propagation 9
(iii) As Δ gt 0 the upper bound of the capacityimprovement can be given as
Δ119862 = 119864H Δ119868 le 119901log2119864H
120578PEproposed
120578PEimbalance
(39)
In (39) we have used Jensenrsquos inequality of119864log(119909) le log(119864119909) as log(119909) is a concavefunction Based on this bound we could estimatethe maximum improvement in capacity that couldbe realized in the proposed system compared to itscounterpart
It is now necessary to evaluate the change in capacitythat is Δ119862 We note that although the distribution of themutual information at high SNRs can be well approximatedby a Gaussian distribution [25] it is still challenging toperform a mathematical evaluation of Δ119862 from a statisticalviewpoint This is mainly due to the fact that the two termsin (37) are complicated dependent random variables Thuswe perform a numerical evaluation of Δ119862 instead Figure 4plots the empirical CCDF of 119879
1 CDF of 119879
2 and CCDF
of Δ119868 In the figure ldquo119882 = 1rdquo stands for the case in whichonly Step 1 in Section 31 is implemented The results areobtained in the systems with 119899
119879= 4 119899
119863= 2 119899
119877= 2 119870= 128
and are averaged over 103 channel realizations Details aboutother simulation parameters are described in Section 6 Thenumerical results confirm that 119879
1gt 0 and 119879
2lt 0 Moreover
as shown in Figure 4(c) Δ119868 is always positive when the peak-power reduction algorithm is implemented (ie 119882= 4 and119882 = 8) For the case of 119882 = 1 the probability of ΔI beingpositive is significant Therefore the proposed system attainsa better ergodic capacity than that in the conventional systemThe achieved capacities in the considered systems will beprovided in Section 6
52 Energy Efficiency In this subsection we further exam-ine the efficacy of the proposed system from an energy-efficiency (EE) perspective Normalized energy efficiency(bitsHzJoule) in MIMO-OFDM systems can be defined as[3 26]
120578EE
=119862 (120588)
119875total (40)
where 119862(120588) is the achievable rate and the total powerconsumption per-subchannel is 119875total = 119899
119879119875dc + 119899
119879119875RF + 119875sp
where 119875RF is the RF power consumption in each transmitbranch excluding the associatedHPA and119875sp is the basebandprocessing power consumption It can be seen from (40)that given a fixed value of 119875total a comparison of energyefficiency achieved in the two systems is based on the capacitycomparison that has been analyzed in Section 51We are nowinterested in evaluating a useful metric of energy efficiency-spectral efficiency performance Recall that the average SNR120588 is given as 120588 = 119875
1199051205902119899= 120578
PE119899119879119875dc1205902
119899 Thus we can rewrite
the energy efficiency in (40) as a function of 119875dc as
120578EE
(119875dc) =119862 (120578
PE119899119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
(41)
Table 2 Simulation parameters
Parameter ValueBandwidth 528MHzFFT size 128Number of samples in zero-padded suffix 37Modulation scheme 4-QAMIEEE 802153a channel model CM1
The energy efficiency of the proposed and conventionalsystems can now be respectively expressed as
120578EEproposed (119875dc) =
119862proposed (120578PEproposed 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEproposed 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(42)
120578EEimbalance (119875dc) =
119862imbalance (120578PEimbalance 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEimbalance 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(43)
Similarly to the case of capacity we compare the energyefficiency achieved in the two systems by means of numericalresults in the next section Note that the calculation of energyefficiency in the proposed system (ie (42)) has assumed thata reduction in spectral efficiency due to the side informationas well as additional processing power required for the peak-power reduction algorithm is negligible In fact a reductionin spectral efficiency is very small For example in a systemwith 16-QAM FFT size of 128 119899
119863= 2 and 119882= 4 (ie 2 bits
are needed for side information) a spectral efficiency lossis 2 bits(128 times 4 times 2 + 2) bits = 019 Also it was shownin [27] that the additional power cost when implementingSLM schemes is minuscule Thus the proposed peak-powerreduction algorithm in Section 32 which is a SLM-basedscheme requires a small additional power cost
6 Numerical Results
In this section we provide numerical results to validatethe analyses mentioned in the previous sections as wellas demonstrate the effectiveness of the proposed allocationscheme over its counterpart A MIMO-OFDM system with119899119879= 4 119899
119863= 2 and 119899
119877= 2 is considered in our simulations
The system parameters are listed in Table 2These parametersare chosen based on the legacy WiMedia MB-OFDM UWB(Multiband-OFDM UWB) standard [28] Also the channelCM1 defined in the IEEE 802153a channel model [29] isbased on ameasurement of a line-of-sight scenario where thedistance between the transmitter and the receiver is up to 4mMoreover the multipath gains are modeled as independentlog normally distributed random variables We assume thatperfect channel state information is available at the receiverAlso the feedback link has no delay and is error-free
10 International Journal of Antennas and Propagation
Empirical CCDF of T110
0
10minus1
10minus2
minus2 0 2
W = 1
W = 4
W = 8
(a)
100
10minus1
10minus2
minus04 minus02 0
Empirical CDF of T2
(b)
Empirical CCDF of (T1 + T2)10
0
10minus1
10minus2
minus1 minus05 0 05 1 15 2
W = 1
W = 4
W = 8
(c)
Figure 4 Statistical distributions (note 1198792is independent of119882)
61 Evaluations of Peak-Power Distribution In Figure 5 weplot the CCDFs of the peak power of time-domain signalsThe analytical curves are based on (16) (17) and (19) Mean-while the simulation curves are empirical CCDF values Thesimulation result confirms that a system with the proposedallocation scheme offers a better CCDF performance than itscounterpart As expected the occurrence of high peak poweris significantly reduced when the peak-power reductionalgorithm is implemented Also it can be seen that theimprovement associated with this algorithm is reduced withincreasing 119882 In other words a very large value of 119882 whilerequiring higher complexity in terms on the number of IFFToperations results in a marginal improvement Thus it isreasonable to choose a relatively small value for 119882 (eg119882 = 4) It is also worth noting that the analytical curvesare relatively close to the simulation curves The small gapsexist due to the fact that the assumption of independentsamples |119904
119894(119899)| to obtain (13) does not strictly hold as we have
sum119870minus1
119899=0|119904119894(119899)|2 = 1205902119870
119894by Parsevalrsquos relation [24]
62 Evaluations of Power Efficiency of HPAs Figure 6 com-pares the CCDFs of the power efficiency achieved in theproposed and conventional systems It can be seen that theprobability of power efficiency being large highly likely occursin the proposed system compared to its counterpart Also
the simulation results agree well with the analytical resultsderived in (23) and (29) In Table 3 we compare the averagepower efficiencies Here the analytical values are obtainedaccording to (26) (27) and (30) Meanwhile the simulationvalues are empirical values based on the original definitionof the drain efficiency in (21) Also these values are averagedover the fading channel realizations It can be seen that thederived expressions approximate well the achieved powerefficiencies Table 3 also provides relative improvements ofthe power efficiencies achieved in the proposed system overthe conventional system Here only 120578
PE (Simulation) valuesare used for calculating these improvements It is clear thatthe proposed system could achieve a significant improvementin terms of average power efficiency
63 Evaluations of Capacity and Energy Efficiency Figure 7shows the system capacity inMbps (ie the normalized valuein (6) is scaled upwith the system bandwidth) versus the SNRvalue of 12059021205902
119899 It is clear that a systemwith the proposed allo-
cation scheme achieves a higher capacity than its counterpartThis agrees with the analysis in Section 51 that the changein capacity Δ119862 is positive In Figure 8 we plot the energyefficiency (MbitsJoule) versus spectral efficiency (MbpsHz)This figure is obtained based on (42) and (43) when varying119875dc Other parameters are 119875RF = 100mW 119875sp = 10mW and
International Journal of Antennas and Propagation 11
Table 3 A comparison of average power efficiencies
Imbalance Proposed (119882 = 1) Proposed (119882 = 4) Proposed (119882 = 8)120578PE (Simulation) 00697 00768 00894 00942
120578PE (Analysis) 00691 00757 00892 00943
Improvement120578PEproposed minus 120578
PEimbalance
120578PEimbalance
mdash 1019 2826 3515
1 2 3 4 5 6 7 8 9
100
10minus1
10minus2
10minus3
Peak power P0
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Pr (P
gtP0)
Figure 5 Comparison of CCDFs of the peak powers
002 004 006 008 01 012 014Power efficiency
CCD
F
100
10minus1
10minus2
10minus3
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Figure 6 Comparison of CCDFs of the power efficiencies
4500
4000
3500
3000
2500
2000
1500
1000
Ergo
dic c
apac
ity (M
bps)
2 4 6 8 10 12 14
SNR (dB)
3300
3200
3100
3000
2900
2800
97 98 99 10 101
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 7 Comparison of the ergodic capacities
12059021205902119899= 15 dB As expected the improvement in the power
efficiency of HPAs results in an improved energy efficiencyIn addition it can be observed that there exists an energyefficiency-spectral efficiency tradeoff in the systems Thistradeoff clearly needs to be taken into consideration whendesigning energy-efficient per-subcarrier antenna selectionbased OFDM wireless systems
7 Conclusions
In this paper a per-subcarrier antenna subset selectionMIMO-OFDM system with linear scaling has been investi-gated from an energy-efficiency perspective We have shownthat an imbalance allocation of data subcarriers associatedwith the conventional selection scheme affects the power effi-ciency of HPAs as well as the energy-efficiency of the wholesystem To deliver the maximum overall power efficiencywe have proposed the two-step strategy consisting of equalallocation data subcarriers across antennas and peak-powerreduction It has been proved from the power-efficiency view-point that the proposed allocation scheme outperforms theconventional scheme We have also derived the expressionsfor measuring the average power efficiency Moreover theimprovements in terms of capacity and energy efficiency
12 International Journal of Antennas and Propagation
0 2 4 6 8 10400
600
800
1000
1200
1400
1600
Spectral efficiency (MbpsHz)
Ener
gy effi
cien
cy (M
bits
J)
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 8 Energy efficiency versus spectral efficiency
resulting from the improved power efficiency have beenanalyzed The analytical results are validated by simulationresults The simulation result also shows that the systemwith the proposed allocation scheme could achieve a betterefficiency efficiency-spectral energy tradeoff compared to itscounterpart
Appendices
A Proof of Theorem 1
Let us consider a function 119891(120592) = 1 minus 119890minus1198750120592 0 lt 120592 le 1205902maxwhere 1205902max = max1205902
1198701 12059021198702
1205902119870119899119879
The second derivativeof this function is
11989110158401015840(120592) =
21198750120592 minus 11987520
1205924119890minus1198750120592 (A1)
From a HPAsrsquo viewpoint it is of interest to consider thesituation when the peak power across antennas 119875
0is large
Thus we consider the scenarios of 1198750
gt 21205902max where 1205902maxis the maximum average power across antennas Under thesesituations it is clear that 11989110158401015840(120592) lt 0 forall120592 isin (0 1205902max] Hencethe function 119891(120592) is concave By applying Jensenrsquos inequalitywe obtain the following inequality
1
119899119879
119899119879
sum119894=1
119891 (1205902
119870119894) le 119891(
1
119899119879
119899119879
sum119894=1
1205902
119870119894)
= 119891(1
119899119879
119899119879
sum119894=1
1205902
119870) = 119891 (120590
2
119870)
(A2)
where the equality comes from the fact that sum119899119879
119894=11205902119870119894
=
sum119899119879
119894=11205902119870
= 1198991198631205902 Expression (A2) can be rewritten as119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le 119899119879(1 minus 119890
minus11987501205902
119870) (A3)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879
On the other hand by applying the arithmetic-geometricmean inequality and note that (1 minus 119890
minus119909) gt 0 forall119909 gt 0 we have
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1
119899119879
119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ))
119899119879
(A4)
Note that the equality in (A4) holds if and only if 1205902119870119894
= 1205902119870
forall119894 = 1 119899119879
Combining (A3) and (A4) results in
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1 minus 119890minus1198750120590
2
119870)119899119879
(A5)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879 Thus we
get the following desired inequality
1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
ge 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(A6)
or
CCDF119875imbalance (1198750) ge CCDF119875balance (1198750) (A7)
This completes the proof
B Upper Bound of an ExpectedValue of Cost Penalty
In this appendix we derive an upper bound of the expectedvalue of Δ
119896 It can be seen from (5) that among all pos-
sible matrices H119896 the matrix H
119896with the highest value of
log2(det(Ω
119896))Ω119896
= Ω(H119896) will be selected as the effective
channel matrix for the 119896th subcarrier in the conventionalscheme Meanwhile in the proposed scheme due to thebalance constraint the effective channel matrix associatedwith the kth subcarrier is not necessarily the one with thehighest log
2(det(Ω
119896)) that is log
2(det(Ω
119896)) le log
2(det(Ω
119896))
Thus the expected value of Δ119896can be computed by using
order statistics In particular an upper bound on the expecteddifference of two-order statistics the Γth and 120574th 1 le 120574 lt Γis given by [30]
119864 Δ119896 = 119864 log
2(det (Ω
119896)) minus 119864 log
2(det (Ω
119896))
le 120590119862radic
Γ (120574 + 1)
120574
(B1)
where 1205902119862is the variance of log
2(det(Ω
119896)) that is assumed to
be the same for all possible matricesH119896
On the other hand suppose that the entries of the 119899119877times119899119879
matrixH119896are iid complex Gaussian random variables with
zero mean and unit variance then for any effective channelmatrix H
119896 Ω119896is a complex Wishart matrix It follows from
[25] that the variance of log2(det(Ω
119896)) can be expressed as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1205951015840(119902 minus 119898 + 1) (B2)
International Journal of Antennas and Propagation 13
where 119901 = min(119899119863 119899119877) 119902 = max(119899
119863 119899119877) and 1205951015840(119909) =
suminfin
120593=11(120593 + 119909 minus 1)
2 is the first derivative of the digammafunction By approximating 1205951015840(119909) asymp 1119909 [25] the simplerexpression for 1205902
119862in (B2) is given as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1
119902 minus 119898 + 1 (B3)
Substitute (B3) into (B1) we finally arrive at
119864 Δ119896 le log
2(119890)radic(
119901
sum119898=1
1
119902 minus 119898 + 1) times
Γ (120574 + 1)
120574 (B4)
Conflict of Interests
The authors declare that there is no conflict of interestsregarding the publication of this paper
References
[1] L M Correia D Zeller O Blume et al ldquoChallenges andenabling technologies for energy aware mobile radio networksrdquoIEEECommunicationsMagazine vol 48 no 11 pp 66ndash72 2010
[2] Z Hasan H Boostanimehr and V K Bhargava ldquoGreen cellularnetworks a survey some research issues and challengesrdquo IEEECommunications Surveys and Tutorials vol 13 no 4 pp 524ndash540 2011
[3] J Joung C K Ho and S Sun ldquoGreenwireless communicationsa power amplifier perspectiverdquo in Proceedings of the 4th Asia-Pacific Signal and Information Processing Association AnnualSummit and Conference (APSIPA ASC rsquo12) pp 1ndash8 December2012
[4] G L Stuber J R Barry S W Mclaughlin Y E Li M AIngram and T G Pratt ldquoBroadband MIMO-OFDM wirelesscommunicationsrdquoProceedings of the IEEE vol 92 no 2 pp 271ndash294 2004
[5] H Bolcskei D Gesbert and A J Paulraj ldquoOn the capacity ofOFDM-based spatial multiplexing systemsrdquo IEEE Transactionson Communications vol 50 no 2 pp 225ndash234 2002
[6] V Tarokh N Seshadri and A R Calderbank ldquoSpace-timecodes for high data rate wireless communication performancecriterion and code constructionrdquo IEEE Transactions on Infor-mation Theory vol 44 no 2 pp 744ndash765 1998
[7] C M Vithanage M Sandell J P Coon and Y Wang ldquoPrecod-ing in OFDM-based multi-antenna ultra-wideband systemsrdquoIEEE Communications Magazine vol 47 no 1 pp 41ndash47 2009
[8] Z Tang H Suzuki and I B Collings ldquoPerformance of antennaselection forMIMO-OFDMsystems based onmeasured indoorcorrelated frequency selective channelsrdquo in Proceedings of theAustralian Telecommunication Networks and Applications Con-ference pp 435ndash439 December 2006
[9] H Zhang and R U Nabar ldquoTransmit antenna selection inMIMO-OFDM systems bulk versus per-tone selectionrdquo inProceedings of the IEEE International Conference on Communi-cations (ICC rsquo08) pp 4371ndash4375 May 2008
[10] H Shi M Katayama T Yamazato H Okada and A OgawaldquoAn adaptive antenna selection scheme for transmit diversityin OFDM systemsrdquo in Proceedings of the IEEE 54th VehicularTechnology Conference (VTC rsquo01) pp 2168ndash2172 October 2001
[11] M Sandell and J P Coon ldquoPer-subcarrier antenna selectionwith power constraints in OFDM systemsrdquo IEEE Transactionson Wireless Communications vol 8 no 2 pp 673ndash677 2009
[12] N P Le F Safaei and L C Tran ldquoTransmit antenna subsetselection for high-rate MIMO-OFDM systems in the presenceof nonlinear power amplifiersrdquo EURASIP Journal on WirelessCommunications and Networking vol 2014 article 27 2014
[13] R PrasadOFDM for Wireless Communications Systems ArtechHouse 1st edition 2004
[14] T Jiang and Y Wu ldquoAn overview peak-to-average power ratioreduction techniques for OFDM signalsrdquo IEEE Transactions onBroadcasting vol 54 no 2 pp 257ndash268 2008
[15] H Ochiai ldquoPerformance analysis of peak power and band-limited OFDM system with linear scalingrdquo IEEE Transactionson Wireless Communications vol 2 no 5 pp 1055ndash1065 2003
[16] C Zhao R J Baxley and G T Zhou ldquoPeak-to-average powerratio and power efficiency considerations in MIMO-OFDMsystemsrdquo IEEE Communications Letters vol 12 no 4 pp 268ndash270 2008
[17] D Wulich and I Gutman ldquoImpact of linear power amplifier onpower loading in OFDM part I principlesrdquo in Proceedings ofthe IEEE 26th Convention of Electrical and Electronics Engineersin Israel (IEEEI rsquo10) pp 360ndash364 November 2010
[18] S Coleri M Ergen A Puri and A Bahai ldquoChannel estimationtechniques based on pilot arrangement in OFDM systemsrdquoIEEE Transactions on Broadcasting vol 48 no 3 pp 223ndash2292002
[19] R W Heath S Sandhu and A Paulraj ldquoAntenna selectionfor spatial multiplexing systems with linear receiversrdquo IEEECommunications Letters vol 5 no 4 pp 142ndash144 2001
[20] R Fletcher Practical Methods of Optimization John Willey ampSons 2nd edition 1987
[21] R W Bauml R F H Fischer and J B Huber ldquoReducingthe peak-to-average power ratio of multicarrier modulation byselected mappingrdquo Electronics Letters vol 32 no 22 pp 2056ndash2057 1996
[22] M Tan Z Latinovic and Y Bar-Ness ldquoSTBC MIMO-OFDMpeak-to-average power ratio reduction by cross-antenna rota-tion and inversionrdquo IEEE Communications Letters vol 9 no 7pp 592ndash594 2005
[23] K M Anstreicher ldquoLinear programming in O(n3lnnL) opera-tionsrdquo SIAM Journal on Optimization vol 9 no 4 pp 803ndash8121999
[24] J G Proakis Digital Communications McGraw Hill 4th edi-tion 2001
[25] O Oyman R U Nabar H Bolcskei and A J Paulraj ldquoChar-acterizing the statistical properties of mutual information inMIMO channelsrdquo IEEE Transactions on Signal Processing vol51 no 11 pp 2784ndash2795 2003
[26] S Cui A J Goldsmith and A Bahai ldquoEnergy-constrainedmodulation optimizationrdquo IEEE Transactions onWireless Com-munications vol 4 no 5 pp 2349ndash2360 2005
[27] R J Baxley and G T Zhou ldquoPower savings analysis of peak-to-average power ratio reduction in OFDMrdquo IEEE Transactions onConsumer Electronics vol 50 no 3 pp 792ndash797 2004
[28] A Batra et al Multiband OFDM Physical Layer SpecificationRelease 1 5 WiMedia Alliance 2009
[29] J Foerster et al ldquoChannel modeling sub-committee reportfinalrdquo IEEE P802 15-02490r1-SG3a 2003
[30] B C Arnold and R A Groeneveld ldquoBounds on expectationsof linear systematic statistics based on dependent samplesrdquoTheAnnals of Statistics vol 7 no 1 pp 220ndash223 1979
International Journal of
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RotatingMachinery
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
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Journal ofEngineeringVolume 2014
Submit your manuscripts athttpwwwhindawicom
VLSI Design
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Shock and Vibration
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Civil EngineeringAdvances in
Acoustics and VibrationAdvances in
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Electrical and Computer Engineering
Journal of
Advances inOptoElectronics
Hindawi Publishing Corporation httpwwwhindawicom
Volume 2014
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Modelling amp Simulation in EngineeringHindawi Publishing Corporation httpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Chemical EngineeringInternational Journal of Antennas and
Propagation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
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Navigation and Observation
International Journal of
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DistributedSensor Networks
International Journal of
8 International Journal of Antennas and Propagation
5 Analyses of Capacity and Energy Efficiency
It has been shown in (22) and (28) that the proposed systemcould achieve a better power efficiency of HPAs than itscounterpart Thus when the power 119875dc is fixed it is intuitivethat an increased average power efficiency results in anincreased average transmit power and in turn leads to anincrease in the achievable rate Moreover an increase in thedata rate under a constant consumption power will translateinto an improvement in energy efficiency The achievedcapacity and energy efficiency are now investigated in thissection
51 System Capacity We begin by rewriting the mutualinformation in (7) with respect to the average SNR valueof 120588 = 119875
1199051205902119899 where 119875
119905= 120572119899
1198631205902 = 120578
PE119899119879119875dc (cf (21))
The ergodic capacity is then calculated by averaging themutual information over the fading channel distributionthat is 119862(120588) = 119864H119868(120588H) From (6) and (7) the mutualinformation in the proposed and conventional systems canbe expressed respectively as
119868 (120588proposedH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
(31)
119868 (120588imbalanceH)
=1
119870
119870minus1
sum119896=0
log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(32)
where 120588proposed = 120578PEproposed119899119879119875dc120590
2
119899and 120588imbalance =
120578PEimbalance119899119879119875dc120590
2
119899 Here 120578
PEproposed = 120578
PEbalance+reduced if the
peak-power reduction algorithm is implemented otherwise120578PEproposed = 120578
PEbalance Also H119896 in (31) denotes the effective
channel matrix on the 119896th subcarrier in the proposed systemwhich is obtainedwhen solving the problem in (8)This chan-nel matrix is generally different from the effective channelmatrix H
119896in the conventional system because the selected
antenna subset may be differentThe difference in the mutualinformation between the two systems can be now calculatedas
Δ119868 = 119868 (120588proposedH) minus 119868 (120588imbalanceH) =1
119870
119870minus1
sum119896=0
Δ119868119896 (33)
where
Δ119868119896= log2(det(I
119899119877+
120588proposed
119899119863
H119896H119867119896))
minus log2(det(I
119899119877+
120588imbalance119899119863
H119896H119867119896))
(34)
For analytical simplicity we focus on the high-SNRregime At the high SNR the mutual information at the 119896thsubcarrier can be approximated as [25]
119868119896= log2(det(
120588
119899119863
Ω119896)) (35)
where
Ω119896= Ω (H
119896) =
H119896H119867119896 119899119877le 119899119863
H119867119896H119896 119899119877gt 119899119863
(36)
Thus the difference in the mutual information can berewritten as
Δ119868 =1
119870
119870minus1
sum119896=0
(log2(det(
120588proposed
119899119863
Ω119896))
minuslog2(det(
120588imbalance119899119863
Ω119896)))
= 119901log2
120578PEproposed
120578PEimbalance
minus1
119870
119870minus1
sum119896=0
Δ119896= 1198791+ 1198792
(37)
where 119901 = min(119899119863 119899119877)Ω119896= Ω(H
119896) and
Δ119896= log2(det (Ω
119896)) minus log
2(det (Ω
119896)) (38)
is the loss in the mutual information associated with the 119896thsubcarrier due to the constrained allocation Note that if bothsystems have the same selected antenna subset at the 119896thsubcarrier then Δ
119896= 0 otherwise Δ
119896gt 0Thus the total loss
in the mutual information Δ = (1119870)sum119870minus1
119896=0Δ119896gt 0
We have some important observations with respect to thevalue of Δ119868 in (37)
(i)The change in mutual information Δ119868 comes fromtwo sources The first source 119879
1is a benefit in mutual
information due to the improvement in the powerefficiency of HPAs The second source 119879
2is a penalty
that incurs because the chosen effective channelmatrices in the proposed system are different from theones in the conventional system(ii) For each channel realization thematrixH
119896is fixed
and the first term 1198791in (37) is a constant Thus the
value of Δ119868 depends on how the effective channelmatrix H
119896is selected in the constrained selection
scheme From this observation it is clear that tomake the value Δ119868 become as positive as possiblethe constrained selection method should result inthe cost penalty Δ as small as possible We note thatthe formulated optimization in (8) could achieve theminimum possible value of the total cost Hence it isexpected that the constrained selection scheme basedon linear optimization will guarantee the maximumachievable value of Δ119868 In addition to have an insightinto the cost penalty we derive the upper bound ofthe expected value of the cost penalty in Appendix BBased on the obtained bound it is observed that forfixed values of 119899
119879and 119899
119863 the cost penalty becomes
smaller with an increasing value of 119902 = max(119899119863 119899119877)
International Journal of Antennas and Propagation 9
(iii) As Δ gt 0 the upper bound of the capacityimprovement can be given as
Δ119862 = 119864H Δ119868 le 119901log2119864H
120578PEproposed
120578PEimbalance
(39)
In (39) we have used Jensenrsquos inequality of119864log(119909) le log(119864119909) as log(119909) is a concavefunction Based on this bound we could estimatethe maximum improvement in capacity that couldbe realized in the proposed system compared to itscounterpart
It is now necessary to evaluate the change in capacitythat is Δ119862 We note that although the distribution of themutual information at high SNRs can be well approximatedby a Gaussian distribution [25] it is still challenging toperform a mathematical evaluation of Δ119862 from a statisticalviewpoint This is mainly due to the fact that the two termsin (37) are complicated dependent random variables Thuswe perform a numerical evaluation of Δ119862 instead Figure 4plots the empirical CCDF of 119879
1 CDF of 119879
2 and CCDF
of Δ119868 In the figure ldquo119882 = 1rdquo stands for the case in whichonly Step 1 in Section 31 is implemented The results areobtained in the systems with 119899
119879= 4 119899
119863= 2 119899
119877= 2 119870= 128
and are averaged over 103 channel realizations Details aboutother simulation parameters are described in Section 6 Thenumerical results confirm that 119879
1gt 0 and 119879
2lt 0 Moreover
as shown in Figure 4(c) Δ119868 is always positive when the peak-power reduction algorithm is implemented (ie 119882= 4 and119882 = 8) For the case of 119882 = 1 the probability of ΔI beingpositive is significant Therefore the proposed system attainsa better ergodic capacity than that in the conventional systemThe achieved capacities in the considered systems will beprovided in Section 6
52 Energy Efficiency In this subsection we further exam-ine the efficacy of the proposed system from an energy-efficiency (EE) perspective Normalized energy efficiency(bitsHzJoule) in MIMO-OFDM systems can be defined as[3 26]
120578EE
=119862 (120588)
119875total (40)
where 119862(120588) is the achievable rate and the total powerconsumption per-subchannel is 119875total = 119899
119879119875dc + 119899
119879119875RF + 119875sp
where 119875RF is the RF power consumption in each transmitbranch excluding the associatedHPA and119875sp is the basebandprocessing power consumption It can be seen from (40)that given a fixed value of 119875total a comparison of energyefficiency achieved in the two systems is based on the capacitycomparison that has been analyzed in Section 51We are nowinterested in evaluating a useful metric of energy efficiency-spectral efficiency performance Recall that the average SNR120588 is given as 120588 = 119875
1199051205902119899= 120578
PE119899119879119875dc1205902
119899 Thus we can rewrite
the energy efficiency in (40) as a function of 119875dc as
120578EE
(119875dc) =119862 (120578
PE119899119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
(41)
Table 2 Simulation parameters
Parameter ValueBandwidth 528MHzFFT size 128Number of samples in zero-padded suffix 37Modulation scheme 4-QAMIEEE 802153a channel model CM1
The energy efficiency of the proposed and conventionalsystems can now be respectively expressed as
120578EEproposed (119875dc) =
119862proposed (120578PEproposed 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEproposed 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(42)
120578EEimbalance (119875dc) =
119862imbalance (120578PEimbalance 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEimbalance 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(43)
Similarly to the case of capacity we compare the energyefficiency achieved in the two systems by means of numericalresults in the next section Note that the calculation of energyefficiency in the proposed system (ie (42)) has assumed thata reduction in spectral efficiency due to the side informationas well as additional processing power required for the peak-power reduction algorithm is negligible In fact a reductionin spectral efficiency is very small For example in a systemwith 16-QAM FFT size of 128 119899
119863= 2 and 119882= 4 (ie 2 bits
are needed for side information) a spectral efficiency lossis 2 bits(128 times 4 times 2 + 2) bits = 019 Also it was shownin [27] that the additional power cost when implementingSLM schemes is minuscule Thus the proposed peak-powerreduction algorithm in Section 32 which is a SLM-basedscheme requires a small additional power cost
6 Numerical Results
In this section we provide numerical results to validatethe analyses mentioned in the previous sections as wellas demonstrate the effectiveness of the proposed allocationscheme over its counterpart A MIMO-OFDM system with119899119879= 4 119899
119863= 2 and 119899
119877= 2 is considered in our simulations
The system parameters are listed in Table 2These parametersare chosen based on the legacy WiMedia MB-OFDM UWB(Multiband-OFDM UWB) standard [28] Also the channelCM1 defined in the IEEE 802153a channel model [29] isbased on ameasurement of a line-of-sight scenario where thedistance between the transmitter and the receiver is up to 4mMoreover the multipath gains are modeled as independentlog normally distributed random variables We assume thatperfect channel state information is available at the receiverAlso the feedback link has no delay and is error-free
10 International Journal of Antennas and Propagation
Empirical CCDF of T110
0
10minus1
10minus2
minus2 0 2
W = 1
W = 4
W = 8
(a)
100
10minus1
10minus2
minus04 minus02 0
Empirical CDF of T2
(b)
Empirical CCDF of (T1 + T2)10
0
10minus1
10minus2
minus1 minus05 0 05 1 15 2
W = 1
W = 4
W = 8
(c)
Figure 4 Statistical distributions (note 1198792is independent of119882)
61 Evaluations of Peak-Power Distribution In Figure 5 weplot the CCDFs of the peak power of time-domain signalsThe analytical curves are based on (16) (17) and (19) Mean-while the simulation curves are empirical CCDF values Thesimulation result confirms that a system with the proposedallocation scheme offers a better CCDF performance than itscounterpart As expected the occurrence of high peak poweris significantly reduced when the peak-power reductionalgorithm is implemented Also it can be seen that theimprovement associated with this algorithm is reduced withincreasing 119882 In other words a very large value of 119882 whilerequiring higher complexity in terms on the number of IFFToperations results in a marginal improvement Thus it isreasonable to choose a relatively small value for 119882 (eg119882 = 4) It is also worth noting that the analytical curvesare relatively close to the simulation curves The small gapsexist due to the fact that the assumption of independentsamples |119904
119894(119899)| to obtain (13) does not strictly hold as we have
sum119870minus1
119899=0|119904119894(119899)|2 = 1205902119870
119894by Parsevalrsquos relation [24]
62 Evaluations of Power Efficiency of HPAs Figure 6 com-pares the CCDFs of the power efficiency achieved in theproposed and conventional systems It can be seen that theprobability of power efficiency being large highly likely occursin the proposed system compared to its counterpart Also
the simulation results agree well with the analytical resultsderived in (23) and (29) In Table 3 we compare the averagepower efficiencies Here the analytical values are obtainedaccording to (26) (27) and (30) Meanwhile the simulationvalues are empirical values based on the original definitionof the drain efficiency in (21) Also these values are averagedover the fading channel realizations It can be seen that thederived expressions approximate well the achieved powerefficiencies Table 3 also provides relative improvements ofthe power efficiencies achieved in the proposed system overthe conventional system Here only 120578
PE (Simulation) valuesare used for calculating these improvements It is clear thatthe proposed system could achieve a significant improvementin terms of average power efficiency
63 Evaluations of Capacity and Energy Efficiency Figure 7shows the system capacity inMbps (ie the normalized valuein (6) is scaled upwith the system bandwidth) versus the SNRvalue of 12059021205902
119899 It is clear that a systemwith the proposed allo-
cation scheme achieves a higher capacity than its counterpartThis agrees with the analysis in Section 51 that the changein capacity Δ119862 is positive In Figure 8 we plot the energyefficiency (MbitsJoule) versus spectral efficiency (MbpsHz)This figure is obtained based on (42) and (43) when varying119875dc Other parameters are 119875RF = 100mW 119875sp = 10mW and
International Journal of Antennas and Propagation 11
Table 3 A comparison of average power efficiencies
Imbalance Proposed (119882 = 1) Proposed (119882 = 4) Proposed (119882 = 8)120578PE (Simulation) 00697 00768 00894 00942
120578PE (Analysis) 00691 00757 00892 00943
Improvement120578PEproposed minus 120578
PEimbalance
120578PEimbalance
mdash 1019 2826 3515
1 2 3 4 5 6 7 8 9
100
10minus1
10minus2
10minus3
Peak power P0
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Pr (P
gtP0)
Figure 5 Comparison of CCDFs of the peak powers
002 004 006 008 01 012 014Power efficiency
CCD
F
100
10minus1
10minus2
10minus3
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Figure 6 Comparison of CCDFs of the power efficiencies
4500
4000
3500
3000
2500
2000
1500
1000
Ergo
dic c
apac
ity (M
bps)
2 4 6 8 10 12 14
SNR (dB)
3300
3200
3100
3000
2900
2800
97 98 99 10 101
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 7 Comparison of the ergodic capacities
12059021205902119899= 15 dB As expected the improvement in the power
efficiency of HPAs results in an improved energy efficiencyIn addition it can be observed that there exists an energyefficiency-spectral efficiency tradeoff in the systems Thistradeoff clearly needs to be taken into consideration whendesigning energy-efficient per-subcarrier antenna selectionbased OFDM wireless systems
7 Conclusions
In this paper a per-subcarrier antenna subset selectionMIMO-OFDM system with linear scaling has been investi-gated from an energy-efficiency perspective We have shownthat an imbalance allocation of data subcarriers associatedwith the conventional selection scheme affects the power effi-ciency of HPAs as well as the energy-efficiency of the wholesystem To deliver the maximum overall power efficiencywe have proposed the two-step strategy consisting of equalallocation data subcarriers across antennas and peak-powerreduction It has been proved from the power-efficiency view-point that the proposed allocation scheme outperforms theconventional scheme We have also derived the expressionsfor measuring the average power efficiency Moreover theimprovements in terms of capacity and energy efficiency
12 International Journal of Antennas and Propagation
0 2 4 6 8 10400
600
800
1000
1200
1400
1600
Spectral efficiency (MbpsHz)
Ener
gy effi
cien
cy (M
bits
J)
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 8 Energy efficiency versus spectral efficiency
resulting from the improved power efficiency have beenanalyzed The analytical results are validated by simulationresults The simulation result also shows that the systemwith the proposed allocation scheme could achieve a betterefficiency efficiency-spectral energy tradeoff compared to itscounterpart
Appendices
A Proof of Theorem 1
Let us consider a function 119891(120592) = 1 minus 119890minus1198750120592 0 lt 120592 le 1205902maxwhere 1205902max = max1205902
1198701 12059021198702
1205902119870119899119879
The second derivativeof this function is
11989110158401015840(120592) =
21198750120592 minus 11987520
1205924119890minus1198750120592 (A1)
From a HPAsrsquo viewpoint it is of interest to consider thesituation when the peak power across antennas 119875
0is large
Thus we consider the scenarios of 1198750
gt 21205902max where 1205902maxis the maximum average power across antennas Under thesesituations it is clear that 11989110158401015840(120592) lt 0 forall120592 isin (0 1205902max] Hencethe function 119891(120592) is concave By applying Jensenrsquos inequalitywe obtain the following inequality
1
119899119879
119899119879
sum119894=1
119891 (1205902
119870119894) le 119891(
1
119899119879
119899119879
sum119894=1
1205902
119870119894)
= 119891(1
119899119879
119899119879
sum119894=1
1205902
119870) = 119891 (120590
2
119870)
(A2)
where the equality comes from the fact that sum119899119879
119894=11205902119870119894
=
sum119899119879
119894=11205902119870
= 1198991198631205902 Expression (A2) can be rewritten as119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le 119899119879(1 minus 119890
minus11987501205902
119870) (A3)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879
On the other hand by applying the arithmetic-geometricmean inequality and note that (1 minus 119890
minus119909) gt 0 forall119909 gt 0 we have
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1
119899119879
119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ))
119899119879
(A4)
Note that the equality in (A4) holds if and only if 1205902119870119894
= 1205902119870
forall119894 = 1 119899119879
Combining (A3) and (A4) results in
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1 minus 119890minus1198750120590
2
119870)119899119879
(A5)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879 Thus we
get the following desired inequality
1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
ge 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(A6)
or
CCDF119875imbalance (1198750) ge CCDF119875balance (1198750) (A7)
This completes the proof
B Upper Bound of an ExpectedValue of Cost Penalty
In this appendix we derive an upper bound of the expectedvalue of Δ
119896 It can be seen from (5) that among all pos-
sible matrices H119896 the matrix H
119896with the highest value of
log2(det(Ω
119896))Ω119896
= Ω(H119896) will be selected as the effective
channel matrix for the 119896th subcarrier in the conventionalscheme Meanwhile in the proposed scheme due to thebalance constraint the effective channel matrix associatedwith the kth subcarrier is not necessarily the one with thehighest log
2(det(Ω
119896)) that is log
2(det(Ω
119896)) le log
2(det(Ω
119896))
Thus the expected value of Δ119896can be computed by using
order statistics In particular an upper bound on the expecteddifference of two-order statistics the Γth and 120574th 1 le 120574 lt Γis given by [30]
119864 Δ119896 = 119864 log
2(det (Ω
119896)) minus 119864 log
2(det (Ω
119896))
le 120590119862radic
Γ (120574 + 1)
120574
(B1)
where 1205902119862is the variance of log
2(det(Ω
119896)) that is assumed to
be the same for all possible matricesH119896
On the other hand suppose that the entries of the 119899119877times119899119879
matrixH119896are iid complex Gaussian random variables with
zero mean and unit variance then for any effective channelmatrix H
119896 Ω119896is a complex Wishart matrix It follows from
[25] that the variance of log2(det(Ω
119896)) can be expressed as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1205951015840(119902 minus 119898 + 1) (B2)
International Journal of Antennas and Propagation 13
where 119901 = min(119899119863 119899119877) 119902 = max(119899
119863 119899119877) and 1205951015840(119909) =
suminfin
120593=11(120593 + 119909 minus 1)
2 is the first derivative of the digammafunction By approximating 1205951015840(119909) asymp 1119909 [25] the simplerexpression for 1205902
119862in (B2) is given as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1
119902 minus 119898 + 1 (B3)
Substitute (B3) into (B1) we finally arrive at
119864 Δ119896 le log
2(119890)radic(
119901
sum119898=1
1
119902 minus 119898 + 1) times
Γ (120574 + 1)
120574 (B4)
Conflict of Interests
The authors declare that there is no conflict of interestsregarding the publication of this paper
References
[1] L M Correia D Zeller O Blume et al ldquoChallenges andenabling technologies for energy aware mobile radio networksrdquoIEEECommunicationsMagazine vol 48 no 11 pp 66ndash72 2010
[2] Z Hasan H Boostanimehr and V K Bhargava ldquoGreen cellularnetworks a survey some research issues and challengesrdquo IEEECommunications Surveys and Tutorials vol 13 no 4 pp 524ndash540 2011
[3] J Joung C K Ho and S Sun ldquoGreenwireless communicationsa power amplifier perspectiverdquo in Proceedings of the 4th Asia-Pacific Signal and Information Processing Association AnnualSummit and Conference (APSIPA ASC rsquo12) pp 1ndash8 December2012
[4] G L Stuber J R Barry S W Mclaughlin Y E Li M AIngram and T G Pratt ldquoBroadband MIMO-OFDM wirelesscommunicationsrdquoProceedings of the IEEE vol 92 no 2 pp 271ndash294 2004
[5] H Bolcskei D Gesbert and A J Paulraj ldquoOn the capacity ofOFDM-based spatial multiplexing systemsrdquo IEEE Transactionson Communications vol 50 no 2 pp 225ndash234 2002
[6] V Tarokh N Seshadri and A R Calderbank ldquoSpace-timecodes for high data rate wireless communication performancecriterion and code constructionrdquo IEEE Transactions on Infor-mation Theory vol 44 no 2 pp 744ndash765 1998
[7] C M Vithanage M Sandell J P Coon and Y Wang ldquoPrecod-ing in OFDM-based multi-antenna ultra-wideband systemsrdquoIEEE Communications Magazine vol 47 no 1 pp 41ndash47 2009
[8] Z Tang H Suzuki and I B Collings ldquoPerformance of antennaselection forMIMO-OFDMsystems based onmeasured indoorcorrelated frequency selective channelsrdquo in Proceedings of theAustralian Telecommunication Networks and Applications Con-ference pp 435ndash439 December 2006
[9] H Zhang and R U Nabar ldquoTransmit antenna selection inMIMO-OFDM systems bulk versus per-tone selectionrdquo inProceedings of the IEEE International Conference on Communi-cations (ICC rsquo08) pp 4371ndash4375 May 2008
[10] H Shi M Katayama T Yamazato H Okada and A OgawaldquoAn adaptive antenna selection scheme for transmit diversityin OFDM systemsrdquo in Proceedings of the IEEE 54th VehicularTechnology Conference (VTC rsquo01) pp 2168ndash2172 October 2001
[11] M Sandell and J P Coon ldquoPer-subcarrier antenna selectionwith power constraints in OFDM systemsrdquo IEEE Transactionson Wireless Communications vol 8 no 2 pp 673ndash677 2009
[12] N P Le F Safaei and L C Tran ldquoTransmit antenna subsetselection for high-rate MIMO-OFDM systems in the presenceof nonlinear power amplifiersrdquo EURASIP Journal on WirelessCommunications and Networking vol 2014 article 27 2014
[13] R PrasadOFDM for Wireless Communications Systems ArtechHouse 1st edition 2004
[14] T Jiang and Y Wu ldquoAn overview peak-to-average power ratioreduction techniques for OFDM signalsrdquo IEEE Transactions onBroadcasting vol 54 no 2 pp 257ndash268 2008
[15] H Ochiai ldquoPerformance analysis of peak power and band-limited OFDM system with linear scalingrdquo IEEE Transactionson Wireless Communications vol 2 no 5 pp 1055ndash1065 2003
[16] C Zhao R J Baxley and G T Zhou ldquoPeak-to-average powerratio and power efficiency considerations in MIMO-OFDMsystemsrdquo IEEE Communications Letters vol 12 no 4 pp 268ndash270 2008
[17] D Wulich and I Gutman ldquoImpact of linear power amplifier onpower loading in OFDM part I principlesrdquo in Proceedings ofthe IEEE 26th Convention of Electrical and Electronics Engineersin Israel (IEEEI rsquo10) pp 360ndash364 November 2010
[18] S Coleri M Ergen A Puri and A Bahai ldquoChannel estimationtechniques based on pilot arrangement in OFDM systemsrdquoIEEE Transactions on Broadcasting vol 48 no 3 pp 223ndash2292002
[19] R W Heath S Sandhu and A Paulraj ldquoAntenna selectionfor spatial multiplexing systems with linear receiversrdquo IEEECommunications Letters vol 5 no 4 pp 142ndash144 2001
[20] R Fletcher Practical Methods of Optimization John Willey ampSons 2nd edition 1987
[21] R W Bauml R F H Fischer and J B Huber ldquoReducingthe peak-to-average power ratio of multicarrier modulation byselected mappingrdquo Electronics Letters vol 32 no 22 pp 2056ndash2057 1996
[22] M Tan Z Latinovic and Y Bar-Ness ldquoSTBC MIMO-OFDMpeak-to-average power ratio reduction by cross-antenna rota-tion and inversionrdquo IEEE Communications Letters vol 9 no 7pp 592ndash594 2005
[23] K M Anstreicher ldquoLinear programming in O(n3lnnL) opera-tionsrdquo SIAM Journal on Optimization vol 9 no 4 pp 803ndash8121999
[24] J G Proakis Digital Communications McGraw Hill 4th edi-tion 2001
[25] O Oyman R U Nabar H Bolcskei and A J Paulraj ldquoChar-acterizing the statistical properties of mutual information inMIMO channelsrdquo IEEE Transactions on Signal Processing vol51 no 11 pp 2784ndash2795 2003
[26] S Cui A J Goldsmith and A Bahai ldquoEnergy-constrainedmodulation optimizationrdquo IEEE Transactions onWireless Com-munications vol 4 no 5 pp 2349ndash2360 2005
[27] R J Baxley and G T Zhou ldquoPower savings analysis of peak-to-average power ratio reduction in OFDMrdquo IEEE Transactions onConsumer Electronics vol 50 no 3 pp 792ndash797 2004
[28] A Batra et al Multiband OFDM Physical Layer SpecificationRelease 1 5 WiMedia Alliance 2009
[29] J Foerster et al ldquoChannel modeling sub-committee reportfinalrdquo IEEE P802 15-02490r1-SG3a 2003
[30] B C Arnold and R A Groeneveld ldquoBounds on expectationsof linear systematic statistics based on dependent samplesrdquoTheAnnals of Statistics vol 7 no 1 pp 220ndash223 1979
International Journal of
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Electrical and Computer Engineering
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Modelling amp Simulation in EngineeringHindawi Publishing Corporation httpwwwhindawicom Volume 2014
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Chemical EngineeringInternational Journal of Antennas and
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DistributedSensor Networks
International Journal of
International Journal of Antennas and Propagation 9
(iii) As Δ gt 0 the upper bound of the capacityimprovement can be given as
Δ119862 = 119864H Δ119868 le 119901log2119864H
120578PEproposed
120578PEimbalance
(39)
In (39) we have used Jensenrsquos inequality of119864log(119909) le log(119864119909) as log(119909) is a concavefunction Based on this bound we could estimatethe maximum improvement in capacity that couldbe realized in the proposed system compared to itscounterpart
It is now necessary to evaluate the change in capacitythat is Δ119862 We note that although the distribution of themutual information at high SNRs can be well approximatedby a Gaussian distribution [25] it is still challenging toperform a mathematical evaluation of Δ119862 from a statisticalviewpoint This is mainly due to the fact that the two termsin (37) are complicated dependent random variables Thuswe perform a numerical evaluation of Δ119862 instead Figure 4plots the empirical CCDF of 119879
1 CDF of 119879
2 and CCDF
of Δ119868 In the figure ldquo119882 = 1rdquo stands for the case in whichonly Step 1 in Section 31 is implemented The results areobtained in the systems with 119899
119879= 4 119899
119863= 2 119899
119877= 2 119870= 128
and are averaged over 103 channel realizations Details aboutother simulation parameters are described in Section 6 Thenumerical results confirm that 119879
1gt 0 and 119879
2lt 0 Moreover
as shown in Figure 4(c) Δ119868 is always positive when the peak-power reduction algorithm is implemented (ie 119882= 4 and119882 = 8) For the case of 119882 = 1 the probability of ΔI beingpositive is significant Therefore the proposed system attainsa better ergodic capacity than that in the conventional systemThe achieved capacities in the considered systems will beprovided in Section 6
52 Energy Efficiency In this subsection we further exam-ine the efficacy of the proposed system from an energy-efficiency (EE) perspective Normalized energy efficiency(bitsHzJoule) in MIMO-OFDM systems can be defined as[3 26]
120578EE
=119862 (120588)
119875total (40)
where 119862(120588) is the achievable rate and the total powerconsumption per-subchannel is 119875total = 119899
119879119875dc + 119899
119879119875RF + 119875sp
where 119875RF is the RF power consumption in each transmitbranch excluding the associatedHPA and119875sp is the basebandprocessing power consumption It can be seen from (40)that given a fixed value of 119875total a comparison of energyefficiency achieved in the two systems is based on the capacitycomparison that has been analyzed in Section 51We are nowinterested in evaluating a useful metric of energy efficiency-spectral efficiency performance Recall that the average SNR120588 is given as 120588 = 119875
1199051205902119899= 120578
PE119899119879119875dc1205902
119899 Thus we can rewrite
the energy efficiency in (40) as a function of 119875dc as
120578EE
(119875dc) =119862 (120578
PE119899119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
(41)
Table 2 Simulation parameters
Parameter ValueBandwidth 528MHzFFT size 128Number of samples in zero-padded suffix 37Modulation scheme 4-QAMIEEE 802153a channel model CM1
The energy efficiency of the proposed and conventionalsystems can now be respectively expressed as
120578EEproposed (119875dc) =
119862proposed (120578PEproposed 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEproposed 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(42)
120578EEimbalance (119875dc) =
119862imbalance (120578PEimbalance 119899
119879119875dc1205902
119899)
119899119879119875dc + 119899
119879119875RF + 119875sp
=119864H 119868 (120578
PEimbalance 119899
119879119875dc1205902
119899H)
119899119879119875dc + 119899
119879119875RF + 119875sp
(43)
Similarly to the case of capacity we compare the energyefficiency achieved in the two systems by means of numericalresults in the next section Note that the calculation of energyefficiency in the proposed system (ie (42)) has assumed thata reduction in spectral efficiency due to the side informationas well as additional processing power required for the peak-power reduction algorithm is negligible In fact a reductionin spectral efficiency is very small For example in a systemwith 16-QAM FFT size of 128 119899
119863= 2 and 119882= 4 (ie 2 bits
are needed for side information) a spectral efficiency lossis 2 bits(128 times 4 times 2 + 2) bits = 019 Also it was shownin [27] that the additional power cost when implementingSLM schemes is minuscule Thus the proposed peak-powerreduction algorithm in Section 32 which is a SLM-basedscheme requires a small additional power cost
6 Numerical Results
In this section we provide numerical results to validatethe analyses mentioned in the previous sections as wellas demonstrate the effectiveness of the proposed allocationscheme over its counterpart A MIMO-OFDM system with119899119879= 4 119899
119863= 2 and 119899
119877= 2 is considered in our simulations
The system parameters are listed in Table 2These parametersare chosen based on the legacy WiMedia MB-OFDM UWB(Multiband-OFDM UWB) standard [28] Also the channelCM1 defined in the IEEE 802153a channel model [29] isbased on ameasurement of a line-of-sight scenario where thedistance between the transmitter and the receiver is up to 4mMoreover the multipath gains are modeled as independentlog normally distributed random variables We assume thatperfect channel state information is available at the receiverAlso the feedback link has no delay and is error-free
10 International Journal of Antennas and Propagation
Empirical CCDF of T110
0
10minus1
10minus2
minus2 0 2
W = 1
W = 4
W = 8
(a)
100
10minus1
10minus2
minus04 minus02 0
Empirical CDF of T2
(b)
Empirical CCDF of (T1 + T2)10
0
10minus1
10minus2
minus1 minus05 0 05 1 15 2
W = 1
W = 4
W = 8
(c)
Figure 4 Statistical distributions (note 1198792is independent of119882)
61 Evaluations of Peak-Power Distribution In Figure 5 weplot the CCDFs of the peak power of time-domain signalsThe analytical curves are based on (16) (17) and (19) Mean-while the simulation curves are empirical CCDF values Thesimulation result confirms that a system with the proposedallocation scheme offers a better CCDF performance than itscounterpart As expected the occurrence of high peak poweris significantly reduced when the peak-power reductionalgorithm is implemented Also it can be seen that theimprovement associated with this algorithm is reduced withincreasing 119882 In other words a very large value of 119882 whilerequiring higher complexity in terms on the number of IFFToperations results in a marginal improvement Thus it isreasonable to choose a relatively small value for 119882 (eg119882 = 4) It is also worth noting that the analytical curvesare relatively close to the simulation curves The small gapsexist due to the fact that the assumption of independentsamples |119904
119894(119899)| to obtain (13) does not strictly hold as we have
sum119870minus1
119899=0|119904119894(119899)|2 = 1205902119870
119894by Parsevalrsquos relation [24]
62 Evaluations of Power Efficiency of HPAs Figure 6 com-pares the CCDFs of the power efficiency achieved in theproposed and conventional systems It can be seen that theprobability of power efficiency being large highly likely occursin the proposed system compared to its counterpart Also
the simulation results agree well with the analytical resultsderived in (23) and (29) In Table 3 we compare the averagepower efficiencies Here the analytical values are obtainedaccording to (26) (27) and (30) Meanwhile the simulationvalues are empirical values based on the original definitionof the drain efficiency in (21) Also these values are averagedover the fading channel realizations It can be seen that thederived expressions approximate well the achieved powerefficiencies Table 3 also provides relative improvements ofthe power efficiencies achieved in the proposed system overthe conventional system Here only 120578
PE (Simulation) valuesare used for calculating these improvements It is clear thatthe proposed system could achieve a significant improvementin terms of average power efficiency
63 Evaluations of Capacity and Energy Efficiency Figure 7shows the system capacity inMbps (ie the normalized valuein (6) is scaled upwith the system bandwidth) versus the SNRvalue of 12059021205902
119899 It is clear that a systemwith the proposed allo-
cation scheme achieves a higher capacity than its counterpartThis agrees with the analysis in Section 51 that the changein capacity Δ119862 is positive In Figure 8 we plot the energyefficiency (MbitsJoule) versus spectral efficiency (MbpsHz)This figure is obtained based on (42) and (43) when varying119875dc Other parameters are 119875RF = 100mW 119875sp = 10mW and
International Journal of Antennas and Propagation 11
Table 3 A comparison of average power efficiencies
Imbalance Proposed (119882 = 1) Proposed (119882 = 4) Proposed (119882 = 8)120578PE (Simulation) 00697 00768 00894 00942
120578PE (Analysis) 00691 00757 00892 00943
Improvement120578PEproposed minus 120578
PEimbalance
120578PEimbalance
mdash 1019 2826 3515
1 2 3 4 5 6 7 8 9
100
10minus1
10minus2
10minus3
Peak power P0
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Pr (P
gtP0)
Figure 5 Comparison of CCDFs of the peak powers
002 004 006 008 01 012 014Power efficiency
CCD
F
100
10minus1
10minus2
10minus3
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Figure 6 Comparison of CCDFs of the power efficiencies
4500
4000
3500
3000
2500
2000
1500
1000
Ergo
dic c
apac
ity (M
bps)
2 4 6 8 10 12 14
SNR (dB)
3300
3200
3100
3000
2900
2800
97 98 99 10 101
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 7 Comparison of the ergodic capacities
12059021205902119899= 15 dB As expected the improvement in the power
efficiency of HPAs results in an improved energy efficiencyIn addition it can be observed that there exists an energyefficiency-spectral efficiency tradeoff in the systems Thistradeoff clearly needs to be taken into consideration whendesigning energy-efficient per-subcarrier antenna selectionbased OFDM wireless systems
7 Conclusions
In this paper a per-subcarrier antenna subset selectionMIMO-OFDM system with linear scaling has been investi-gated from an energy-efficiency perspective We have shownthat an imbalance allocation of data subcarriers associatedwith the conventional selection scheme affects the power effi-ciency of HPAs as well as the energy-efficiency of the wholesystem To deliver the maximum overall power efficiencywe have proposed the two-step strategy consisting of equalallocation data subcarriers across antennas and peak-powerreduction It has been proved from the power-efficiency view-point that the proposed allocation scheme outperforms theconventional scheme We have also derived the expressionsfor measuring the average power efficiency Moreover theimprovements in terms of capacity and energy efficiency
12 International Journal of Antennas and Propagation
0 2 4 6 8 10400
600
800
1000
1200
1400
1600
Spectral efficiency (MbpsHz)
Ener
gy effi
cien
cy (M
bits
J)
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 8 Energy efficiency versus spectral efficiency
resulting from the improved power efficiency have beenanalyzed The analytical results are validated by simulationresults The simulation result also shows that the systemwith the proposed allocation scheme could achieve a betterefficiency efficiency-spectral energy tradeoff compared to itscounterpart
Appendices
A Proof of Theorem 1
Let us consider a function 119891(120592) = 1 minus 119890minus1198750120592 0 lt 120592 le 1205902maxwhere 1205902max = max1205902
1198701 12059021198702
1205902119870119899119879
The second derivativeof this function is
11989110158401015840(120592) =
21198750120592 minus 11987520
1205924119890minus1198750120592 (A1)
From a HPAsrsquo viewpoint it is of interest to consider thesituation when the peak power across antennas 119875
0is large
Thus we consider the scenarios of 1198750
gt 21205902max where 1205902maxis the maximum average power across antennas Under thesesituations it is clear that 11989110158401015840(120592) lt 0 forall120592 isin (0 1205902max] Hencethe function 119891(120592) is concave By applying Jensenrsquos inequalitywe obtain the following inequality
1
119899119879
119899119879
sum119894=1
119891 (1205902
119870119894) le 119891(
1
119899119879
119899119879
sum119894=1
1205902
119870119894)
= 119891(1
119899119879
119899119879
sum119894=1
1205902
119870) = 119891 (120590
2
119870)
(A2)
where the equality comes from the fact that sum119899119879
119894=11205902119870119894
=
sum119899119879
119894=11205902119870
= 1198991198631205902 Expression (A2) can be rewritten as119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le 119899119879(1 minus 119890
minus11987501205902
119870) (A3)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879
On the other hand by applying the arithmetic-geometricmean inequality and note that (1 minus 119890
minus119909) gt 0 forall119909 gt 0 we have
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1
119899119879
119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ))
119899119879
(A4)
Note that the equality in (A4) holds if and only if 1205902119870119894
= 1205902119870
forall119894 = 1 119899119879
Combining (A3) and (A4) results in
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1 minus 119890minus1198750120590
2
119870)119899119879
(A5)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879 Thus we
get the following desired inequality
1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
ge 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(A6)
or
CCDF119875imbalance (1198750) ge CCDF119875balance (1198750) (A7)
This completes the proof
B Upper Bound of an ExpectedValue of Cost Penalty
In this appendix we derive an upper bound of the expectedvalue of Δ
119896 It can be seen from (5) that among all pos-
sible matrices H119896 the matrix H
119896with the highest value of
log2(det(Ω
119896))Ω119896
= Ω(H119896) will be selected as the effective
channel matrix for the 119896th subcarrier in the conventionalscheme Meanwhile in the proposed scheme due to thebalance constraint the effective channel matrix associatedwith the kth subcarrier is not necessarily the one with thehighest log
2(det(Ω
119896)) that is log
2(det(Ω
119896)) le log
2(det(Ω
119896))
Thus the expected value of Δ119896can be computed by using
order statistics In particular an upper bound on the expecteddifference of two-order statistics the Γth and 120574th 1 le 120574 lt Γis given by [30]
119864 Δ119896 = 119864 log
2(det (Ω
119896)) minus 119864 log
2(det (Ω
119896))
le 120590119862radic
Γ (120574 + 1)
120574
(B1)
where 1205902119862is the variance of log
2(det(Ω
119896)) that is assumed to
be the same for all possible matricesH119896
On the other hand suppose that the entries of the 119899119877times119899119879
matrixH119896are iid complex Gaussian random variables with
zero mean and unit variance then for any effective channelmatrix H
119896 Ω119896is a complex Wishart matrix It follows from
[25] that the variance of log2(det(Ω
119896)) can be expressed as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1205951015840(119902 minus 119898 + 1) (B2)
International Journal of Antennas and Propagation 13
where 119901 = min(119899119863 119899119877) 119902 = max(119899
119863 119899119877) and 1205951015840(119909) =
suminfin
120593=11(120593 + 119909 minus 1)
2 is the first derivative of the digammafunction By approximating 1205951015840(119909) asymp 1119909 [25] the simplerexpression for 1205902
119862in (B2) is given as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1
119902 minus 119898 + 1 (B3)
Substitute (B3) into (B1) we finally arrive at
119864 Δ119896 le log
2(119890)radic(
119901
sum119898=1
1
119902 minus 119898 + 1) times
Γ (120574 + 1)
120574 (B4)
Conflict of Interests
The authors declare that there is no conflict of interestsregarding the publication of this paper
References
[1] L M Correia D Zeller O Blume et al ldquoChallenges andenabling technologies for energy aware mobile radio networksrdquoIEEECommunicationsMagazine vol 48 no 11 pp 66ndash72 2010
[2] Z Hasan H Boostanimehr and V K Bhargava ldquoGreen cellularnetworks a survey some research issues and challengesrdquo IEEECommunications Surveys and Tutorials vol 13 no 4 pp 524ndash540 2011
[3] J Joung C K Ho and S Sun ldquoGreenwireless communicationsa power amplifier perspectiverdquo in Proceedings of the 4th Asia-Pacific Signal and Information Processing Association AnnualSummit and Conference (APSIPA ASC rsquo12) pp 1ndash8 December2012
[4] G L Stuber J R Barry S W Mclaughlin Y E Li M AIngram and T G Pratt ldquoBroadband MIMO-OFDM wirelesscommunicationsrdquoProceedings of the IEEE vol 92 no 2 pp 271ndash294 2004
[5] H Bolcskei D Gesbert and A J Paulraj ldquoOn the capacity ofOFDM-based spatial multiplexing systemsrdquo IEEE Transactionson Communications vol 50 no 2 pp 225ndash234 2002
[6] V Tarokh N Seshadri and A R Calderbank ldquoSpace-timecodes for high data rate wireless communication performancecriterion and code constructionrdquo IEEE Transactions on Infor-mation Theory vol 44 no 2 pp 744ndash765 1998
[7] C M Vithanage M Sandell J P Coon and Y Wang ldquoPrecod-ing in OFDM-based multi-antenna ultra-wideband systemsrdquoIEEE Communications Magazine vol 47 no 1 pp 41ndash47 2009
[8] Z Tang H Suzuki and I B Collings ldquoPerformance of antennaselection forMIMO-OFDMsystems based onmeasured indoorcorrelated frequency selective channelsrdquo in Proceedings of theAustralian Telecommunication Networks and Applications Con-ference pp 435ndash439 December 2006
[9] H Zhang and R U Nabar ldquoTransmit antenna selection inMIMO-OFDM systems bulk versus per-tone selectionrdquo inProceedings of the IEEE International Conference on Communi-cations (ICC rsquo08) pp 4371ndash4375 May 2008
[10] H Shi M Katayama T Yamazato H Okada and A OgawaldquoAn adaptive antenna selection scheme for transmit diversityin OFDM systemsrdquo in Proceedings of the IEEE 54th VehicularTechnology Conference (VTC rsquo01) pp 2168ndash2172 October 2001
[11] M Sandell and J P Coon ldquoPer-subcarrier antenna selectionwith power constraints in OFDM systemsrdquo IEEE Transactionson Wireless Communications vol 8 no 2 pp 673ndash677 2009
[12] N P Le F Safaei and L C Tran ldquoTransmit antenna subsetselection for high-rate MIMO-OFDM systems in the presenceof nonlinear power amplifiersrdquo EURASIP Journal on WirelessCommunications and Networking vol 2014 article 27 2014
[13] R PrasadOFDM for Wireless Communications Systems ArtechHouse 1st edition 2004
[14] T Jiang and Y Wu ldquoAn overview peak-to-average power ratioreduction techniques for OFDM signalsrdquo IEEE Transactions onBroadcasting vol 54 no 2 pp 257ndash268 2008
[15] H Ochiai ldquoPerformance analysis of peak power and band-limited OFDM system with linear scalingrdquo IEEE Transactionson Wireless Communications vol 2 no 5 pp 1055ndash1065 2003
[16] C Zhao R J Baxley and G T Zhou ldquoPeak-to-average powerratio and power efficiency considerations in MIMO-OFDMsystemsrdquo IEEE Communications Letters vol 12 no 4 pp 268ndash270 2008
[17] D Wulich and I Gutman ldquoImpact of linear power amplifier onpower loading in OFDM part I principlesrdquo in Proceedings ofthe IEEE 26th Convention of Electrical and Electronics Engineersin Israel (IEEEI rsquo10) pp 360ndash364 November 2010
[18] S Coleri M Ergen A Puri and A Bahai ldquoChannel estimationtechniques based on pilot arrangement in OFDM systemsrdquoIEEE Transactions on Broadcasting vol 48 no 3 pp 223ndash2292002
[19] R W Heath S Sandhu and A Paulraj ldquoAntenna selectionfor spatial multiplexing systems with linear receiversrdquo IEEECommunications Letters vol 5 no 4 pp 142ndash144 2001
[20] R Fletcher Practical Methods of Optimization John Willey ampSons 2nd edition 1987
[21] R W Bauml R F H Fischer and J B Huber ldquoReducingthe peak-to-average power ratio of multicarrier modulation byselected mappingrdquo Electronics Letters vol 32 no 22 pp 2056ndash2057 1996
[22] M Tan Z Latinovic and Y Bar-Ness ldquoSTBC MIMO-OFDMpeak-to-average power ratio reduction by cross-antenna rota-tion and inversionrdquo IEEE Communications Letters vol 9 no 7pp 592ndash594 2005
[23] K M Anstreicher ldquoLinear programming in O(n3lnnL) opera-tionsrdquo SIAM Journal on Optimization vol 9 no 4 pp 803ndash8121999
[24] J G Proakis Digital Communications McGraw Hill 4th edi-tion 2001
[25] O Oyman R U Nabar H Bolcskei and A J Paulraj ldquoChar-acterizing the statistical properties of mutual information inMIMO channelsrdquo IEEE Transactions on Signal Processing vol51 no 11 pp 2784ndash2795 2003
[26] S Cui A J Goldsmith and A Bahai ldquoEnergy-constrainedmodulation optimizationrdquo IEEE Transactions onWireless Com-munications vol 4 no 5 pp 2349ndash2360 2005
[27] R J Baxley and G T Zhou ldquoPower savings analysis of peak-to-average power ratio reduction in OFDMrdquo IEEE Transactions onConsumer Electronics vol 50 no 3 pp 792ndash797 2004
[28] A Batra et al Multiband OFDM Physical Layer SpecificationRelease 1 5 WiMedia Alliance 2009
[29] J Foerster et al ldquoChannel modeling sub-committee reportfinalrdquo IEEE P802 15-02490r1-SG3a 2003
[30] B C Arnold and R A Groeneveld ldquoBounds on expectationsof linear systematic statistics based on dependent samplesrdquoTheAnnals of Statistics vol 7 no 1 pp 220ndash223 1979
International Journal of
AerospaceEngineeringHindawi Publishing Corporationhttpwwwhindawicom Volume 2014
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Active and Passive Electronic Components
Control Scienceand Engineering
Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
International Journal of
RotatingMachinery
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporation httpwwwhindawicom
Journal ofEngineeringVolume 2014
Submit your manuscripts athttpwwwhindawicom
VLSI Design
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Shock and Vibration
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Civil EngineeringAdvances in
Acoustics and VibrationAdvances in
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Electrical and Computer Engineering
Journal of
Advances inOptoElectronics
Hindawi Publishing Corporation httpwwwhindawicom
Volume 2014
The Scientific World JournalHindawi Publishing Corporation httpwwwhindawicom Volume 2014
SensorsJournal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Modelling amp Simulation in EngineeringHindawi Publishing Corporation httpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Chemical EngineeringInternational Journal of Antennas and
Propagation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Navigation and Observation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
DistributedSensor Networks
International Journal of
10 International Journal of Antennas and Propagation
Empirical CCDF of T110
0
10minus1
10minus2
minus2 0 2
W = 1
W = 4
W = 8
(a)
100
10minus1
10minus2
minus04 minus02 0
Empirical CDF of T2
(b)
Empirical CCDF of (T1 + T2)10
0
10minus1
10minus2
minus1 minus05 0 05 1 15 2
W = 1
W = 4
W = 8
(c)
Figure 4 Statistical distributions (note 1198792is independent of119882)
61 Evaluations of Peak-Power Distribution In Figure 5 weplot the CCDFs of the peak power of time-domain signalsThe analytical curves are based on (16) (17) and (19) Mean-while the simulation curves are empirical CCDF values Thesimulation result confirms that a system with the proposedallocation scheme offers a better CCDF performance than itscounterpart As expected the occurrence of high peak poweris significantly reduced when the peak-power reductionalgorithm is implemented Also it can be seen that theimprovement associated with this algorithm is reduced withincreasing 119882 In other words a very large value of 119882 whilerequiring higher complexity in terms on the number of IFFToperations results in a marginal improvement Thus it isreasonable to choose a relatively small value for 119882 (eg119882 = 4) It is also worth noting that the analytical curvesare relatively close to the simulation curves The small gapsexist due to the fact that the assumption of independentsamples |119904
119894(119899)| to obtain (13) does not strictly hold as we have
sum119870minus1
119899=0|119904119894(119899)|2 = 1205902119870
119894by Parsevalrsquos relation [24]
62 Evaluations of Power Efficiency of HPAs Figure 6 com-pares the CCDFs of the power efficiency achieved in theproposed and conventional systems It can be seen that theprobability of power efficiency being large highly likely occursin the proposed system compared to its counterpart Also
the simulation results agree well with the analytical resultsderived in (23) and (29) In Table 3 we compare the averagepower efficiencies Here the analytical values are obtainedaccording to (26) (27) and (30) Meanwhile the simulationvalues are empirical values based on the original definitionof the drain efficiency in (21) Also these values are averagedover the fading channel realizations It can be seen that thederived expressions approximate well the achieved powerefficiencies Table 3 also provides relative improvements ofthe power efficiencies achieved in the proposed system overthe conventional system Here only 120578
PE (Simulation) valuesare used for calculating these improvements It is clear thatthe proposed system could achieve a significant improvementin terms of average power efficiency
63 Evaluations of Capacity and Energy Efficiency Figure 7shows the system capacity inMbps (ie the normalized valuein (6) is scaled upwith the system bandwidth) versus the SNRvalue of 12059021205902
119899 It is clear that a systemwith the proposed allo-
cation scheme achieves a higher capacity than its counterpartThis agrees with the analysis in Section 51 that the changein capacity Δ119862 is positive In Figure 8 we plot the energyefficiency (MbitsJoule) versus spectral efficiency (MbpsHz)This figure is obtained based on (42) and (43) when varying119875dc Other parameters are 119875RF = 100mW 119875sp = 10mW and
International Journal of Antennas and Propagation 11
Table 3 A comparison of average power efficiencies
Imbalance Proposed (119882 = 1) Proposed (119882 = 4) Proposed (119882 = 8)120578PE (Simulation) 00697 00768 00894 00942
120578PE (Analysis) 00691 00757 00892 00943
Improvement120578PEproposed minus 120578
PEimbalance
120578PEimbalance
mdash 1019 2826 3515
1 2 3 4 5 6 7 8 9
100
10minus1
10minus2
10minus3
Peak power P0
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Pr (P
gtP0)
Figure 5 Comparison of CCDFs of the peak powers
002 004 006 008 01 012 014Power efficiency
CCD
F
100
10minus1
10minus2
10minus3
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Figure 6 Comparison of CCDFs of the power efficiencies
4500
4000
3500
3000
2500
2000
1500
1000
Ergo
dic c
apac
ity (M
bps)
2 4 6 8 10 12 14
SNR (dB)
3300
3200
3100
3000
2900
2800
97 98 99 10 101
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 7 Comparison of the ergodic capacities
12059021205902119899= 15 dB As expected the improvement in the power
efficiency of HPAs results in an improved energy efficiencyIn addition it can be observed that there exists an energyefficiency-spectral efficiency tradeoff in the systems Thistradeoff clearly needs to be taken into consideration whendesigning energy-efficient per-subcarrier antenna selectionbased OFDM wireless systems
7 Conclusions
In this paper a per-subcarrier antenna subset selectionMIMO-OFDM system with linear scaling has been investi-gated from an energy-efficiency perspective We have shownthat an imbalance allocation of data subcarriers associatedwith the conventional selection scheme affects the power effi-ciency of HPAs as well as the energy-efficiency of the wholesystem To deliver the maximum overall power efficiencywe have proposed the two-step strategy consisting of equalallocation data subcarriers across antennas and peak-powerreduction It has been proved from the power-efficiency view-point that the proposed allocation scheme outperforms theconventional scheme We have also derived the expressionsfor measuring the average power efficiency Moreover theimprovements in terms of capacity and energy efficiency
12 International Journal of Antennas and Propagation
0 2 4 6 8 10400
600
800
1000
1200
1400
1600
Spectral efficiency (MbpsHz)
Ener
gy effi
cien
cy (M
bits
J)
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 8 Energy efficiency versus spectral efficiency
resulting from the improved power efficiency have beenanalyzed The analytical results are validated by simulationresults The simulation result also shows that the systemwith the proposed allocation scheme could achieve a betterefficiency efficiency-spectral energy tradeoff compared to itscounterpart
Appendices
A Proof of Theorem 1
Let us consider a function 119891(120592) = 1 minus 119890minus1198750120592 0 lt 120592 le 1205902maxwhere 1205902max = max1205902
1198701 12059021198702
1205902119870119899119879
The second derivativeof this function is
11989110158401015840(120592) =
21198750120592 minus 11987520
1205924119890minus1198750120592 (A1)
From a HPAsrsquo viewpoint it is of interest to consider thesituation when the peak power across antennas 119875
0is large
Thus we consider the scenarios of 1198750
gt 21205902max where 1205902maxis the maximum average power across antennas Under thesesituations it is clear that 11989110158401015840(120592) lt 0 forall120592 isin (0 1205902max] Hencethe function 119891(120592) is concave By applying Jensenrsquos inequalitywe obtain the following inequality
1
119899119879
119899119879
sum119894=1
119891 (1205902
119870119894) le 119891(
1
119899119879
119899119879
sum119894=1
1205902
119870119894)
= 119891(1
119899119879
119899119879
sum119894=1
1205902
119870) = 119891 (120590
2
119870)
(A2)
where the equality comes from the fact that sum119899119879
119894=11205902119870119894
=
sum119899119879
119894=11205902119870
= 1198991198631205902 Expression (A2) can be rewritten as119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le 119899119879(1 minus 119890
minus11987501205902
119870) (A3)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879
On the other hand by applying the arithmetic-geometricmean inequality and note that (1 minus 119890
minus119909) gt 0 forall119909 gt 0 we have
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1
119899119879
119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ))
119899119879
(A4)
Note that the equality in (A4) holds if and only if 1205902119870119894
= 1205902119870
forall119894 = 1 119899119879
Combining (A3) and (A4) results in
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1 minus 119890minus1198750120590
2
119870)119899119879
(A5)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879 Thus we
get the following desired inequality
1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
ge 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(A6)
or
CCDF119875imbalance (1198750) ge CCDF119875balance (1198750) (A7)
This completes the proof
B Upper Bound of an ExpectedValue of Cost Penalty
In this appendix we derive an upper bound of the expectedvalue of Δ
119896 It can be seen from (5) that among all pos-
sible matrices H119896 the matrix H
119896with the highest value of
log2(det(Ω
119896))Ω119896
= Ω(H119896) will be selected as the effective
channel matrix for the 119896th subcarrier in the conventionalscheme Meanwhile in the proposed scheme due to thebalance constraint the effective channel matrix associatedwith the kth subcarrier is not necessarily the one with thehighest log
2(det(Ω
119896)) that is log
2(det(Ω
119896)) le log
2(det(Ω
119896))
Thus the expected value of Δ119896can be computed by using
order statistics In particular an upper bound on the expecteddifference of two-order statistics the Γth and 120574th 1 le 120574 lt Γis given by [30]
119864 Δ119896 = 119864 log
2(det (Ω
119896)) minus 119864 log
2(det (Ω
119896))
le 120590119862radic
Γ (120574 + 1)
120574
(B1)
where 1205902119862is the variance of log
2(det(Ω
119896)) that is assumed to
be the same for all possible matricesH119896
On the other hand suppose that the entries of the 119899119877times119899119879
matrixH119896are iid complex Gaussian random variables with
zero mean and unit variance then for any effective channelmatrix H
119896 Ω119896is a complex Wishart matrix It follows from
[25] that the variance of log2(det(Ω
119896)) can be expressed as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1205951015840(119902 minus 119898 + 1) (B2)
International Journal of Antennas and Propagation 13
where 119901 = min(119899119863 119899119877) 119902 = max(119899
119863 119899119877) and 1205951015840(119909) =
suminfin
120593=11(120593 + 119909 minus 1)
2 is the first derivative of the digammafunction By approximating 1205951015840(119909) asymp 1119909 [25] the simplerexpression for 1205902
119862in (B2) is given as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1
119902 minus 119898 + 1 (B3)
Substitute (B3) into (B1) we finally arrive at
119864 Δ119896 le log
2(119890)radic(
119901
sum119898=1
1
119902 minus 119898 + 1) times
Γ (120574 + 1)
120574 (B4)
Conflict of Interests
The authors declare that there is no conflict of interestsregarding the publication of this paper
References
[1] L M Correia D Zeller O Blume et al ldquoChallenges andenabling technologies for energy aware mobile radio networksrdquoIEEECommunicationsMagazine vol 48 no 11 pp 66ndash72 2010
[2] Z Hasan H Boostanimehr and V K Bhargava ldquoGreen cellularnetworks a survey some research issues and challengesrdquo IEEECommunications Surveys and Tutorials vol 13 no 4 pp 524ndash540 2011
[3] J Joung C K Ho and S Sun ldquoGreenwireless communicationsa power amplifier perspectiverdquo in Proceedings of the 4th Asia-Pacific Signal and Information Processing Association AnnualSummit and Conference (APSIPA ASC rsquo12) pp 1ndash8 December2012
[4] G L Stuber J R Barry S W Mclaughlin Y E Li M AIngram and T G Pratt ldquoBroadband MIMO-OFDM wirelesscommunicationsrdquoProceedings of the IEEE vol 92 no 2 pp 271ndash294 2004
[5] H Bolcskei D Gesbert and A J Paulraj ldquoOn the capacity ofOFDM-based spatial multiplexing systemsrdquo IEEE Transactionson Communications vol 50 no 2 pp 225ndash234 2002
[6] V Tarokh N Seshadri and A R Calderbank ldquoSpace-timecodes for high data rate wireless communication performancecriterion and code constructionrdquo IEEE Transactions on Infor-mation Theory vol 44 no 2 pp 744ndash765 1998
[7] C M Vithanage M Sandell J P Coon and Y Wang ldquoPrecod-ing in OFDM-based multi-antenna ultra-wideband systemsrdquoIEEE Communications Magazine vol 47 no 1 pp 41ndash47 2009
[8] Z Tang H Suzuki and I B Collings ldquoPerformance of antennaselection forMIMO-OFDMsystems based onmeasured indoorcorrelated frequency selective channelsrdquo in Proceedings of theAustralian Telecommunication Networks and Applications Con-ference pp 435ndash439 December 2006
[9] H Zhang and R U Nabar ldquoTransmit antenna selection inMIMO-OFDM systems bulk versus per-tone selectionrdquo inProceedings of the IEEE International Conference on Communi-cations (ICC rsquo08) pp 4371ndash4375 May 2008
[10] H Shi M Katayama T Yamazato H Okada and A OgawaldquoAn adaptive antenna selection scheme for transmit diversityin OFDM systemsrdquo in Proceedings of the IEEE 54th VehicularTechnology Conference (VTC rsquo01) pp 2168ndash2172 October 2001
[11] M Sandell and J P Coon ldquoPer-subcarrier antenna selectionwith power constraints in OFDM systemsrdquo IEEE Transactionson Wireless Communications vol 8 no 2 pp 673ndash677 2009
[12] N P Le F Safaei and L C Tran ldquoTransmit antenna subsetselection for high-rate MIMO-OFDM systems in the presenceof nonlinear power amplifiersrdquo EURASIP Journal on WirelessCommunications and Networking vol 2014 article 27 2014
[13] R PrasadOFDM for Wireless Communications Systems ArtechHouse 1st edition 2004
[14] T Jiang and Y Wu ldquoAn overview peak-to-average power ratioreduction techniques for OFDM signalsrdquo IEEE Transactions onBroadcasting vol 54 no 2 pp 257ndash268 2008
[15] H Ochiai ldquoPerformance analysis of peak power and band-limited OFDM system with linear scalingrdquo IEEE Transactionson Wireless Communications vol 2 no 5 pp 1055ndash1065 2003
[16] C Zhao R J Baxley and G T Zhou ldquoPeak-to-average powerratio and power efficiency considerations in MIMO-OFDMsystemsrdquo IEEE Communications Letters vol 12 no 4 pp 268ndash270 2008
[17] D Wulich and I Gutman ldquoImpact of linear power amplifier onpower loading in OFDM part I principlesrdquo in Proceedings ofthe IEEE 26th Convention of Electrical and Electronics Engineersin Israel (IEEEI rsquo10) pp 360ndash364 November 2010
[18] S Coleri M Ergen A Puri and A Bahai ldquoChannel estimationtechniques based on pilot arrangement in OFDM systemsrdquoIEEE Transactions on Broadcasting vol 48 no 3 pp 223ndash2292002
[19] R W Heath S Sandhu and A Paulraj ldquoAntenna selectionfor spatial multiplexing systems with linear receiversrdquo IEEECommunications Letters vol 5 no 4 pp 142ndash144 2001
[20] R Fletcher Practical Methods of Optimization John Willey ampSons 2nd edition 1987
[21] R W Bauml R F H Fischer and J B Huber ldquoReducingthe peak-to-average power ratio of multicarrier modulation byselected mappingrdquo Electronics Letters vol 32 no 22 pp 2056ndash2057 1996
[22] M Tan Z Latinovic and Y Bar-Ness ldquoSTBC MIMO-OFDMpeak-to-average power ratio reduction by cross-antenna rota-tion and inversionrdquo IEEE Communications Letters vol 9 no 7pp 592ndash594 2005
[23] K M Anstreicher ldquoLinear programming in O(n3lnnL) opera-tionsrdquo SIAM Journal on Optimization vol 9 no 4 pp 803ndash8121999
[24] J G Proakis Digital Communications McGraw Hill 4th edi-tion 2001
[25] O Oyman R U Nabar H Bolcskei and A J Paulraj ldquoChar-acterizing the statistical properties of mutual information inMIMO channelsrdquo IEEE Transactions on Signal Processing vol51 no 11 pp 2784ndash2795 2003
[26] S Cui A J Goldsmith and A Bahai ldquoEnergy-constrainedmodulation optimizationrdquo IEEE Transactions onWireless Com-munications vol 4 no 5 pp 2349ndash2360 2005
[27] R J Baxley and G T Zhou ldquoPower savings analysis of peak-to-average power ratio reduction in OFDMrdquo IEEE Transactions onConsumer Electronics vol 50 no 3 pp 792ndash797 2004
[28] A Batra et al Multiband OFDM Physical Layer SpecificationRelease 1 5 WiMedia Alliance 2009
[29] J Foerster et al ldquoChannel modeling sub-committee reportfinalrdquo IEEE P802 15-02490r1-SG3a 2003
[30] B C Arnold and R A Groeneveld ldquoBounds on expectationsof linear systematic statistics based on dependent samplesrdquoTheAnnals of Statistics vol 7 no 1 pp 220ndash223 1979
International Journal of
AerospaceEngineeringHindawi Publishing Corporationhttpwwwhindawicom Volume 2014
RoboticsJournal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Active and Passive Electronic Components
Control Scienceand Engineering
Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
International Journal of
RotatingMachinery
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporation httpwwwhindawicom
Journal ofEngineeringVolume 2014
Submit your manuscripts athttpwwwhindawicom
VLSI Design
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Shock and Vibration
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Civil EngineeringAdvances in
Acoustics and VibrationAdvances in
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Electrical and Computer Engineering
Journal of
Advances inOptoElectronics
Hindawi Publishing Corporation httpwwwhindawicom
Volume 2014
The Scientific World JournalHindawi Publishing Corporation httpwwwhindawicom Volume 2014
SensorsJournal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Modelling amp Simulation in EngineeringHindawi Publishing Corporation httpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Chemical EngineeringInternational Journal of Antennas and
Propagation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Navigation and Observation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
DistributedSensor Networks
International Journal of
International Journal of Antennas and Propagation 11
Table 3 A comparison of average power efficiencies
Imbalance Proposed (119882 = 1) Proposed (119882 = 4) Proposed (119882 = 8)120578PE (Simulation) 00697 00768 00894 00942
120578PE (Analysis) 00691 00757 00892 00943
Improvement120578PEproposed minus 120578
PEimbalance
120578PEimbalance
mdash 1019 2826 3515
1 2 3 4 5 6 7 8 9
100
10minus1
10minus2
10minus3
Peak power P0
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Pr (P
gtP0)
Figure 5 Comparison of CCDFs of the peak powers
002 004 006 008 01 012 014Power efficiency
CCD
F
100
10minus1
10minus2
10minus3
Imbalance (analysis)Imbalance (simulation)Proposed W = 1 (analysis)Proposed W = 1 (simulation)
Proposed W = 4 (analysis)Proposed W = 4 (simulation)Proposed W = 8 (analysis)Proposed W = 8 (simulation)
Figure 6 Comparison of CCDFs of the power efficiencies
4500
4000
3500
3000
2500
2000
1500
1000
Ergo
dic c
apac
ity (M
bps)
2 4 6 8 10 12 14
SNR (dB)
3300
3200
3100
3000
2900
2800
97 98 99 10 101
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 7 Comparison of the ergodic capacities
12059021205902119899= 15 dB As expected the improvement in the power
efficiency of HPAs results in an improved energy efficiencyIn addition it can be observed that there exists an energyefficiency-spectral efficiency tradeoff in the systems Thistradeoff clearly needs to be taken into consideration whendesigning energy-efficient per-subcarrier antenna selectionbased OFDM wireless systems
7 Conclusions
In this paper a per-subcarrier antenna subset selectionMIMO-OFDM system with linear scaling has been investi-gated from an energy-efficiency perspective We have shownthat an imbalance allocation of data subcarriers associatedwith the conventional selection scheme affects the power effi-ciency of HPAs as well as the energy-efficiency of the wholesystem To deliver the maximum overall power efficiencywe have proposed the two-step strategy consisting of equalallocation data subcarriers across antennas and peak-powerreduction It has been proved from the power-efficiency view-point that the proposed allocation scheme outperforms theconventional scheme We have also derived the expressionsfor measuring the average power efficiency Moreover theimprovements in terms of capacity and energy efficiency
12 International Journal of Antennas and Propagation
0 2 4 6 8 10400
600
800
1000
1200
1400
1600
Spectral efficiency (MbpsHz)
Ener
gy effi
cien
cy (M
bits
J)
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 8 Energy efficiency versus spectral efficiency
resulting from the improved power efficiency have beenanalyzed The analytical results are validated by simulationresults The simulation result also shows that the systemwith the proposed allocation scheme could achieve a betterefficiency efficiency-spectral energy tradeoff compared to itscounterpart
Appendices
A Proof of Theorem 1
Let us consider a function 119891(120592) = 1 minus 119890minus1198750120592 0 lt 120592 le 1205902maxwhere 1205902max = max1205902
1198701 12059021198702
1205902119870119899119879
The second derivativeof this function is
11989110158401015840(120592) =
21198750120592 minus 11987520
1205924119890minus1198750120592 (A1)
From a HPAsrsquo viewpoint it is of interest to consider thesituation when the peak power across antennas 119875
0is large
Thus we consider the scenarios of 1198750
gt 21205902max where 1205902maxis the maximum average power across antennas Under thesesituations it is clear that 11989110158401015840(120592) lt 0 forall120592 isin (0 1205902max] Hencethe function 119891(120592) is concave By applying Jensenrsquos inequalitywe obtain the following inequality
1
119899119879
119899119879
sum119894=1
119891 (1205902
119870119894) le 119891(
1
119899119879
119899119879
sum119894=1
1205902
119870119894)
= 119891(1
119899119879
119899119879
sum119894=1
1205902
119870) = 119891 (120590
2
119870)
(A2)
where the equality comes from the fact that sum119899119879
119894=11205902119870119894
=
sum119899119879
119894=11205902119870
= 1198991198631205902 Expression (A2) can be rewritten as119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le 119899119879(1 minus 119890
minus11987501205902
119870) (A3)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879
On the other hand by applying the arithmetic-geometricmean inequality and note that (1 minus 119890
minus119909) gt 0 forall119909 gt 0 we have
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1
119899119879
119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ))
119899119879
(A4)
Note that the equality in (A4) holds if and only if 1205902119870119894
= 1205902119870
forall119894 = 1 119899119879
Combining (A3) and (A4) results in
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1 minus 119890minus1198750120590
2
119870)119899119879
(A5)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879 Thus we
get the following desired inequality
1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
ge 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(A6)
or
CCDF119875imbalance (1198750) ge CCDF119875balance (1198750) (A7)
This completes the proof
B Upper Bound of an ExpectedValue of Cost Penalty
In this appendix we derive an upper bound of the expectedvalue of Δ
119896 It can be seen from (5) that among all pos-
sible matrices H119896 the matrix H
119896with the highest value of
log2(det(Ω
119896))Ω119896
= Ω(H119896) will be selected as the effective
channel matrix for the 119896th subcarrier in the conventionalscheme Meanwhile in the proposed scheme due to thebalance constraint the effective channel matrix associatedwith the kth subcarrier is not necessarily the one with thehighest log
2(det(Ω
119896)) that is log
2(det(Ω
119896)) le log
2(det(Ω
119896))
Thus the expected value of Δ119896can be computed by using
order statistics In particular an upper bound on the expecteddifference of two-order statistics the Γth and 120574th 1 le 120574 lt Γis given by [30]
119864 Δ119896 = 119864 log
2(det (Ω
119896)) minus 119864 log
2(det (Ω
119896))
le 120590119862radic
Γ (120574 + 1)
120574
(B1)
where 1205902119862is the variance of log
2(det(Ω
119896)) that is assumed to
be the same for all possible matricesH119896
On the other hand suppose that the entries of the 119899119877times119899119879
matrixH119896are iid complex Gaussian random variables with
zero mean and unit variance then for any effective channelmatrix H
119896 Ω119896is a complex Wishart matrix It follows from
[25] that the variance of log2(det(Ω
119896)) can be expressed as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1205951015840(119902 minus 119898 + 1) (B2)
International Journal of Antennas and Propagation 13
where 119901 = min(119899119863 119899119877) 119902 = max(119899
119863 119899119877) and 1205951015840(119909) =
suminfin
120593=11(120593 + 119909 minus 1)
2 is the first derivative of the digammafunction By approximating 1205951015840(119909) asymp 1119909 [25] the simplerexpression for 1205902
119862in (B2) is given as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1
119902 minus 119898 + 1 (B3)
Substitute (B3) into (B1) we finally arrive at
119864 Δ119896 le log
2(119890)radic(
119901
sum119898=1
1
119902 minus 119898 + 1) times
Γ (120574 + 1)
120574 (B4)
Conflict of Interests
The authors declare that there is no conflict of interestsregarding the publication of this paper
References
[1] L M Correia D Zeller O Blume et al ldquoChallenges andenabling technologies for energy aware mobile radio networksrdquoIEEECommunicationsMagazine vol 48 no 11 pp 66ndash72 2010
[2] Z Hasan H Boostanimehr and V K Bhargava ldquoGreen cellularnetworks a survey some research issues and challengesrdquo IEEECommunications Surveys and Tutorials vol 13 no 4 pp 524ndash540 2011
[3] J Joung C K Ho and S Sun ldquoGreenwireless communicationsa power amplifier perspectiverdquo in Proceedings of the 4th Asia-Pacific Signal and Information Processing Association AnnualSummit and Conference (APSIPA ASC rsquo12) pp 1ndash8 December2012
[4] G L Stuber J R Barry S W Mclaughlin Y E Li M AIngram and T G Pratt ldquoBroadband MIMO-OFDM wirelesscommunicationsrdquoProceedings of the IEEE vol 92 no 2 pp 271ndash294 2004
[5] H Bolcskei D Gesbert and A J Paulraj ldquoOn the capacity ofOFDM-based spatial multiplexing systemsrdquo IEEE Transactionson Communications vol 50 no 2 pp 225ndash234 2002
[6] V Tarokh N Seshadri and A R Calderbank ldquoSpace-timecodes for high data rate wireless communication performancecriterion and code constructionrdquo IEEE Transactions on Infor-mation Theory vol 44 no 2 pp 744ndash765 1998
[7] C M Vithanage M Sandell J P Coon and Y Wang ldquoPrecod-ing in OFDM-based multi-antenna ultra-wideband systemsrdquoIEEE Communications Magazine vol 47 no 1 pp 41ndash47 2009
[8] Z Tang H Suzuki and I B Collings ldquoPerformance of antennaselection forMIMO-OFDMsystems based onmeasured indoorcorrelated frequency selective channelsrdquo in Proceedings of theAustralian Telecommunication Networks and Applications Con-ference pp 435ndash439 December 2006
[9] H Zhang and R U Nabar ldquoTransmit antenna selection inMIMO-OFDM systems bulk versus per-tone selectionrdquo inProceedings of the IEEE International Conference on Communi-cations (ICC rsquo08) pp 4371ndash4375 May 2008
[10] H Shi M Katayama T Yamazato H Okada and A OgawaldquoAn adaptive antenna selection scheme for transmit diversityin OFDM systemsrdquo in Proceedings of the IEEE 54th VehicularTechnology Conference (VTC rsquo01) pp 2168ndash2172 October 2001
[11] M Sandell and J P Coon ldquoPer-subcarrier antenna selectionwith power constraints in OFDM systemsrdquo IEEE Transactionson Wireless Communications vol 8 no 2 pp 673ndash677 2009
[12] N P Le F Safaei and L C Tran ldquoTransmit antenna subsetselection for high-rate MIMO-OFDM systems in the presenceof nonlinear power amplifiersrdquo EURASIP Journal on WirelessCommunications and Networking vol 2014 article 27 2014
[13] R PrasadOFDM for Wireless Communications Systems ArtechHouse 1st edition 2004
[14] T Jiang and Y Wu ldquoAn overview peak-to-average power ratioreduction techniques for OFDM signalsrdquo IEEE Transactions onBroadcasting vol 54 no 2 pp 257ndash268 2008
[15] H Ochiai ldquoPerformance analysis of peak power and band-limited OFDM system with linear scalingrdquo IEEE Transactionson Wireless Communications vol 2 no 5 pp 1055ndash1065 2003
[16] C Zhao R J Baxley and G T Zhou ldquoPeak-to-average powerratio and power efficiency considerations in MIMO-OFDMsystemsrdquo IEEE Communications Letters vol 12 no 4 pp 268ndash270 2008
[17] D Wulich and I Gutman ldquoImpact of linear power amplifier onpower loading in OFDM part I principlesrdquo in Proceedings ofthe IEEE 26th Convention of Electrical and Electronics Engineersin Israel (IEEEI rsquo10) pp 360ndash364 November 2010
[18] S Coleri M Ergen A Puri and A Bahai ldquoChannel estimationtechniques based on pilot arrangement in OFDM systemsrdquoIEEE Transactions on Broadcasting vol 48 no 3 pp 223ndash2292002
[19] R W Heath S Sandhu and A Paulraj ldquoAntenna selectionfor spatial multiplexing systems with linear receiversrdquo IEEECommunications Letters vol 5 no 4 pp 142ndash144 2001
[20] R Fletcher Practical Methods of Optimization John Willey ampSons 2nd edition 1987
[21] R W Bauml R F H Fischer and J B Huber ldquoReducingthe peak-to-average power ratio of multicarrier modulation byselected mappingrdquo Electronics Letters vol 32 no 22 pp 2056ndash2057 1996
[22] M Tan Z Latinovic and Y Bar-Ness ldquoSTBC MIMO-OFDMpeak-to-average power ratio reduction by cross-antenna rota-tion and inversionrdquo IEEE Communications Letters vol 9 no 7pp 592ndash594 2005
[23] K M Anstreicher ldquoLinear programming in O(n3lnnL) opera-tionsrdquo SIAM Journal on Optimization vol 9 no 4 pp 803ndash8121999
[24] J G Proakis Digital Communications McGraw Hill 4th edi-tion 2001
[25] O Oyman R U Nabar H Bolcskei and A J Paulraj ldquoChar-acterizing the statistical properties of mutual information inMIMO channelsrdquo IEEE Transactions on Signal Processing vol51 no 11 pp 2784ndash2795 2003
[26] S Cui A J Goldsmith and A Bahai ldquoEnergy-constrainedmodulation optimizationrdquo IEEE Transactions onWireless Com-munications vol 4 no 5 pp 2349ndash2360 2005
[27] R J Baxley and G T Zhou ldquoPower savings analysis of peak-to-average power ratio reduction in OFDMrdquo IEEE Transactions onConsumer Electronics vol 50 no 3 pp 792ndash797 2004
[28] A Batra et al Multiband OFDM Physical Layer SpecificationRelease 1 5 WiMedia Alliance 2009
[29] J Foerster et al ldquoChannel modeling sub-committee reportfinalrdquo IEEE P802 15-02490r1-SG3a 2003
[30] B C Arnold and R A Groeneveld ldquoBounds on expectationsof linear systematic statistics based on dependent samplesrdquoTheAnnals of Statistics vol 7 no 1 pp 220ndash223 1979
International Journal of
AerospaceEngineeringHindawi Publishing Corporationhttpwwwhindawicom Volume 2014
RoboticsJournal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Active and Passive Electronic Components
Control Scienceand Engineering
Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
International Journal of
RotatingMachinery
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporation httpwwwhindawicom
Journal ofEngineeringVolume 2014
Submit your manuscripts athttpwwwhindawicom
VLSI Design
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Shock and Vibration
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Civil EngineeringAdvances in
Acoustics and VibrationAdvances in
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Electrical and Computer Engineering
Journal of
Advances inOptoElectronics
Hindawi Publishing Corporation httpwwwhindawicom
Volume 2014
The Scientific World JournalHindawi Publishing Corporation httpwwwhindawicom Volume 2014
SensorsJournal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Modelling amp Simulation in EngineeringHindawi Publishing Corporation httpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Chemical EngineeringInternational Journal of Antennas and
Propagation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Navigation and Observation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
DistributedSensor Networks
International Journal of
12 International Journal of Antennas and Propagation
0 2 4 6 8 10400
600
800
1000
1200
1400
1600
Spectral efficiency (MbpsHz)
Ener
gy effi
cien
cy (M
bits
J)
ImbalanceProposed W = 1
Proposed W = 4
Proposed W = 8
Figure 8 Energy efficiency versus spectral efficiency
resulting from the improved power efficiency have beenanalyzed The analytical results are validated by simulationresults The simulation result also shows that the systemwith the proposed allocation scheme could achieve a betterefficiency efficiency-spectral energy tradeoff compared to itscounterpart
Appendices
A Proof of Theorem 1
Let us consider a function 119891(120592) = 1 minus 119890minus1198750120592 0 lt 120592 le 1205902maxwhere 1205902max = max1205902
1198701 12059021198702
1205902119870119899119879
The second derivativeof this function is
11989110158401015840(120592) =
21198750120592 minus 11987520
1205924119890minus1198750120592 (A1)
From a HPAsrsquo viewpoint it is of interest to consider thesituation when the peak power across antennas 119875
0is large
Thus we consider the scenarios of 1198750
gt 21205902max where 1205902maxis the maximum average power across antennas Under thesesituations it is clear that 11989110158401015840(120592) lt 0 forall120592 isin (0 1205902max] Hencethe function 119891(120592) is concave By applying Jensenrsquos inequalitywe obtain the following inequality
1
119899119879
119899119879
sum119894=1
119891 (1205902
119870119894) le 119891(
1
119899119879
119899119879
sum119894=1
1205902
119870119894)
= 119891(1
119899119879
119899119879
sum119894=1
1205902
119870) = 119891 (120590
2
119870)
(A2)
where the equality comes from the fact that sum119899119879
119894=11205902119870119894
=
sum119899119879
119894=11205902119870
= 1198991198631205902 Expression (A2) can be rewritten as119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le 119899119879(1 minus 119890
minus11987501205902
119870) (A3)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879
On the other hand by applying the arithmetic-geometricmean inequality and note that (1 minus 119890
minus119909) gt 0 forall119909 gt 0 we have
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1
119899119879
119899119879
sum119894=1
(1 minus 119890minus1198750120590
2
119870119894 ))
119899119879
(A4)
Note that the equality in (A4) holds if and only if 1205902119870119894
= 1205902119870
forall119894 = 1 119899119879
Combining (A3) and (A4) results in
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 ) le (1 minus 119890minus1198750120590
2
119870)119899119879
(A5)
with equality if and only if 1205902119870119894
= 1205902119870 forall119894 = 1 119899
119879 Thus we
get the following desired inequality
1 minus
119899119879
prod119894=1
(1 minus 119890minus1198750120590
2
119870119894 )119870
ge 1 minus (1 minus 119890minus1198750120590
2
119870)119899119879119870
(A6)
or
CCDF119875imbalance (1198750) ge CCDF119875balance (1198750) (A7)
This completes the proof
B Upper Bound of an ExpectedValue of Cost Penalty
In this appendix we derive an upper bound of the expectedvalue of Δ
119896 It can be seen from (5) that among all pos-
sible matrices H119896 the matrix H
119896with the highest value of
log2(det(Ω
119896))Ω119896
= Ω(H119896) will be selected as the effective
channel matrix for the 119896th subcarrier in the conventionalscheme Meanwhile in the proposed scheme due to thebalance constraint the effective channel matrix associatedwith the kth subcarrier is not necessarily the one with thehighest log
2(det(Ω
119896)) that is log
2(det(Ω
119896)) le log
2(det(Ω
119896))
Thus the expected value of Δ119896can be computed by using
order statistics In particular an upper bound on the expecteddifference of two-order statistics the Γth and 120574th 1 le 120574 lt Γis given by [30]
119864 Δ119896 = 119864 log
2(det (Ω
119896)) minus 119864 log
2(det (Ω
119896))
le 120590119862radic
Γ (120574 + 1)
120574
(B1)
where 1205902119862is the variance of log
2(det(Ω
119896)) that is assumed to
be the same for all possible matricesH119896
On the other hand suppose that the entries of the 119899119877times119899119879
matrixH119896are iid complex Gaussian random variables with
zero mean and unit variance then for any effective channelmatrix H
119896 Ω119896is a complex Wishart matrix It follows from
[25] that the variance of log2(det(Ω
119896)) can be expressed as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1205951015840(119902 minus 119898 + 1) (B2)
International Journal of Antennas and Propagation 13
where 119901 = min(119899119863 119899119877) 119902 = max(119899
119863 119899119877) and 1205951015840(119909) =
suminfin
120593=11(120593 + 119909 minus 1)
2 is the first derivative of the digammafunction By approximating 1205951015840(119909) asymp 1119909 [25] the simplerexpression for 1205902
119862in (B2) is given as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1
119902 minus 119898 + 1 (B3)
Substitute (B3) into (B1) we finally arrive at
119864 Δ119896 le log
2(119890)radic(
119901
sum119898=1
1
119902 minus 119898 + 1) times
Γ (120574 + 1)
120574 (B4)
Conflict of Interests
The authors declare that there is no conflict of interestsregarding the publication of this paper
References
[1] L M Correia D Zeller O Blume et al ldquoChallenges andenabling technologies for energy aware mobile radio networksrdquoIEEECommunicationsMagazine vol 48 no 11 pp 66ndash72 2010
[2] Z Hasan H Boostanimehr and V K Bhargava ldquoGreen cellularnetworks a survey some research issues and challengesrdquo IEEECommunications Surveys and Tutorials vol 13 no 4 pp 524ndash540 2011
[3] J Joung C K Ho and S Sun ldquoGreenwireless communicationsa power amplifier perspectiverdquo in Proceedings of the 4th Asia-Pacific Signal and Information Processing Association AnnualSummit and Conference (APSIPA ASC rsquo12) pp 1ndash8 December2012
[4] G L Stuber J R Barry S W Mclaughlin Y E Li M AIngram and T G Pratt ldquoBroadband MIMO-OFDM wirelesscommunicationsrdquoProceedings of the IEEE vol 92 no 2 pp 271ndash294 2004
[5] H Bolcskei D Gesbert and A J Paulraj ldquoOn the capacity ofOFDM-based spatial multiplexing systemsrdquo IEEE Transactionson Communications vol 50 no 2 pp 225ndash234 2002
[6] V Tarokh N Seshadri and A R Calderbank ldquoSpace-timecodes for high data rate wireless communication performancecriterion and code constructionrdquo IEEE Transactions on Infor-mation Theory vol 44 no 2 pp 744ndash765 1998
[7] C M Vithanage M Sandell J P Coon and Y Wang ldquoPrecod-ing in OFDM-based multi-antenna ultra-wideband systemsrdquoIEEE Communications Magazine vol 47 no 1 pp 41ndash47 2009
[8] Z Tang H Suzuki and I B Collings ldquoPerformance of antennaselection forMIMO-OFDMsystems based onmeasured indoorcorrelated frequency selective channelsrdquo in Proceedings of theAustralian Telecommunication Networks and Applications Con-ference pp 435ndash439 December 2006
[9] H Zhang and R U Nabar ldquoTransmit antenna selection inMIMO-OFDM systems bulk versus per-tone selectionrdquo inProceedings of the IEEE International Conference on Communi-cations (ICC rsquo08) pp 4371ndash4375 May 2008
[10] H Shi M Katayama T Yamazato H Okada and A OgawaldquoAn adaptive antenna selection scheme for transmit diversityin OFDM systemsrdquo in Proceedings of the IEEE 54th VehicularTechnology Conference (VTC rsquo01) pp 2168ndash2172 October 2001
[11] M Sandell and J P Coon ldquoPer-subcarrier antenna selectionwith power constraints in OFDM systemsrdquo IEEE Transactionson Wireless Communications vol 8 no 2 pp 673ndash677 2009
[12] N P Le F Safaei and L C Tran ldquoTransmit antenna subsetselection for high-rate MIMO-OFDM systems in the presenceof nonlinear power amplifiersrdquo EURASIP Journal on WirelessCommunications and Networking vol 2014 article 27 2014
[13] R PrasadOFDM for Wireless Communications Systems ArtechHouse 1st edition 2004
[14] T Jiang and Y Wu ldquoAn overview peak-to-average power ratioreduction techniques for OFDM signalsrdquo IEEE Transactions onBroadcasting vol 54 no 2 pp 257ndash268 2008
[15] H Ochiai ldquoPerformance analysis of peak power and band-limited OFDM system with linear scalingrdquo IEEE Transactionson Wireless Communications vol 2 no 5 pp 1055ndash1065 2003
[16] C Zhao R J Baxley and G T Zhou ldquoPeak-to-average powerratio and power efficiency considerations in MIMO-OFDMsystemsrdquo IEEE Communications Letters vol 12 no 4 pp 268ndash270 2008
[17] D Wulich and I Gutman ldquoImpact of linear power amplifier onpower loading in OFDM part I principlesrdquo in Proceedings ofthe IEEE 26th Convention of Electrical and Electronics Engineersin Israel (IEEEI rsquo10) pp 360ndash364 November 2010
[18] S Coleri M Ergen A Puri and A Bahai ldquoChannel estimationtechniques based on pilot arrangement in OFDM systemsrdquoIEEE Transactions on Broadcasting vol 48 no 3 pp 223ndash2292002
[19] R W Heath S Sandhu and A Paulraj ldquoAntenna selectionfor spatial multiplexing systems with linear receiversrdquo IEEECommunications Letters vol 5 no 4 pp 142ndash144 2001
[20] R Fletcher Practical Methods of Optimization John Willey ampSons 2nd edition 1987
[21] R W Bauml R F H Fischer and J B Huber ldquoReducingthe peak-to-average power ratio of multicarrier modulation byselected mappingrdquo Electronics Letters vol 32 no 22 pp 2056ndash2057 1996
[22] M Tan Z Latinovic and Y Bar-Ness ldquoSTBC MIMO-OFDMpeak-to-average power ratio reduction by cross-antenna rota-tion and inversionrdquo IEEE Communications Letters vol 9 no 7pp 592ndash594 2005
[23] K M Anstreicher ldquoLinear programming in O(n3lnnL) opera-tionsrdquo SIAM Journal on Optimization vol 9 no 4 pp 803ndash8121999
[24] J G Proakis Digital Communications McGraw Hill 4th edi-tion 2001
[25] O Oyman R U Nabar H Bolcskei and A J Paulraj ldquoChar-acterizing the statistical properties of mutual information inMIMO channelsrdquo IEEE Transactions on Signal Processing vol51 no 11 pp 2784ndash2795 2003
[26] S Cui A J Goldsmith and A Bahai ldquoEnergy-constrainedmodulation optimizationrdquo IEEE Transactions onWireless Com-munications vol 4 no 5 pp 2349ndash2360 2005
[27] R J Baxley and G T Zhou ldquoPower savings analysis of peak-to-average power ratio reduction in OFDMrdquo IEEE Transactions onConsumer Electronics vol 50 no 3 pp 792ndash797 2004
[28] A Batra et al Multiband OFDM Physical Layer SpecificationRelease 1 5 WiMedia Alliance 2009
[29] J Foerster et al ldquoChannel modeling sub-committee reportfinalrdquo IEEE P802 15-02490r1-SG3a 2003
[30] B C Arnold and R A Groeneveld ldquoBounds on expectationsof linear systematic statistics based on dependent samplesrdquoTheAnnals of Statistics vol 7 no 1 pp 220ndash223 1979
International Journal of
AerospaceEngineeringHindawi Publishing Corporationhttpwwwhindawicom Volume 2014
RoboticsJournal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Active and Passive Electronic Components
Control Scienceand Engineering
Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
International Journal of
RotatingMachinery
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporation httpwwwhindawicom
Journal ofEngineeringVolume 2014
Submit your manuscripts athttpwwwhindawicom
VLSI Design
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Shock and Vibration
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Civil EngineeringAdvances in
Acoustics and VibrationAdvances in
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Electrical and Computer Engineering
Journal of
Advances inOptoElectronics
Hindawi Publishing Corporation httpwwwhindawicom
Volume 2014
The Scientific World JournalHindawi Publishing Corporation httpwwwhindawicom Volume 2014
SensorsJournal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Modelling amp Simulation in EngineeringHindawi Publishing Corporation httpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Chemical EngineeringInternational Journal of Antennas and
Propagation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Navigation and Observation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
DistributedSensor Networks
International Journal of
International Journal of Antennas and Propagation 13
where 119901 = min(119899119863 119899119877) 119902 = max(119899
119863 119899119877) and 1205951015840(119909) =
suminfin
120593=11(120593 + 119909 minus 1)
2 is the first derivative of the digammafunction By approximating 1205951015840(119909) asymp 1119909 [25] the simplerexpression for 1205902
119862in (B2) is given as
1205902
119862= [log
2(119890)]2
119901
sum119898=1
1
119902 minus 119898 + 1 (B3)
Substitute (B3) into (B1) we finally arrive at
119864 Δ119896 le log
2(119890)radic(
119901
sum119898=1
1
119902 minus 119898 + 1) times
Γ (120574 + 1)
120574 (B4)
Conflict of Interests
The authors declare that there is no conflict of interestsregarding the publication of this paper
References
[1] L M Correia D Zeller O Blume et al ldquoChallenges andenabling technologies for energy aware mobile radio networksrdquoIEEECommunicationsMagazine vol 48 no 11 pp 66ndash72 2010
[2] Z Hasan H Boostanimehr and V K Bhargava ldquoGreen cellularnetworks a survey some research issues and challengesrdquo IEEECommunications Surveys and Tutorials vol 13 no 4 pp 524ndash540 2011
[3] J Joung C K Ho and S Sun ldquoGreenwireless communicationsa power amplifier perspectiverdquo in Proceedings of the 4th Asia-Pacific Signal and Information Processing Association AnnualSummit and Conference (APSIPA ASC rsquo12) pp 1ndash8 December2012
[4] G L Stuber J R Barry S W Mclaughlin Y E Li M AIngram and T G Pratt ldquoBroadband MIMO-OFDM wirelesscommunicationsrdquoProceedings of the IEEE vol 92 no 2 pp 271ndash294 2004
[5] H Bolcskei D Gesbert and A J Paulraj ldquoOn the capacity ofOFDM-based spatial multiplexing systemsrdquo IEEE Transactionson Communications vol 50 no 2 pp 225ndash234 2002
[6] V Tarokh N Seshadri and A R Calderbank ldquoSpace-timecodes for high data rate wireless communication performancecriterion and code constructionrdquo IEEE Transactions on Infor-mation Theory vol 44 no 2 pp 744ndash765 1998
[7] C M Vithanage M Sandell J P Coon and Y Wang ldquoPrecod-ing in OFDM-based multi-antenna ultra-wideband systemsrdquoIEEE Communications Magazine vol 47 no 1 pp 41ndash47 2009
[8] Z Tang H Suzuki and I B Collings ldquoPerformance of antennaselection forMIMO-OFDMsystems based onmeasured indoorcorrelated frequency selective channelsrdquo in Proceedings of theAustralian Telecommunication Networks and Applications Con-ference pp 435ndash439 December 2006
[9] H Zhang and R U Nabar ldquoTransmit antenna selection inMIMO-OFDM systems bulk versus per-tone selectionrdquo inProceedings of the IEEE International Conference on Communi-cations (ICC rsquo08) pp 4371ndash4375 May 2008
[10] H Shi M Katayama T Yamazato H Okada and A OgawaldquoAn adaptive antenna selection scheme for transmit diversityin OFDM systemsrdquo in Proceedings of the IEEE 54th VehicularTechnology Conference (VTC rsquo01) pp 2168ndash2172 October 2001
[11] M Sandell and J P Coon ldquoPer-subcarrier antenna selectionwith power constraints in OFDM systemsrdquo IEEE Transactionson Wireless Communications vol 8 no 2 pp 673ndash677 2009
[12] N P Le F Safaei and L C Tran ldquoTransmit antenna subsetselection for high-rate MIMO-OFDM systems in the presenceof nonlinear power amplifiersrdquo EURASIP Journal on WirelessCommunications and Networking vol 2014 article 27 2014
[13] R PrasadOFDM for Wireless Communications Systems ArtechHouse 1st edition 2004
[14] T Jiang and Y Wu ldquoAn overview peak-to-average power ratioreduction techniques for OFDM signalsrdquo IEEE Transactions onBroadcasting vol 54 no 2 pp 257ndash268 2008
[15] H Ochiai ldquoPerformance analysis of peak power and band-limited OFDM system with linear scalingrdquo IEEE Transactionson Wireless Communications vol 2 no 5 pp 1055ndash1065 2003
[16] C Zhao R J Baxley and G T Zhou ldquoPeak-to-average powerratio and power efficiency considerations in MIMO-OFDMsystemsrdquo IEEE Communications Letters vol 12 no 4 pp 268ndash270 2008
[17] D Wulich and I Gutman ldquoImpact of linear power amplifier onpower loading in OFDM part I principlesrdquo in Proceedings ofthe IEEE 26th Convention of Electrical and Electronics Engineersin Israel (IEEEI rsquo10) pp 360ndash364 November 2010
[18] S Coleri M Ergen A Puri and A Bahai ldquoChannel estimationtechniques based on pilot arrangement in OFDM systemsrdquoIEEE Transactions on Broadcasting vol 48 no 3 pp 223ndash2292002
[19] R W Heath S Sandhu and A Paulraj ldquoAntenna selectionfor spatial multiplexing systems with linear receiversrdquo IEEECommunications Letters vol 5 no 4 pp 142ndash144 2001
[20] R Fletcher Practical Methods of Optimization John Willey ampSons 2nd edition 1987
[21] R W Bauml R F H Fischer and J B Huber ldquoReducingthe peak-to-average power ratio of multicarrier modulation byselected mappingrdquo Electronics Letters vol 32 no 22 pp 2056ndash2057 1996
[22] M Tan Z Latinovic and Y Bar-Ness ldquoSTBC MIMO-OFDMpeak-to-average power ratio reduction by cross-antenna rota-tion and inversionrdquo IEEE Communications Letters vol 9 no 7pp 592ndash594 2005
[23] K M Anstreicher ldquoLinear programming in O(n3lnnL) opera-tionsrdquo SIAM Journal on Optimization vol 9 no 4 pp 803ndash8121999
[24] J G Proakis Digital Communications McGraw Hill 4th edi-tion 2001
[25] O Oyman R U Nabar H Bolcskei and A J Paulraj ldquoChar-acterizing the statistical properties of mutual information inMIMO channelsrdquo IEEE Transactions on Signal Processing vol51 no 11 pp 2784ndash2795 2003
[26] S Cui A J Goldsmith and A Bahai ldquoEnergy-constrainedmodulation optimizationrdquo IEEE Transactions onWireless Com-munications vol 4 no 5 pp 2349ndash2360 2005
[27] R J Baxley and G T Zhou ldquoPower savings analysis of peak-to-average power ratio reduction in OFDMrdquo IEEE Transactions onConsumer Electronics vol 50 no 3 pp 792ndash797 2004
[28] A Batra et al Multiband OFDM Physical Layer SpecificationRelease 1 5 WiMedia Alliance 2009
[29] J Foerster et al ldquoChannel modeling sub-committee reportfinalrdquo IEEE P802 15-02490r1-SG3a 2003
[30] B C Arnold and R A Groeneveld ldquoBounds on expectationsof linear systematic statistics based on dependent samplesrdquoTheAnnals of Statistics vol 7 no 1 pp 220ndash223 1979
International Journal of
AerospaceEngineeringHindawi Publishing Corporationhttpwwwhindawicom Volume 2014
RoboticsJournal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Active and Passive Electronic Components
Control Scienceand Engineering
Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
International Journal of
RotatingMachinery
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporation httpwwwhindawicom
Journal ofEngineeringVolume 2014
Submit your manuscripts athttpwwwhindawicom
VLSI Design
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Shock and Vibration
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Civil EngineeringAdvances in
Acoustics and VibrationAdvances in
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Electrical and Computer Engineering
Journal of
Advances inOptoElectronics
Hindawi Publishing Corporation httpwwwhindawicom
Volume 2014
The Scientific World JournalHindawi Publishing Corporation httpwwwhindawicom Volume 2014
SensorsJournal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Modelling amp Simulation in EngineeringHindawi Publishing Corporation httpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Chemical EngineeringInternational Journal of Antennas and
Propagation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Navigation and Observation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
DistributedSensor Networks
International Journal of
International Journal of
AerospaceEngineeringHindawi Publishing Corporationhttpwwwhindawicom Volume 2014
RoboticsJournal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Active and Passive Electronic Components
Control Scienceand Engineering
Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
International Journal of
RotatingMachinery
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporation httpwwwhindawicom
Journal ofEngineeringVolume 2014
Submit your manuscripts athttpwwwhindawicom
VLSI Design
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Shock and Vibration
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Civil EngineeringAdvances in
Acoustics and VibrationAdvances in
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Electrical and Computer Engineering
Journal of
Advances inOptoElectronics
Hindawi Publishing Corporation httpwwwhindawicom
Volume 2014
The Scientific World JournalHindawi Publishing Corporation httpwwwhindawicom Volume 2014
SensorsJournal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Modelling amp Simulation in EngineeringHindawi Publishing Corporation httpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Chemical EngineeringInternational Journal of Antennas and
Propagation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
Navigation and Observation
International Journal of
Hindawi Publishing Corporationhttpwwwhindawicom Volume 2014
DistributedSensor Networks
International Journal of