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8/19/2019 5. MechatronicsWorkshop KCCDay2 Session1-2.pdf
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K. Craig 1
Mechatronics for the 21st Century
Agreement?
Control System
Design
Agreement?
Expected
Closed-Loop
System
Response
Predicted
Closed-Loop
System
Response
System
Design
Concept
System Design
and Performance
Specifications
Concept
Physical
Model
Concept
Mathematical
Model
Predicted
Open-Loop
System
Response
ExpectedComponent
and Open-
Loop System
Response
Is predicted
response acceptable
with respect to
specifications?no
yes
no
Mechatronic System
Design ProcessSTART
HERE
Simplifying
Assumptions
no
yes
yes
no
Build and Test Physical SystemCheck That System Meets Specifications
Evaluate, Iterate, and Improve As Needed
Apply
Laws of Nature
Solve Equations:
Analytical &
Numerical
Past
Experience &Experiments
Engineering
JudgmentRe-evaluate
Physical Model
Assumptions &
Parameters
Identify
Model
Parameters
Improve Control Design:
Feedback, Feedforward,
Observers, Filters
Improve System Design:
Parameters and/or
Configuration / Concept
Design &
Simulate
R e a l W o r l d
S i m ul a t i onW or l d Re-evaluate
Past
Experience &
Experiments
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K. Craig 2
Mechatronics Master Class
Schedule Day 1 Day 2 Day 3
Session 1Mechatronics
and
Innovation
Modeling &
Analysis of
Dynamic Physical
Systems
High-Performance
Mechatronic
Motion Systems
Session 2Human-Centered
Design
Automotive
Mechatronics
Session 3
Model-Based
Design
Control System
Design: Feedback,Feedforward, &
Observers
Web-Handling
Mechatronic Applications
Session 4Mechatronic
System Design
Fluid Power
Mechatronic
Applications
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Modeling Engineering Systems K. Craig 1
Modeling Engineering Systems
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Modeling Engineering Systems K. Craig 2
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Modeling Engineering Systems K. Craig 3
Engineering System Investigation Process
Physical
System
System
Measurement
Measurement Analysis
Physical
Model
Mathematical
Model
Parameter
Identification
Mathematical Analysis
Comparison:
Predicted vs.
Measured
Design
Changes
Is The
Comparison
Adequate ?
NO
YES
START HERE
The cornerstone of
modern engineering
practice !
Engineering
SystemInvestigation
ProcessModeling
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Modeling Engineering Systems K. Craig 4
• Apply the steps in the process when:
– An actual physical system exists and one desires to
understand and predict its behavior.
– The physical system is a concept in the design process
that needs to be analyzed and evaluated.
• After recognizing a need for a new product or service, onegenerates design concepts by using: past experience
(personal and vicarious), awareness of existing hardware,
understanding of physical laws, and creativity.• The importance of modeling and analysis in the design
process has never been more important. Design concepts
can no longer be evaluated by the build-and-test approach
because it is too costly and time consuming. Validating thepredicted dynamic behavior in this case, when no actual
physical system exists, then becomes even more dependent
on one's past hardware and experimental experience.
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Modeling Engineering Systems K. Craig 5
• What is a Physical Model?
– In general, a physical model is an imaginary physical system
which resembles an actual system in its most significant
features, but which is simpler, more ideal, and is thereby
more amenable to analytical studies.
– There is a hierarchy of physical models of varying complexitypossible.
– The difference between a physical system and a physical
model is analogous to the difference between the actualphysical terrain and a map.
– Not oversimplified, not overly complicated - a slice of reality.
– The very crux of engineering analysis and the hallmark ofevery successful engineer is the ability to make shrewd and
viable approximations which greatly simplify the system and
still lead to a rapid, reasonably accurate prediction of its
behavior.
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Modeling Engineering Systems K. Craig 6
• What is a Mathematical Model?
– We apply the Laws of Nature to the Physical Model,NOT to the Physical System, to obtain the
Mathematical Model.
– What Laws of Nature?• Newton’s Laws of Motion
• Maxwell’s Equations of Electromagnetism
• Laws of Thermodynamics – Once we have the Mathematical Model of the
Physical Model, we then solve the equations, either
analytically or numerically, or both to get the greatestinsight, to predict how the Physical Model behaves.
This predicted behavior must then be compared to
the actual measured behavior of the Physical System.
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Modeling Engineering Systems K. Craig 7
Balance: The Key to Success
Computer Simulation Without Experimental Verification
Is At Best Questionable, And At Worst Useless!
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Modeling Engineering Systems K. Craig 8
Balance in Engineering is the Key!
• The essential characteristic of an engineer and
the key to success is a balance between thefollowing sets of skills:
– modeling (physical and mathematical), analysis
(closed-form and numerical simulation), and controldesign (analog and digital) of dynamic physical
systems
– experimental validation of models and analysis andunderstanding the key issues in hardware
implementation of designs
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Modeling Engineering Systems K. Craig 9
• Dynamic Physical System
– Any collection of interacting elements for which thereare cause-and-effect relationships among the time-
dependent variables. The present output of the system
depends on past inputs.
• Analysis of the Dynamic Behavior of Physical
Systems
– Cornerstone of modern technology – More than any other field links the engineering
disciplines
• Purpose of a Dynamic System Investigation – Understand & predict the dynamic behavior of a system
– Modify and/or control the system, if necessary
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Modeling Engineering Systems K. Craig 10
• Essential Features of the Study of Dynamic
Systems – Deals with entire operating machines and
processes rather than just isolated components.
– Treats dynamic behavior of mechanical, electrical,electromechanical, fluid, thermal, chemical, and
mixed systems.
– Emphasizes the behavioral similarity betweensystems that differ physically and develops general
analysis and design tools useful for all kinds of
physical systems. – Sacrifices detail in component descriptions so as to
enable understanding of the behavior of complex
systems made from many components.
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Modeling Engineering Systems K. Craig 11
– Uses methods which accommodate componentdescriptions in terms of experimental
measurements, when accurate theory is lacking or
is not cost-effective, and develops universal lab
test methods for characterizing component
behavior.
– Serves as a unifying foundation for many practical
application areas, e.g., vibrations, measurementsystems, control systems, acoustics, vehicle
dynamics, etc.
– Offers a wide variety of computer software toimplement its methods of analysis and design.
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Modeling Engineering Systems K. Craig 12
Electro-Dynamic Vibration Exciter
Physical System vs. Physical Model
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Modeling Engineering Systems K. Craig 13
• This "moving coil" type of device converts an electrical
command signal into a mechanical force and/or motion and
is very common, e.g., vibration shakers, loudspeakers,linear motors for positioning heads on computer disk
memories, and optical mirror scanners.
• In all these cases, a current-carrying coil is located in asteady magnetic field provided by permanent magnets in
small devices and electrically-excited wound coils in large
ones.• Two electromechanical effects are observed in such
configurations:
– Generator Effect: Motion of the coil through the magnetic fieldcauses a voltage proportional to velocity to be induced into the coil.
– Motor Effect: Passage of current through the coil causes it toexperience a magnetic force proportional to the current.
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Modeling Engineering Systems K. Craig 14
• Flexure Kf is an intentional soft spring (stiff, however, in
the radial direction) that serves to guide the axial motion
of the coil and table.
• Flexure damping Bf is usually intentional, fairly strong,
and obtained by laminated construction of the flexure
spring, using layers of metal, elastomer, plastic, and soon.
• The coupling of the coil to the shaker table would ideally
be rigid so that magnetic force is transmitted undistortedto the mechanical load. Thus Kt (generally large) and Bt(quite small) represent parasitic effects rather than
intentional spring and damper elements.• R and L are the total circuit resistance and inductance,
including contributions from both the shaker coil and the
amplifier output circuit.
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Modeling Engineering Systems K. Craig 15
t t f t f t t c t t c t
c c t c t t c t
i c
M x K x B x B (x x ) K (x x )
M x B (x x ) K (x x ) Ki
Li e Ri Kx
= − − + − + −
= − − − − +
= − −
Equationsof Motion
f t f t t tt t
t t t tt t
ic c
t t t tc c
c c c c c
0 1 0 0 0
0K K B B K Bx x0M M M M 0x x
0 0 0 1 0 0ex x
K B K B 0K x xM M M M M 1
i iLK R
0 0 0L L
⎡ ⎤⎢ ⎥− − − − ⎡ ⎤⎢ ⎥⎡ ⎤ ⎡ ⎤ ⎢ ⎥⎢ ⎥⎢ ⎥ ⎢ ⎥ ⎢ ⎥⎢ ⎥⎢ ⎥ ⎢ ⎥ ⎢ ⎥= +⎢ ⎥⎢ ⎥ ⎢ ⎥ ⎢ ⎥
− −⎢ ⎥⎢ ⎥ ⎢ ⎥ ⎢ ⎥⎢ ⎥⎢ ⎥ ⎢ ⎥ ⎢ ⎥⎢ ⎥⎢ ⎥ ⎢ ⎥⎣ ⎦ ⎣ ⎦ ⎢ ⎥⎣ ⎦− −⎢ ⎥
⎢ ⎥⎣ ⎦
State-Space
Representation
Mathematical Modeling: Laws of Nature applied to Physical Model
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Modeling Engineering Systems K. Craig 16
Analytical Frequency Response Plots
Typical
Parameter
Values
(SI Units)L = 0.0012
R = 3.0
K = 190
Kt
= 8.16E8
Bt = 3850
Kf = 6.3E5
Bf = 1120
Mc = 1.815
Mt = 6.12
resonance due to flexures
parasitic resonance
due to coil-table
coupling
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Modeling Engineering Systems K. Craig 17
Experimental Frequency Response Plot
B&K
PM Vibration Exciter
Type 4809
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Modeling Engineering Systems K. Craig 18
Electro-PneumaticTransducer
Σ Σ
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Modeling Engineering Systems K. Craig 19
This system can be
collapsed into a
simplified
approximate overall
model when
numerical valuesare properly
chosen:
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Modeling Engineering Systems K. Craig 20
• It is interesting to note here that while the blockdiagram shows one input for the system, i.e.,
command voltage ein , there are possible undesired
inputs that must also be considered.
• For example, the ambient temperature will affect the
electric coil resistance, the permanent magnet
strength, the leaf-spring stiffness, the damper-oil
viscosity, the air density, and the dimensions of the
mechanical parts. All these changes will affect the
system output pressure po in some way, and the
cumulative effects may not be negligible.
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Modeling Engineering Systems K. Craig 21
Temperature FeedbackControl System:
A Larger-Scale
Engineering System
Bridge
Circuit Amplifier Controller
Electro-
Pneumatic
Transducer
ValveChemical
Process
Thermistor
RV
eE
RC
DesiredTemperature
(set with RV)
Block Diagram of an Temperature Control System
Σ
Actual
Temperature
(measured with
RC)
eM pM xVTC
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Modeling Engineering Systems K. Craig 22
• Note that in the block diagram of this system, the
detailed operation of the electropneumatic transducer
is not made apparent; only its overall input/output
relation is included.
• The designer of the temperature feedback-controldynamic system would consider the electropneumatic
transducer an off-the-shelf component with certain
desirable operating characteristics.• The methods of system dynamics are used by both
the electropneumatic transducer designer and the
designer of the larger temperature feedback-controlsystem.
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Modeling Engineering Systems K. Craig 23
Physical Modeling
Less Real, Less Complex, More Easily Solved
Truth Model Design Model
More Real, More Complex, Less Easily Solved
Hierarchy Of Models
Always Ask: Why Am I Modeling?
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Modeling Engineering Systems K. Craig 24
• Physical System
– Define the physical system to be studied, along withthe system boundaries, input variables, and output
variables.
• Physical System to Physical Model – In general, a physical model is an imaginary physical
system which resembles an actual system in its
salient features, but which is simpler, more ideal, andis thereby more amenable to analytical studies.
There is a hierarchy of physical models of varying
complexity possible. – Not oversimplified, not overly complicated - a slice of
reality.
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Modeling Engineering Systems K. Craig 25
– The astuteness with which approximations are
made at the onset of an investigation is the verycrux of engineering analysis.
– The ability to make shrewd and viable
approximations which greatly simplify the systemand still lead to a rapid, reasonably accurate
prediction of its behavior is the hallmark of every
successful engineer. – What is the purpose of the model? Develop a set
of performance specifications for the model based
on the specific purpose of the model. Whatfeatures must be included? How accurately do
they need to be represented?
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Modeling Engineering Systems K. Craig 26
– The challenges to physical modeling are formidable:• Dynamic behavior of many physical processes is
complex.
• Cause and effect relationships are not easilydiscernible.
• Many important variables are not readily identified.
• Interactions among the variables are hard tocapture.
• Engineering Judgment is the Key!
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Modeling Engineering Systems K. Craig 27
– In modeling dynamic systems, we consider matter
and energy as being continuously, though not
necessarily uniformly, distributed over the space
within the system boundaries.
– This is the macroscopic or continuum point of view.We consider the system variables as quantities which
change continuously from point to point in the system
as well as with time and this always leads to adistributed-parameter physical model which results in
a partial differential equation mathematical model.
– Models in this most general form behave most like thereal systems at the macroscopic level.
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Modeling Engineering Systems K. Craig 28
– Because of the mathematical complexity of these
models, engineers find it necessary and desirable towork with less exact models in many cases.
– Simpler models which concentrate matter and energy
into discrete lumps are called lumped-parameterphysical models and lead to ordinary differential
equation mathematical models.
– An understanding of the difference between
distributed-parameter and lumped-parameter models
is vital to the intelligent formulation and use of lumped
models.
– The time-variation of the system parameters can be
random or deterministic, and if deterministic, variable
or constant.
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Modeling Engineering Systems K. Craig 29
• Comments on Truth Model vs. Design Model
– In modeling dynamic systems, we use engineering judgment and simplifying assumptions to develop a
physical model. The complexity of the physical model
depends on the particular need, and the intelligent
use of simple physical models requires that we have
some understanding of what we are missing when we
choose the simpler model over the more complex
model. – The truth model is the model that includes all the
known relevant characteristics of the real system.
This model is often too complicated for use inengineering design, but is most useful in verifying
design changes or control designs prior to hardware
implementation.
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Modeling Engineering Systems K. Craig 30
– The design model captures the important features
of the process for which a control system is to be
designed or design iterations are to be performed,
but omits the details which you believe are not
significant.
– In practice, you may need a hierarchy of models of
varying complexity:
• A very detailed truth model for final
performance evaluation before hardwareimplementation
• Several less complex truth models for use in
evaluating particular effects
• One or more design models
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Modeling Engineering Systems K. Craig 31
Approximation Mathematical
Simplification
Neglect small effects Reduces the number and
complexity of the equations of
motion
Assume the environment isindependent of system motions
Reduces the number andcomplexity of the equations of
motion
Replace distributed
characteristics with appropriatelumped elements
Leads to ordinary (rather than
partial) differential equations
Assume linear relationships Makes equations linear; allows
superposition of solutions Assume constant parameters Leads to constant coefficients in
the differential equations
Neglect uncertainty and noise Avoids statistical treatment
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Modeling Engineering Systems K. Craig 32
• Neglect Small Effects
– Small effects are neglected on a relative basis. In
analyzing the motion of an airplane, we are unlikely to
consider the effects of solar pressure, the earth's
magnetic field, or gravity gradient. To ignore these
effects in a space vehicle problem would lead to
grossly incorrect results!
• Independent Environment
– In analyzing the vibration of an instrument panel in a
vehicle, we assume that the vehicle motion is
independent of the motion of the instrument panel.
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Modeling Engineering Systems K. Craig 33
• Lumped Characteristics
– In a lumped-parameter model, system dependentvariables are assumed uniform over finite regions of
space rather than over infinitesimal elements, as in a
distributed-parameter model. Time is the onlyindependent variable and the mathematical model is
an ordinary differential equation.
– In a distributed-parameter model, time and spatialvariables are independent variables and the
mathematical model is a partial differential equation.
– Note that elements in a lumped-parameter model donot necessarily correspond to separate physical parts
of the actual system.
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Modeling Engineering Systems K. Craig 34
– A long electrical transmission line has resistance,
inductance, and capacitance distributed continuouslyalong its length. These distributed properties are
approximated by lumped elements at discrete points
along the line. – It is important to note that a lumped-parameter model,
which may be valid in low-frequency operations, may
not be valid at higher frequencies, since the neglected
property of distributed parameters may become
important. For example, the mass of a spring may be
neglected in low-frequency operations, but it becomes
an important property of the system at highfrequencies.
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Modeling Engineering Systems K. Craig 35
• Linear Relationships
– Nearly all physical elements or systems are inherentlynonlinear if there are no restrictions at all placed on
the allowable values of the inputs, e.g., saturation,
dead-zone, square-law nonlinearities. – If the values of the inputs are confined to a sufficiently
small range, the original nonlinear model of the
system may often be replaced by a linear model
whose response closely approximates that of the
nonlinear model.
– When a linear equation has been solved once, the
solution is general, holding for all magnitudes of
motion.
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Modeling Engineering Systems K. Craig 36
– Linear systems also satisfy conditions for
superposition.
– The superposition property states that for a system
initially at rest with zero energy: (1) multiplying the
inputs by any constant multiplies the outputs by the
same constant, and (2) the response to several inputsapplied simultaneously is the sum of the individual
responses to each input applied separately.
• Constant Parameters – Time-varying systems are ones whose characteristics
change with time.
– Physical problems are simplified by the adoption of a
model in which all the physical parameters are
constant.
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Modeling Engineering Systems K. Craig 37
• Neglect Uncertainty and Noise
– In real systems we are uncertain, in varying degrees,about values of parameters, about measurements,
and about expected inputs and disturbances.
Disturbances contain random inputs, called noise,
which can influence system behavior.
– It is common to neglect such uncertainties and noise
and proceed as if all quantities have definite values
that are known precisely.
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Modeling Engineering Systems K. Craig 38
• Summary
– The most realistic physical model of a dynamicsystem leads to differential equations of motion that
are:
• nonlinear, partial differential equations with time-varying and space-varying parameters
• These equations are the most difficult to solve.
– The simplifying assumptions discussed lead to aphysical model of a dynamic system that is less
realistic and to equations of motion that are:
• linear, ordinary differential equations with constantcoefficients
• These equations are easier to solve and design
with.
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Modeling Engineering Systems K. Craig 39
Classes of Systems
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Modeling Engineering Systems K. Craig 40
Pure and Ideal Elements vs. Real Devices
• A pure element refers to an element (spring, damper,
inertia, resistor, capacitor, inductor, etc.) which has only the
named attribute.• For example, a pure spring element has no inertia or friction
and is thus a mathematical model (approximation), not a
real device.• The term ideal, as applied to elements, means linear , that
is, the input/output relationship of the element is linear, or
straight-line. The output is perfectly proportional to theinput.
• A device can be pure without being ideal and ideal without
being pure.
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Modeling Engineering Systems K. Craig 41
• From a functional engineering viewpoint, nonlinear
behavior may often be preferable, even though it leadsto difficult equations.
• Why do we choose to define and use pure and ideal
elements when we know that they do not behave like thereal devices used in designing systems?
– Once we have defined these pure and ideal elements,
we can use these as building blocks to model realdevices more accurately.
• For example, if a real spring has significant friction and
mass, we model it as a combination of pure/ideal spring,mass, and damper elements, which may come quite
close in behavior to the real spring.
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Modeling Engineering Systems K. Craig 42
Physical Model of a Real Spring
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Modeling Engineering Systems K. Craig 43
• There are three basic types of building blocks,two that can store energy and one that
dissipates energy.
– All Mechanical Systems have three attributes - mass,springiness, and energy dissipation. The basic
elements corresponding to these attributes are inertia
(mass), damper (friction), and spring (compliance). – All Electrical Systems have three attributes -
inductance, resistance, and capacitance. The
corresponding basic elements are inductor, resistor,and capacitor.
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Modeling Engineering Systems K. Craig 44
Mechanical System Elements
• It is hard to imagine any engineering system that does
not have mechanical components.
• Motion and force are concepts used to describe the
behavior of engineering systems that employ mechanical
components.
• The three basic mechanical building block elements are:
– Spring (elasticity or compliance) element
– Damper (friction or energy dissipation) element
– Mass (inertia) element
• There are both translational and rotational versions of
these basic building blocks.
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Modeling Engineering Systems K. Craig 45
• These are passive (non-energy producing) devices.
• Driving Inputs are force and motion sources which causeelements to respond.
• Each of the elements has one of two possible energy
behaviors: – stores all the energy supplied to it
– dissipates all energy into heat by some kind of
“frictional” effect• Spring stores energy as potential energy.
• Mass stores energy as kinetic energy.
• Damper dissipates energy into heat.
• The Dynamic Response of each element is important.
S i El t
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Modeling Engineering Systems K. Craig 46
• Spring Element
– A spring is a fundamental mechanical component found
intentionally or unintentionally in almost everymechanical system.
– Real-world spring is neither pure nor ideal.
– Real-world spring has inertia and friction.
– Pure spring has only elasticity - it is a mathematical
model, not a real device.
– Some dynamic operation requires that spring inertia
and/or damping not be neglected.
– Ideal spring is linear. However, nonlinear behavior may
often be preferable and give significant performanceadvantages.
2 1
F K(x x )= −
Pure & Ideal
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Modeling Engineering Systems K. Craig 47
0
s
2 2x
s 0 s 0s
0
Differential Work Done
(f )dx (K x)dx
Total Work Done
K x C f (K x)dx
2 2
= =
= = =∫
Pure & IdealSpring Element
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Modeling Engineering Systems K. Craig 48
• Damping Element
– A damper is a mechanical component often found inengineering systems.
– A pure damper dissipates all the energy supplied to it,
i.e., converts the mechanical energy to thermalenergy.
– Various physical mechanisms, usually associated
with some form of friction, can provide this dissipativeaction, e.g.,
• Coulomb (dry friction) damping
• Material (solid) damping
• Viscous (fluid) damping
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Modeling Engineering Systems K. Craig 50
Pure & IdealDamper Element
Step Input
Forcecauses instantly
(a pure damper
has no inertia) aStep of dx/dt
and a
Ramp of x
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Modeling Engineering Systems K. Craig 51
• Mass or Inertia Element
– All real mechanical components used in engineeringsystems have mass.
– A designer rarely inserts a component for the purpose
of adding inertia; the mass or inertia element oftenrepresents an undesirable effect which is unavoidable
since all materials have mass.
– There are some applications in which mass itselfserves a useful function, e.g., flywheels – a flywheel
is an energy-storage device and can be used as a
means of smoothing out speed fluctuations in enginesor other machines.
N t ’ L d fi th b h i f l t
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Modeling Engineering Systems K. Craig 52
– Newton’s Law defines the behavior of mass elements
and refers basically to an idealized “point mass”:
– The concept of rigid body is introduced to deal with
practical situations. For pure translatory motion,every point in a rigid body has identical motion.
– Real physical bodies never display ideal rigid
behavior when being accelerated.
– The pure and ideal inertia element is a model, not a
real object. Real inertias may be impure (have some
springiness and friction) but are very close to ideal.
forces (mass)(acceleration)=∑
F Ma=
Pur & Id l
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Modeling Engineering Systems K. Craig 53
Pure & IdealInertia Element
Real inertias may be
impure (have some
springiness and friction) but
are very close to ideal.
2 2
x 1 1(D) (D)
f MD T JD
θ= =
Inertia Element stores energy
as kinetic energy:
2 2Mv J or
2 2
ω
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Modeling Engineering Systems K. Craig 55
Ideal vs. Real Sources
• External driving agencies are physical quantities which
pass from the environment, through the interface into the
system, and cause the system to respond.• In practical situations, there may be interactions between
the environment and the system; however, we often use
the concept of ideal source.• An ideal source (force, motion, voltage, current, etc.) is
totally unaffected by being coupled to the system it is
driving.• For example, a “real” 6-volt battery will not supply 6 volts
to a circuit! The circuit will draw some current from the
battery and the battery’s voltage will drop.
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Modeling Engineering Systems K. Craig 56
Physical Model to Mathematical Model
• We derive a mathematical model to represent the physical
model, i.e., apply the Laws of Nature to the physical model and
write down the differential equations of motion.• The goal is a generalized treatment of dynamic systems,
including mechanical, electrical, electromechanical, fluid,
thermal, chemical, and mixed systems.
– Define System: Boundary, Inputs, Outputs
– Define Variables: Through and Across Variables
– Write System Relations: Dynamic Equilibrium Relations and
Compatibility Relations
– Write Constitutive Relations: Physical Relations for Each
Element
– Combine: Generate State Equations
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Modeling Engineering Systems K. Craig 57
• Define System
– A system must be defined before equilibrium and/orcompatibility relations can be written.
– Unless physical boundaries of a system are clearly
specified, any equilibrium and/or compatibilityrelations we may write are meaningless.
• Define Variables
– Physical Variables
• Select precise physical variables (velocity, voltage,
pressure, flow rate, etc.) with which to describe the
instantaneous state of a system, and in terms ofwhich to study its behavior.
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Modeling Engineering Systems K. Craig 58
– Through Variables
• Through variables (one-point variables) measure the
transmission of something through an element, e.g.,
– electric current through a resistor
– fluid flow through a duct – force through a spring
– Across Variables
• Across variables (two-point) variables measure adifference in state between the ends of an element,
e.g.,
– voltage drop across a resistor – pressure drop between the ends of a duct
– difference in velocity between the ends of a
damper
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Modeling Engineering Systems K. Craig 59
– In addition to through and across variables, integrated
through variables (e.g., momentum) and integratedacross variables (e.g., displacement) are important.
• Write System Relations
– Dynamic Equilibrium Relations• Write dynamic equilibrium relations to describe the
balance - of forces, of flow rates, of energy - which
must exist for the system and its subsystems.• Equilibrium relations are always relations among
through variables, e.g.,
– Kirchhoff’s Current Law (at an electrical node) – continuity of fluid flow
– equilibrium of forces meeting at a point
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Modeling Engineering Systems K. Craig 60
– Compatibility Relations
• Write system compatibility relations to describehow motions of the system elements are
interrelated because of the way they are
interconnected.• These are inter-element or system relations.
• Compatibility relations are always relations among
across variables, e.g., – Kirchhoff’s Voltage Law around a circuit
– pressure drop across all the interconnected
stages of a fluid system
– geometric compatibility in a mechanical system
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Modeling Engineering Systems K. Craig 61
• Write Physical Relations for Each Element
– These relations are called constitutive physicalrelations as they concern only individual elements or
constituents of the system.
– They are natural physical laws which the individualelements of the system obey, e.g.,
• mechanical relations between force and motion
• electrical relations between current and voltage• electromechanical relations between force and
magnetic field
• thermodynamic relations between temperature,pressure, etc.
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Modeling Engineering Systems K. Craig 62
– They are relations between through and across
variables of each individual physical element. – They may be algebraic, differential, integral, linear or
nonlinear, constant or time-varying.
– They are purely empirical relations observed byexperiment and not deduced from any basic
principles.
• Combine System Relations and Physical
Relations to Generate System Differential
Equations
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Modeling Engineering Systems K. Craig 63
• Study Dynamic Behavior – Study the dynamic behavior of the mathematicalmodel by solving the differential equations of
motion either through mathematical analysis or
computer simulation.
– Dynamic behavior is a consequence of the system
structure - don’t blame the input!
– Seek a relationship between physical model
structure and behavior.
– Develop insight into system behavior.
• Comparison: Actual vs Predicted
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Modeling Engineering Systems K. Craig 64
Comparison: Actual vs. Predicted
– Compare the predicted dynamic behavior to the
measured dynamic behavior from tests on the actualphysical system; make physical model corrections, if
necessary.
• Make Design Decisions
– Make design decisions so that the system will behave
as desired:• modify the system (e.g., change the physical
parameters of the system, add a sensor, change
the actuator or its location)• control the system (e.g., augment the system,
typically by adding a dynamic system called a
compensator or controller)
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Dynamic System Response K. Craig 1
Dynamic System Response
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Dynamic System Response K. Craig 2
Dynamic System Response
• LTI Behavior vs. Non-LTI Behavior
• Solution of Linear, Constant-Coefficient, Ordinary
Differential Equations
– Classical Operator Method
– Laplace Transform Method
• Laplace Transform Properties
• 1st-Order Dynamic System Time and Frequency
Response• 2nd-Order Dynamic System Time and Frequency
Response
• Dynamic System Response Example Problems
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Dynamic System Response K. Craig 3
LTI Behavior vs. Non-LTI Behavior
• Linear Time-Invariant (LTI) Systems
– A frequency-domain transfer function is limited todescribing elements that are linear and time invariant
– severe restrictions! No real-world system meets
them!
– Linear Time-Invariant System Properties
• Homogeneity: If r(t) → c(t), then kr(t) → kc(t)
• Superposition: If r 1(t) → c1(t) and r 2(t) → c2(t), thenr 1(t) + r 2(t) → c1(t) + c2(t)
• Time Invariance: If r(t) → c(t), then r(t-t1) → c(t-t1)
C f S
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Dynamic System Response K. Craig 4
– Comments on the Principle of Superposition
• The principle of superposition states that if the
system has an input that can be expressed as the
sum of signals, then the response of the system can
be expressed as the sum of the individual
responses to the respective signals. Superpositionapplies if and only if the system is linear .
• Using the principle of superposition, we can solve
for the system responses to a set of elementarysignals. We are then able to solve for the response
to a general signal simply by decomposing the
given signal into a sum of the elementarycomponents and, by superposition, concluding that
the response to the general signal is sum of the
responses to the elementary signals.
• In order for this process to work, the
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Dynamic System Response K. Craig 5
p ,
elementary signals need to be sufficiently rich
that any reasonable signal can be expressedas a sum of them, and their responses have to
be easy to find. The most common candidate
for elementary signals for use in linear systems
are the impulse and the exponential.
• The unit impulse δ(t) is a pulse of zero durationand infinite height. The area under the unit
impulse (its strength) is equal to one.
• The impulse δ(t) is defined by δ(t-τ) = 0 for all t≠ τ. It has the property that if f(t) is continuousat t = τ, then
f ( ) (t )d f (t)
∞
−∞ τ δ − τ τ =∫
(t )dt 1+
−
τ
τδ − τ =∫
Th i l i h t d i t th t
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Dynamic System Response K. Craig 6
• The impulse is so short and so intense that no
value of f matters except over the short range
where the δ occurs. The integral can be viewed asrepresenting the function f as a sum of impulses.
• To find the response to an arbitrary input, the
principle of superposition tells us that we need onlyfind the response to a unit impulse.
• For a linear, time-invariant system, the impulse
response, i.e., the response at time t to an impulseapplied at time τ, can be expressed as h(t – τ)because the response at time t to an input applied
at time τ depends only on the difference betweenthe time the impulse is applied and the time we areobserving the response.
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Dynamic System Response K. Craig 7
• For linear, time-invariant systems with input
u(t), the superposition integral, called the
convolution integral, is:
• Here u(t) is the input to the system and h(t-τ) is
the impulse response of the system.
y(t) u( )h(t )d u(t )h( )d u h
∞ ∞
−∞ −∞= τ − τ τ = − τ τ τ = ∗∫ ∫
Convolution Example y ky u (t) y(0 ) 0−+ = = δ =
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Dynamic System Response K. Craig 8
– Convolution Example0 0 0
0 0 0
y y ( ) y( )
ydt k ydt (t)dt
y(0 ) y(0 ) k(0) 1
y(0 ) 1
y ky 0 y(0 ) 1
+ + +
− − −
+ −
+
+
+ = δ⎡ ⎤− + =⎣ ⎦
=+ = =
∫ ∫ ∫
st
st st
kt
Assume y Ae
Ase kAe 0
s k A 1
y(t) h(t) e for t 0−
=
+ =
= − == = >
0 t 01 t 0
<≥
1(t)
kty(t) h(t) e 1(t)−= =
The response to a general input u(t) is
given by the convolution of this impulseresponse and the input:
kt
kt
0
y(t) e 1(t)u(t )d
e u(t )d
∞ −
−∞
∞ −
= − τ τ
= − τ τ
∫
∫
unit step function
impulse response
A consequence of convolution is the concept of transfer
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Dynamic System Response K. Craig 9
– A consequence of convolution is the concept of transfer
function.
– Note that both the input and output are exponential timefunctions and that the output differs from the input only in
the amplitude H(s).
– The function H(s) is the transfer function from the inputto output of the system. It is the ratio of the Laplace
transform of the output to the Laplace transform of the
input assuming all initial conditions are zero.
( )
s( t ) st
st s st s
st s
y t h( )u(t )d Convolution Integral
h( )e d Input e
h( )e e d e h( )e d
e H(s) where H(s) h( )e d
∞
−∞∞ −τ
−∞
∞ ∞− τ − τ
−∞ −∞
∞ − τ
−∞
= τ − τ τ
= τ τ =
= τ τ = τ τ= = τ τ
∫∫
∫ ∫∫
– If the input is the unit impulse function δ(t), then y(t) is
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Dynamic System Response K. Craig 10
If the input is the unit impulse function δ(t), then y(t) isthe unit impulse response. The Laplace transform of
δ(t) is 1 and the Laplace transform of y(t) is Y(s), soY(s) = H(s).
– The transfer function H(s) is the Laplace transform of
the unit impulse response h(t) where the Laplacetransform is defined by:
– Thus, if one wishes to characterize a linear time-invariant system, one applies a unit impulse, and the
resulting response is a description (inverse Laplace
transform) of the transform function.
st
st
0
H(s) h(t)e dt
h(t)e dt since h(t) 0 for t 0
∞ −
−∞∞ −
=
= =
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Dynamic System Response K. Craig 11
a linear time-invariant system is in finding the
frequency response. – Euler’s relation is:
– Let s = jω and, by superposition, the response tothe sum of these two exponentials which make up
the cosine signal, is the sum of the responses:
– The transfer function H(jω) is a complex number
that can be expressed in polar form (magnitudeand phase form) as H(jω) = M(ω)e jΦ(ω).
j t j tAAcos( t) (e e )2
ω − ωω = +
j t j tAy(t) H( j )e H( j )e2
ω − ω⎡ ⎤= ω + − ω⎣ ⎦
j( t ) j( t )Ay(t) M e e AM cos( t )2
ω +φ − ω +φ⎡ ⎤= + = ω + φ⎣ ⎦
– This means that if a system represented by the
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Dynamic System Response K. Craig 12
– This means that if a system represented by the
transfer function H(s) has a sinusoidal input with
magnitude A, the output will be sinusoidal at thesame frequency with magnitude AM and will be
shifted in phase by the angle Φ.
– The response of a linear time-invariant system to asinusoid of frequency ω is a sinusoid with the samefrequency and with an amplitude ratio equal to the
magnitude of the transfer function evaluated at theinput frequency. The phase difference between input
and output signals is given by the phase of the
transfer function evaluated at the input frequency.
The magnitude ratio and phase difference can be
computed from the transfer function or measured
experimentally.
T f F i h b i f l i l l
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Dynamic System Response K. Craig 13
– Transfer Functions, the basis of classical control
theory, require LTI systems, but no real-world system
is completely LTI. There are regions of nonlinear
operation and often significant parameter variation.
– Examples of Linear Behavior
• addition, subtraction, scaling by a fixed constant,
integration, differentiation, time delay, and
sampling
– No practical control system is completely linear and
most vary over time.
– LTI systems can be represented completely in the
frequency domain. Non-LTI systems can have
frequency response plots, however, these plots
change depending on system operating conditions.
• Non-LTI Behavior
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Dynamic System Response K. Craig 14
Non LTI Behavior
– Non-LTI behavior is any behavior that violates one
or more of the three criteria for an LTI system.
– Within nonlinear behavior, an important distinction
is whether the variation is slow or fast with respect
to the loop dynamics.
• Slow Variation
– When the variation is slow, the nonlinear behavior
may be viewed as a linear system with parametersthat vary during operation.
– The dynamics can still be characterized effectively
with a transfer function. However, the frequencyresponse plots will change at different operating
points.
• Fast Response
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Dynamic System Response K. Craig 15
Fast Response
– If the variation of the loop parameter is fast with
respect to the loop dynamics, the situation becomesmore complicated. Transfer functions cannot be
relied upon for analysis.
– The definition of fast depends on the systemdynamics.
• Fast vs. Slow
– The line between fast and slow is determined bycomparing the rate at which the parameter changes
to the bandwidth of the control system. If the
parameter variation occurs over a period of time nofaster than 10 times the control loop settling time, the
effect can be considered slow for most applications.
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Dynamic System Response K. Craig 16
• Dealing with Nonlinear Behavior
– Nonlinear behavior can usually be ignored if the
changes in parameter values effect the loop gain
by no more than about 25%. A variation this small
will be tolerated by systems with reasonablemargins of stability.
– If a parameter varies more than that, there are at
least three courses of action:• Modify the plant
• Tune for the worst-case conditions
• Compensate for the nonlinearity of the controlloop
• Modify the Plant
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Dynamic System Response K. Craig 17
• Modify the Plant
– Modifying the plant to reduce the parameter
variation is the most straightforward solution to
nonlinear behavior. It cures the problem without
adding complexity to the controller or
compromising system performance.
– This solution is commonly employed in the sense
that components used in control systems are
generally better (closer to LTI) than componentsused in open-loop systems.
– Enhancing the LTI behavior of a loop component
can increase its cost significantly. Componentsfor control systems are often more expensive than
open-loop components.
• Tune for the Worst-Case Conditions
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Dynamic System Response K. Craig 18
Tune for the Worst Case Conditions
– Assuming that the variation from the non-LTI
behavior is slow with respect to the control loop, itseffect is to change gains in the control loop. In this
case, the operating conditions can be varied to
produce the worst-case gains while tuning the controlsystem. Doing so will ensure stability for all
operating conditions.
– Tuning the system for worst-case operatingconditions generally implies tuning the proportional
gain of the inner loop when the plant gain is at its
maximum. This ensures that the inner loop will bestable in all conditions; parameter variation will only
lower the loop gain, which will reduce
responsiveness but will not cause instability.
– The other loop gains (inner loop integral and the outer
loops) should be stabilized when the plant gain is
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Dynamic System Response K. Craig 19
loops) should be stabilized when the plant gain is
minimized. This is because minimizing the plant gain
reduces the inner loop response; this will provide the
maximum phase lag to the outer loops and again
provides the worst case for stability.
– So tune the proportional gain with a high plant gain
and tune the other gains with a low plant gain to
ensure stability in all conditions.
– The penalty for tuning for worst case is the reduction inresponsiveness. Consider the proportional gain.
Because the proportional term is tuned with the highest
plant gain, the loop gain will be reduced at operatingpoints where the plant gain is low.
– In general, you should expect to lose responsiveness
in proportion to plant variation.
• Compensate in the Control Loop
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Dynamic System Response K. Craig 20
Compensate in the Control Loop
– Compensating for the nonlinear behavior in the
controller requires that a gain equal to the inverseof the non-LTI behavior be placed in the loop.
– This is called gain scheduling. By using gain
scheduling, the impact of the non-LTI behavior iseliminated from the control loop.
– Gain scheduling requires that the non-LTI
behavior be slow with respect to any transferfunctions between the non-LTI component and the
scheduled gain.
– This is a less onerous requirement than beingslow with respect to the loop bandwidth because
the loop components are always much faster than
the loop itself.
– Gain scheduling assumes that the non-LTI behavior
b di t d t bl ( ll
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Dynamic System Response K. Craig 21
can be predicted to reasonable accuracy (generally ±
25%) based on information available to the controller.This is often the case.
– Many times, a dedicated control loop will be placed
under the direction of a larger system controller. Themore flexible system controller can be used to
accumulate information on a changing gain and then
modify gains inside dedicated controllers to affect the
compensation.
– The chief shortcoming of gain scheduling via the
system controller is limited speed. The system
controller may be unable to keep up with the fastestplant variations. Still this solution is commonly
employed because of the controller’s higher level of
flexibility and broader access to information.
Solution of Linear, Constant-Coefficient
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Dynamic System Response K. Craig 22
,
Ordinary Differential Equations• A basic mathematical model used in many areas of
engineering is the linear, ordinary differential
equation with constant coefficients:
• qo is the output (response) variable of the system
• qi is the input (excitation) variable of the system
• an and bm are the physical parameters of the system
n n 1
o o on n 1 1 0 on n 1
m m 1
i i im m 1 1 0 im m 1
d q d q dqa a a a q
dt dt dt
d q d q dq b b b b q
dt dt dt
−
− −
−
− −
+ + + + =
+ + + +
• Straightforward analytical solutions are available no
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Dynamic System Response K. Craig 23
g y
matter how high the order n of the equation.
• Review of the classical operator method for solving lineardifferential equations with constant coefficients will be
useful. When the input qi(t) is specified, the right hand
side of the equation becomes a known function of time,f(t).
• The classical operator method of solution is a three-step
procedure: – Find the complimentary (homogeneous) solution qoc for
the equation with f(t) = 0.
– Find the particular solution qop with f(t) present. – Get the complete solution qo = qoc + qop and evaluate
the constants of integration by applying known initial
conditions.
• Step 1
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Dynamic System Response K. Craig 24
Step 1
– To find qoc
, rewrite the differential equation using
the differential operator notation D = d/dt, treat the
equation as if it were algebraic, and write the
system characteristic equation as:
– Treat this equation as an algebraic equation in the
unknown D and solve for the n roots (eigenvalues)
s1, s2, ..., sn. Since root finding is a rapid
computerized operation, we assume all the roots
are available and now we state rules that allowone to immediately write down qoc.
n n 1
n n 1 1 0a D a D a D a 0−
−+ + + + =
– Real unrepeated root s1:1s t
oc 1q c e=
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Dynamic System Response K. Craig 25
Real, unrepeated root s1:
– Real root s2
repeated m times:
– When the a0 to an in the differential equation are
real numbers, then any complex roots that mightappear always come in pairs a ± ib:
– For repeated root pairs a ± ib, a ± ib, and soforth, we have:
– The c’s and φ ’s are constants of integration whose
numerical values cannot be found until the last
step.
oc 1q c e
2 2 2 2s t s t s t s t2 m
oc 0 1 2 mq c e c te c t e c t e= + + + +
at
ocq ce sin(bt )= + φ
at at
oc 0 0 1 1q c e sin(bt ) c te sin(bt )= + φ + + φ +
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Dynamic System Response K. Craig 26
• Step 2
– The particular solution qop takes into account the"forcing function" f(t) and methods for getting the
particular solution depend on the form of f(t).
– The method of undetermined coefficients providesa simple method of getting particular solutions for
most f(t)'s of practical interest.
– To check whether this approach will work,differentiate f(t) over and over. If repeated
differentiation ultimately leads to zeros, or else to
repetition of a finite number of different timefunctions, then the method will work.
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Dynamic System Response K. Craig 27
– The particular solution will then be a sum of terms
made up of each different type of function found inf(t) and all its derivatives, each term multiplied by
an unknown constant (undetermined coefficient).
– If f(t) or one of its derivatives contains a termidentical to a term in qoc, the corresponding terms
should be multiplied by t.
– This particular solution is then substituted into thedifferential equation making it an identity. Gather
like terms on each side, equate their coefficients,
and obtain a set of simultaneous algebraic
equations that can be solved for all the
undetermined coefficients.
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Dynamic System Response K. Craig 28
• Step 3 – We now have qoc (with n unknown constants) and
qop (with no unknown constants).
– The complete solution qo = qoc + qop. – The initial conditions are then applied to find the n
unknown constants.
• Certain advanced analysis methods are most easily
d l d h h h f h L l T f
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Dynamic System Response K. Craig 29
developed through the use of the Laplace Transform.
• A transformation is a technique in which a function istransformed from dependence on one variable to
dependence on another variable. Here we will
transform relationships specified in the time domaininto a new domain wherein the axioms of algebra can
be applied rather than the axioms of differential or
difference equations.
• The transformations used are the Laplace
transformation (differential equations) and the Z
transformation (difference equations).
• The Laplace transformation results in functions of the
time variable t being transformed into functions of the
frequency-related variable s.
• The Z transformation is a direct outgrowth of the
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Dynamic System Response K. Craig 30
g
Laplace transformation and the use of a modulated
train of impulses to represent a sampled functionmathematically.
• The Z transformation allows us to apply the
frequency-domain analysis and design techniques ofcontinuous control theory to discrete control systems.
• One use of the Laplace Transform is as an
alternative method for solving linear differentialequations with constant coefficients. Although this
method will not solve any equations that cannot be
solved also by the classical operator method, itpresents certain advantages.
– Separate steps to find the complementary
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Dynamic System Response K. Craig 31
p p p y
solution, particular solution, and constants of
integration are not used. The complete solution,including initial conditions, is obtained at once.
– There is never any question about which initial
conditions are needed. In the classical operatormethod, the initial conditions are evaluated at t =
0+, a time just after the input is applied. For some
kinds of systems and inputs, these initialconditions are not the same as those before the
input is applied, so extra work is required to find
them. The Laplace Transform method uses theconditions before the input is applied; these are
generally physically known and are often zero,
simplifying the work.
– For inputs that cannot be described by a single
f l f th i ti b t t b d fi d
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Dynamic System Response K. Craig 32
formula for their entire course, but must be defined
over segments of time, the classical operator methodrequires a piecewise solution with tedious matching of
final conditions of one piece with initial conditions of
the next. The Laplace Transform method handles
such discontinuous inputs very neatly.
– The Laplace Transform method allows the use of
graphical techniques for predicting system
performance without actually solving system
differential equations.
• All theorems and techniques of the Laplace Transform
derive from the fundamental definition for the direct
Laplace Transform F(s) of the time function f(t):
[ ] st0
L f (t) F(s) f (t)e dt t > 0 s complex variable i∞ −= = = = σ + ω
∫
• This integral cannot be evaluated for all f(t)'s, but
h it it t bli h i i f f ti
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Dynamic System Response K. Craig 33
when it can, it establishes a unique pair of functions,
f(t) in the time domain and its companion F(s) in the sdomain. Comprehensive tables of Laplace
Transform pairs are available. Signals we can
physically generate always have corresponding
Laplace transforms. When we use the Laplace
Transform to solve differential equations, we must
transform entire equations, not just isolated f(t)
functions, so several theorems are necessary for this.
• Linearity (Superposition and Amplitude Scaling)
Theorem:
[ ] [ ] [ ]1 1 2 2 1 1 2 2 1 1 2 2L a f (t) a f (t) L a f (t) L a f (t) a F (s) a F (s)+ = + = +
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• Integration Theorem:
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Dynamic System Response K. Craig 35
– Again, the initial values of f(t) and its integrals areevaluated numerically at a time instant before the
driving input is applied.
• Convolution Theorem:
– Convolution in the time domain corresponds to
multiplication in the frequency domain.
( )
( )( )
( ) ( )
1
k nn
n n k 1
k 1n -0n
F(s) f (0)
L f (t)dt s s
F(s) f (0)L f (t)
s s
where f (t) f (t)(dt) and f (t) f (t)
−
−−
− +
=−
⎡ ⎤ = +⎣ ⎦
⎡ ⎤ = +⎣ ⎦
= ∫ ∫ =
∫∑
[ ]1 2 1 2L f (t) f (t) F (s)F (s)∗ =
• Time Delay Theorem:
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Dynamic System Response K. Craig 36
y
– The Laplace Transform provides a theorem useful
for the dynamic system element called dead time
(transport lag) and for dealing efficiently with
discontinuous inputs.
• Time Scaling Theorem: – If the time t is scaled by a factor a, then the
Laplace transform of the time-scaled signal is
u(t) 1.0 t 0
u(t) 0 t 0
u(t a) 1.0 t a
u(t a) 0 t a
= ⇒ >
= ⇒ <
− = ⇒ >− = ⇒ <
[ ] asL f (t a)u(t a) e F(s)−− − =
1 sF
a a
⎛ ⎞⎜ ⎟⎝ ⎠
• Final Value Theorem:
If we know Q (s) q ( ) can be found quickly without
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Dynamic System Response K. Craig 37
– If we know Q0(s), q0(∞) can be found quickly without
doing the complete inverse transform by use of the finalvalue theorem.
– This is true if the system and input are such that the
output approaches a constant value as t approaches ∞. – The DC gain of a system, the steady-state value of theunit-step response, is given by:
• Initial Value Theorem:
– This theorem is helpful for finding the value of f(t) just
after the input has been applied, i.e., at t = 0+. In gettingthe F(s) needed to apply this theorem, our usual
definition of initial conditions as those before the input is
applied must be used.
t s 0lim f (t) lim sF(s)→∞ →=
t 0 slim f (t) lim sF(s)→ →∞=
s 0 s 0
1DC Gain limsG(s) limG(s)
s→ →= =
• Impulse Function (t)δ
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Dynamic System Response K. Craig 38
– The step function is the integral of the impulse
function, or conversely, the impulse function is thederivative of the step function.
1/b
b
Approximating function for
the unit impulse function
p(t)
t
[ ]
b 0(t) lim p(t)
du 1L (t) L sU(s) s 1.0
dt s
→δ =
⎡ ⎤δ = = = =⎢ ⎥
⎣ ⎦
(t) 0 t 0
(t)dt 1 0+ε
−ε
δ = ⇒ ≠δ = ⇒ ε >∫
– When we multiply the impulse function by some
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Dynamic System Response K. Craig 39
When we multiply the impulse function by some
number, we increase the “strength of the impulse”,but “strength” now means area, not height as it
does for “ordinary” functions.
• An impulse that has an infinite magnitude and zero
duration is mathematical fiction and does not occur in
physical systems.
• If, however, the magnitude of a pulse input to a
system is very large and its duration is very short
compared to the system time constants, then we can
approximate the pulse input by an impulse function.
• The impulse input supplies energy to the system in
an infinitesimal time.
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Dynamic System Response K. Craig 40
Approximate and Exact
Impulse Functions
If es
=1.0 (unit step function),
its derivative is the unit
impulse function with a
strength (or area) of one unit.
This “non-rigorous” approach
does produce the correct result.
• Inverse Laplace Transformation
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Dynamic System Response K. Craig 41
– A convenient method for obtaining the inverse
Laplace transform is to use a table of Laplace
transforms. In this case, the Laplace transform must
be in a form immediately recognizable in such a table.
– If a particular transform F(s) cannot be found in atable, then we may expand it into partial fractions and
write F(s) in terms of simple functions of s for which
inverse Laplace transforms are already known. – These methods for finding inverse Laplace transforms
are based on the fact that the unique correspondence
of a time function and its inverse Laplace transformholds for any continuous time function.
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Dynamic System Response K. Craig 42
Time Response & Frequency Response
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Dynamic System Response K. Craig 43
1st-Order Dynamic System
Example: RC Low-Pass Filter
in out
in out
Dynamic System Investigation
of the
RC Low-Pass Filter
Zero-Order Dynamic System Model
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Dynamic System Response K. Craig 44
Zero Order Dynamic System Model
Step ResponseFrequency Response
Validation of a Zero-Order
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Dynamic System Response K. Craig 45
Dynamic System Model
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• How would you determine if an experimentally-
d t i d t f t ld b
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Dynamic System Response K. Craig 47
determined step response of a system could be
represented by a first-order system step response?
t
o is
t
o is
is
t
o
is
o10 10
is
q (t) Kq 1 e
q (t) Kqe
Kqq (t)
1 eKq
q (t) t tlog 1 log e 0.4343
Kq
−τ
−τ
−τ
⎛ ⎞
= −⎜ ⎟⎝ ⎠
−= −
− =
⎡ ⎤− = − = −⎢ ⎥ τ τ⎣ ⎦
Straight-Line Plot:
o10
is
q (t)log 1 vs. t
Kq
⎡ ⎤−⎢ ⎥
⎣ ⎦
Slope = -0.4343/τ
– This approach gives a more accurate value of τ sinceth b t li th h ll th d t i t i d th
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Dynamic System Response K. Craig 48
the best line through all the data points is used rather
than just two points, as in the 63.2% method.Furthermore, if the data points fall nearly on a straight
line, we are assured that the instrument is behaving as
a first-order type. If the data deviate considerably froma straight line, we know the system is not truly first order
and a τ value obtained by the 63.2% method would be
quite misleading. – An even stronger verification (or refutation) of first-order
dynamic characteristics is available from frequency-
response testing. If the system is truly first-order, the
amplitude ratio follows the typical low- and high-
frequency asymptotes (slope 0 and –20 dB/decade) and
the phase angle approaches -90° asymptotically.
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Dynamic System Response K. Craig 49
– If these characteristics are present, the numerical
value of τ is found by determining ω (rad/sec) atthe breakpoint and using τ = 1/ωbreak. Deviationsfrom the above amplitude and/or phase
characteristics indicate non-first-order behavior.
• What is the relationship between the unit-step
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Dynamic System Response K. Craig 50
What is the relationship between the unit step
response and the unit-ramp response and betweenthe unit-impulse response and the unit-step
response?
– For a linear time-invariant system, the response tothe derivative of an input signal can be obtained
by differentiating the response of the system to the
original signal.
– For a linear time-invariant system, the response to
the integral of an input signal can be obtained by
integrating the response of the system to the
original signal and by determining the integrationconstants from the zero-output initial condition.
• Unit-Step Input is the derivative of the Unit-Ramp
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Dynamic System Response K. Craig 51
p p p
Input.• Unit-Impulse Input is the derivative of the Unit-Step
Input.
• Once you know the unit-step response, take thederivative to get the unit-impulse response and
integrate to get the unit-ramp response.
System Frequency Response
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Dynamic System Response K. Craig 52
System Frequency Response
Bode Plotting of
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Dynamic System Response K. Craig 53
dB = 20 log10 (amplitude ratio)
decade = 10 to 1 frequency change
octave = 2 to 1 frequency change
g
1st
-Order Frequency
Response
0.01 40 dB0.1 20 dB
0.5 6 dB
1.0 0 dB2.0 6 dB
10.0 20 dB
100.0 40 dB
= −= −
= −
==
=
=
A l El t i
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Dynamic System Response K. Craig 54
Analog Electronics:
RC Low-Pass Filter
Time Response &
Frequency Response
outin
outin
outout
in
ee RCs 1 R
ii Cs 1
e 1 1 when i 0
e RCs 1 s 1
+ − ⎡ ⎤⎡ ⎤ ⎡ ⎤= ⎢ ⎥⎢ ⎥ ⎢ ⎥−⎣ ⎦⎣ ⎦ ⎣ ⎦
= = =+ τ +
Time Response to Unit Step Input
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Dynamic System Response K. Craig 55
0 1 2 3 4 5 6 7 8
x 10-4
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1
Time (sec)
A m p l i t u d e
Time Constant τ = RC
R = 15 K Ω
C = 0.01 μF
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Dynamic System Response K. Craig 56
• Time Constant τ
– Time it takes the step response to reach 63% of
the steady-state value
• Rise Time Tr
= 2.2 τ
– Time it takes the step response to go from 10% to
90% of the steady-state value
• Delay Time Td = 0.69 τ – Time it takes the step response to reach 50% ofthe steady-state value
Frequency
R
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Dynamic System Response K. Craig 57
Bandwidth = 1/τ
Response
1out
2 2 1 2 2in
e K K 0 K (i ) tan
e i 1 ( ) 1 tan ( ) 1
−
−
∠ω = = = ∠ − ωτ
ωτ + ωτ + ∠ ωτ ωτ +
R = 15 K Ω
C = 0.01 μF
• Bandwidth
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Dynamic System Response K. Craig 58
– The bandwidth is the frequency where the amplituderatio drops by a factor of 0.707 = -3dB of its gain at
zero or low-frequency.
– For a 1
st
-order system, the bandwidth is equal to1/τ.
– The larger (smaller) the bandwidth, the faster
(slower) the step response.
– Bandwidth is a direct measure of system
susceptibility to noise, as well as an indicator of the
system speed of response.
1Response to Input 1061 Hz Sine Wave
Amplitude Ratio = 0.707 = -3 dB Phase Angle = -45°
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Dynamic System Response K. Craig 59
0 0.5 1 1.5 2 2.5 3 3.5 4
x 10-3
-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1
time (sec)
a m p l i t u d e
Input
Output
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Physical Model Ideal Transfer Function
⎛ ⎞⎛ ⎞
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Dynamic System Response K. Craig 61
7
6 1 3 2 5out
2in
3 2 1 2 4 2 3 4 2 5
R 1
R R R C Ce(s)
e 1 1 1 1s s
R C R C R C R R C C
⎛ ⎞⎛ ⎞⎜ ⎟⎜ ⎟⎝ ⎠⎝ ⎠=
⎛ ⎞+ + + +⎜ ⎟
⎝ ⎠
2nd-Order Dynamic
System Model
0n
2
aundamped natural frequency
aω =
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Dynamic System Response K. Craig 62
System Model
2
0 02 1 0 0 0 i2
20 0
0 i2 2
n n
d q dqa a a q b q
dt dt
d q dq1 2q Kq
dt dt
+ + =
ζ+ + =ω ω
1
2 0
0
0
a damping ratio2 a a
b
K steady-state gaina
ζ =
=
Step Response
of a2nd-Order System
2
0 00 i2 2
d q dq1 2q Kq
dt dt
ς+ ζ + =
ω ω
Step Response
of ad d
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Dynamic System Response K. Craig 63
n ndt dtω ω
( )n t 2 1 2
o is n
2
1q Kq 1 e sin 1 t sin 1 1
1
−ζω −⎡ ⎤
= − ω − ζ + − ζ ζ ⎢ ⎥ζ − ζ −⎢ ⎥+⎢ ⎥ζ −
⎣ ⎦
( ) n to is nq Kq 1 1 t e 1−ω⎡ ⎤= − + ω ζ =⎣ ⎦
Over-
damped
Critically Damped
Underdamped
Frequency Response
of a
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Dynamic System Response K. Craig 64
of a
2nd-Order System
( )o 2i
2
n n
Q K s
s 2 sQ 1
=
ζ+ +ω ω
( ) 1o22i 2 2 n
2 n
n n
Q K 2i tan
Q 41
− ζω = ∠⎛ ⎞ω ω⎡ ⎤ −⎛ ⎞ω ζ ω ⎜ ⎟− +⎢ ⎥ ω ω⎜ ⎟ ⎝ ⎠ω ω⎢ ⎥⎝ ⎠⎣ ⎦
Laplace Transfer Function
Sinusoidal Transfer Function
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Dynamic System Response K. Craig 65
Frequency Response
of a
2nd-Order System
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Dynamic System Response K. Craig 66
Frequency Response
of a
2nd-Order System
-40 dB per decade slope
• Some Observations
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Dynamic System Response K. Craig 67
• When a physical system exhibits a natural oscillatorybehavior, a 1st-order model (or even a cascade of
several 1st-order models) cannot provide the desired
response. The simplest model that does possess
that possibility is the 2nd-order dynamic system
model.
• This system is very important in control design.
– System specifications are often given assuming
that the system is 2nd order.
– For higher-order systems, we can often use
dominant pole techniques to approximate the
system with a 2nd-order transfer function.
• Damping ratio ζ clearly controls oscillation; ζ < 1 isrequired for oscillatory behavior.
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Dynamic System Response K. Craig 68
• The undamped case (ζ = 0) is not physically realizable(total absence of energy loss effects) but gives us,mathematically, a sustained oscillation at frequency ωn.
• Natural oscillations of damped systems are at thedamped natural frequency ωd, and not at ωn.
• In hardware design, an optimum value of ζ = 0.64 isoften used to give maximum response speed withoutexcessive oscillation.
• Undamped natural frequency ωn is the major factor inresponse speed. For a given ζ response speed isdirectly proportional to ωn.
2
d n 1ω = ω − ζ
• Thus, when 2nd-order components are used in
feedback system design, large values of ωn (small
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Dynamic System Response K. Craig 69
lags) are desirable since they allow the use of largerloop gain before stability limits are encountered.
• For frequency response, a resonant peak occurs for ζ
< 0.707. The peak frequency is ωp and the peakamplitude ratio depends only on ζ.
• Bandwidth
– The bandwidth is the frequency where theamplitude ratio drops by a factor of 0.707 = -3dB of
its gain at zero or low-frequency.
2
p n 2
K 1 2 peak amplitude ratio
2 1ω = ω − ζ =
ζ − ζ
– For a 1st -order system, the bandwidth is equal to
1/τ.
The larger (smaller) the bandwidth the faster
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