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Wei Wu Electrical Engineering Department
University of California, Los Angeles
Chapter 2
Interconnect Analysis
Delay Modeling
S2P and Effective Capacitance
2
Outline
Delay models
Review of Elmore Delay
Second Order Analysis (S2P algorithm)
Gate delay
3
( ) 1
t
RCV t e
R
C
V(t) 1v
How about more complex circuits?
Review of Elmore Delay
1
0.5
50% delay
RCt
e RC
t
69.0
5.0
50% Delay for lumped RC model
R1
C1
s
C3
R3
Ci
Ri
1
2
3
4
i
4
Example
Elmore delay at node i is
))()( iii433i43211
ii314313312111
iii4i43i32i21i1Di
CRCCCCCCCC0.69(R
))CRR(R)CR(R)CR(RCRC0.69(R
)CRCRCRCRC0.69(Rτ
R
R1
C1
s
C3
R3
Ci
Ri
1
2
3
4
i
5
Elmore Delay Approximation
The Elmore delay is the metric of choice for performance-driven design applications due to its simple, explicit form and ease with which sensitivity information can be calculated
However, for deep submicron technologies (DSM), the
accuracy of the Elmore delay is insufficient
6
Outline
Delay models
Review of Elmore Delay
Second Order Analysis (S2P algorithm)
Gate delay
7
Second Order Analysis (Stable 2-Pole Delay Algorithm) General Idea: MOR Original RC network: 2 poles Model: (Model Order Reduction: AWE) Generate the time domain single from 2P model: eg:
Alternative solution: S2P Algorithm
( ), ( ) 0
1
qknH s Y s k
s pnn
0 1 1 2
21 2 1 2
( )1
b b s k kh s
s p s pa s a s
1 2ˆImpulse Response: ( ) ( ) ( )1 2p t p t
h t k e k e u t
Emrah Acar, Altan Odabasioglu, Mustafa Celik, and Lawrence T. Pileggi. 1999. “S2P: A Stable 2-
Pole RC Delay and Coupling Noise Metric”. In Proceedings of the Ninth Great Lakes Symposium on
VLSI(GLS '99).
8
Moments of H(s)
Moments of H(s) are coefficients of the Taylor’s Expansion of H(s) about s=0
0
1( ) ( )! s
jdjm H sjj ds
0 0 0
2 31 12 3( ) ( ) ( ) ( ) ...0 2 32! 3!s s s
d d dH s H s H s s H s s H s
ds ds ds
(0) (1) 2 (2) 3 (3) ...m sm s m s m
9
Let Y(s) be an driving point admittance function of a general RC circuit. Consider its representation in terms poles and residues
where q is the exact order of the circuit
Moments of Y(s) can be written as:
( ) 0
1
qknY s k
s pnn
01
1
qknm ii ipnn
Driving Point Admittance
10
Compute m1, m2, m3 and m4 for Y(s) Find the two poles at the driving point admittance as follows: To match the voltage moments at the response nodes, choose and the S2P approximation is then expressed as:
Note that m0* and m1* are the moments of H(s). m0* is the Elmore delay.
S2P Algorithm
Emrah Acar, Altan Odabasioglu, Mustafa Celik, and Lawrence T. Pileggi. 1999. “S2P: A Stable 2-
Pole RC Delay and Coupling Noise Metric”. In Proceedings of the Ninth Great Lakes Symposium on
VLSI(GLS '99).
11
S2P Vs. Elmore Delay
0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1
0.4
0.5
0.6
0.7
0.8
0.9
1
t
Voltage
SPICE
Elmore
S2P
12
Outline
Delay models
Review of Elmore Delay
Second Order Analysis (S2P algorithm)
Gate delay
13
Gate Delay
BCABAC DelayDelayDelay
A B C
Inv 1 Inv 2
Overall flow of delay calculation
DelayAB: Gate delay DelayBC: RC network delay
14
General Model of a Gate
15
Definitions
Vin Vout
Time
Gate Delay
90%
10%
Output Transition Time
Gate/Cell
T in
Cloadt
in
16
The gate delay and the output transition time are functions of both input slew and the output load
Gate/Cell
T in
Cload
( , )in loadGate Delay f T C
( , )in loadOutput Transition Time f T C
Gate Delay and Output Transition Time
17
Output Response for Different Loads
18
Three approaches for gate propagation delay computation are based on: – Delay look-up tables – K-factor approximation Effective capacitance
Delay look-up table is currently in wide use especially in the ASIC design flow
Effective capacitance promises to be more accurate when the load is not purely capacitive
ASIC Cell Delay Model
19
What is the delay when Cload is 505f F and Tin is 90pS?
Cload (fF)
Tin
(pS)
0 5 10 500 505 510
50
70
90
110
310
330
115pS
Table Look-Up Method
20
We can fit the output transition time v.s. input
transition time and output load as a polynomial function, e.g.
A similar equation gives the gate delay
2( )1 2 3 4 5T k k C T k k C k Coutput load in load load
K-factor Approximation
2 2.4 2.8 3.2 3.6 4
x 10-10
5
6
7
8
9
10
11x 10
-11
Size=69 Cout=23fF
Size=48 Cout=15fF
Size=90 Cout=18fF
Input Transition Time (s)
Ou
tpu
t T
ran
siti
on
tim
e (s
)
10-10
1 1.4 1.8 2.2 2.6 3
x 10-14
6
7
8
9
10
11x 10
-11
Size=60 Tin=300pS
Size=81 Tin=350pS
Size=45 Tin=200pS
Ou
tpu
t T
ran
siti
on
tim
e (s
)
CLoad (F) 10-14
21
The gate delay and the output transition time are functions of both input slew and the output load
Gate/Cell
T in
Cload
( , )in loadGate Delay f T C
( , )in loadOutput Transition Time f T C
How to calculate the Cload??
22
Gate /Cell
T in
2 31 2 3( ) .....inY s A s A s A s
2 2 2 3 31 2 2 2( ) ( ) .....inY s C C s R C s R C s
22 232 2
1 1 233 32
AA AC A R C
A AA
Gate /Cell
Tin R
C1
C2
Using Taylor Expansion around s = 0
Second-order RC- Model
23
Gate /Cell
Tin R
C1
C2
1 2( , , , )inGate Delay f T C R C
This equation requires creation of a four-dimensional table to achieve high accuracy
This is however costly in terms of memory space and computational requirements
Second-order RC- Model (Cont’d)
24
The “Effective Capacitance” approach attempts to find a single capacitance value that can be replaced instead of the RC- load such that both circuits behave similarly during transition
What’s the value of Ceff, C1+C2???
Gate /Cell
Tin R
C1
C2
Gate /Cell
T in
Ceff
Effective Capacitance Approach
25
Output Response for Effective Capacitance
26
Effective Capacitance (Cont’d)
27
0<k<1
Gate /Cell
Tin R
C1
C2
21 kCCCeff
Because of the shielding effect of the interconnect resistance , the driver will only “see” a portion of the far-end capacitance C2
R 0 k = 1
R ∞ k = 0
Gate /Cell
T in
Ceff
Effective Capacitance (Cont’d)
28
Effective Capacitance for Different Resistive Shielding
29
Assumption: If two circuits have the same loads and output transition times, then their effective capacitances are the same
=> the effective capacitance is only a function of the output transition time and the load
GATE 2
Tin2 R
C1
C2
GATE 1
Tin1 R
C1
C2
Macy’s Approach
R. Macys and S. McCormick, “A New Algorithm for Computing the “Effective Capacitance” in Deep
Sub-micron Circuits”, Custom Integrated Circuits Conference 1998, pp. 313-316
30
1. Compute a from C1 and C2 2. Choose an initial value for
Ceff 3. Compute Tout for the given
Ceff and Tin
4. Compute b
5. Compute g from a and b 6. Find new Ceff 7. Go to step 3 until Ceff
converges
GATE 1
Tin1 R
C1
C2
21
1
CC
C
a
2CR
Tout
b
21 CC
Ceff
g
Macy’s Iterative Solution
R. Macys and S. McCormick, “A New Algorithm for Computing the “Effective Capacitance” in Deep
Sub-micron Circuits”, Custom Integrated Circuits Conference 1998, pp. 313-316
31
Summary
31
Delay model – Elmore Delay model – S2P model Reduce the RC network to a 2-pole model AWE is adopted for MOR
– Gate delay: look-up table, k-factor approximation, effective capacitance
A B C
Inv 1 Inv 2
32
References
32
R. Macys and S. McCormick, “A New Algorithm for Computing the “Effective Capacitance” in Deep
Sub-micron Circuits”, Custom Integrated Circuits Conference 1998, pp. 313-316
J. Qian, S. Pullela, and L. T. Pileggi, "Modeling the "effective capacitance" for the RC interconnect
of CMOS gates," IEEE Trans. on Computer-Aided Design of Integrated Circuits and Systems, vol.
13, pp. 1526-1535, Dec. 1994.
Jason Cong , Lei He , Cheng-Kok Koh , Patrick H. Madden, Performance optimization of VLSI
interconnect layout, Integration, the VLSI Journal, v.21 n.1-2, p.1-94, Nov. 1996 (Section 2.1-2.2)
W. C. Elmore, “The Transient Response of Damped Linear Networks with Particular Regard to
Wideband Amplifiers”, Journal of Applied Physics, 1948.
Jorge Rubinstein, and etc. “Signal Delay in RC Tree Networks”, TCAD'83
Emrah Acar, Altan Odabasioglu, Mustafa Celik, and Lawrence T. Pileggi. 1999. “S2P: A Stable 2-Pole
RC Delay and Coupling Noise Metric”. In Proceedings of the Ninth Great Lakes Symposium on
VLSI(GLS '99).